HIP5600IS2 [RENESAS]
1.2 V-ADJUSTABLE POSITIVE REGULATOR, PSSO3, GULLWING, PLASTIC, SIP-3;
| 型号： | HIP5600IS2 |
| 厂家： | 
RENESAS TECHNOLOGY CORP |
| 描述： | 1.2 V-ADJUSTABLE POSITIVE REGULATOR, PSSO3, GULLWING, PLASTIC, SIP-3 输出元件 调节器 |
| 文件： | 总16页 (文件大小：889K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
HIP5600
®
September 1998
File Number 3270.7
Thermally Protected High Voltage Linear
Regulator
Features
• Operates from 50V
• Operates from 50V
• UL Recognized
to 400V
DC
DC
The HIP5600 is an adjustable 3-terminal positive linear
to 280V
Line
RMS
RMS
voltage regulator capable of operating up to either 400V
DC
. The output voltage is adjustable from 1.2V
or 280V
RMS
DC
• Variable DC Output Voltage 1.2V
DC
to V - 50V
IN
to within 50V of the peak input voltage with two external
resistors. This high voltage linear regulator is capable of
sourcing 1mA to 30mA with proper heat sinking. The
HIP5600 can also provide 40mA peak (typical) for short
periods of time.
• Internal Thermal Shutdown Protection
• Internal Over Current Protection
• Up to 40mA Peak Output Current
Protection is provided by the on chip thermal shutdown and
output current limiting circuitry. The HIP5600 has a unique
advantage over other high voltage linear regulators due to its
ability to withstand input to output voltages as high as
400V(peak), a condition that could exist under output short
circuit conditions.
• Surge Rated to ±650V; Meets IEEE/ANSI C62.41.1980
with Additional MOV
CAUTION: This product does not provide isolation from AC
line.
Applications
• Switch Mode Power Supply Start-Up
Common linear regulator configurations can be implemented
as well as AC/DC conversion and start-up circuits for switch
mode power supplies.
• Electronically Commutated Motor Housekeeping Supply
• Power Supply for Simple Industrial/Commercial/Consumer
Equipment Controls
The HIP5600 requires a minimum output capacitor of 10µF
for stability of the output and may require a 0.02µF input
decoupling capacitor depending on the source impedance. It
also requires a minimum load current of 1mA to maintain
output voltage regulation.
• Off-Line (Buck) Switch Mode Power Supply
Ordering Information
PART
All protection circuitry remains fully functional even if the
adjustment terminal is disconnected. However, if this
happens the output voltage will approach the input voltage.
NUMBER
HIP5600IS
HIP5600IS2
TEMP. RANGE
PACKAGE
o
o
-40 C to +100 C
3 Lead Plastic SIP
o
o
-40 C to +100 C
3 Lead Gullwing Plastic
SIP
Pinouts
HIP5600 (TO-220)
HIP5600 (MO-169)
TOP VIEW
TOP VIEW
TAB ELECTRICALLY
CONNECTED
V
OUT
TO V
OUT
HIP5600
CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures.
1-888-INTERSIL or 321-724-7143 | Intersil (and design) is a registered trademark of Intersil Americas Inc.
Copyright © Intersil Americas Inc. 2002. All Rights Reserved
63
HIP5600
Functional Block Diagram
HIP5600
RECTIFIER FOR
AC OPERATION
PASS
TRANSISTOR
SHORT-CIRCUIT
PROTECTION
V
OUT
-
V
IN
+
+
-
RF1
RF2
BIAS
NETWORK
C2
-
C1
+
THERMAL
SHUTDOWN
FEEDBACK
OR CONTROL
AMPLIFIER
VOLTAGE
REFERENCE
+
-
ADJ
Schematic Diagram
V
IN
R1
D3
D2
D1
D4
Q1
R2
Q2
R3
Q11
R12
D7
D8
Q12
R13
D9
Q4
R4
Q9
D6
Q5
R11
R5
D5
Q14
R14
C1
R7
Q3
Q6
Q10
Q13
R8
R6
R15
Q8
Q7
V
OUT
R10
R9
ADJ
FIGURE 1.
64
HIP5600
Absolute Maximum Ratings
Thermal Information (Typical)
Input to Output Voltage, Continuous . . . . . . . . . . . . +480V to -550V Thermal Resistance
θ
θ
JC
4 C/W
JA
o
o
Input to Output Voltage, Peak (Non Repetitive, 2ms) . . . . . . . ±650V
Plastic SIP Package . . . . . . . . . . . . . . 60 C/W
o
Junction Temperature. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . +150 C
ADJ to Output, Voltage to ADJ . . . . . . . . . . . . . . . . . . . . . . . . . . . . ±5V
o
o
o
Storage Temperature Range . . . . . . . . . . . . . . . . . -65 C to +150 C
Lead Temperature (Soldering 10s). . . . . . . . . . . . . . . . . . . . +265 C
CAUTION: Stresses above those listed in “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress only rating and operation
of the device at these or any other conditions above those indicated in the operational sections of this specification is not implied.
Operating Conditions
o
o
Operating Voltage Range. . . . . . . . . . . . . . 80V
RMS
to 280V
or
Operating Temperature Range . . . . . . . . . . . . . . . .-40 C to +100 C
RMS
to 400V
50V
DC
DC
Electrical Specifications Conditions V = 400VDC, I = 1mA, C = 10µF, V
= 3.79V, V
= 5V (Unless Otherwise Specified) Tem-
IN
L
L
ADJ
OUT
perature = Case Temperature.
PARAMETER
CONDITION
TEMP
MIN
TYP
MAX
UNITS
INPUT
Input Voltage
DC
Non-Repetitive (2ms)
Full
Full
Full
Full
50
-
-
-
400
±650
1000
0.6
V
V
Max Peak Input Voltage
Input Frequency (Note 1)
DC
0.4
-
Hz
mA
Bias Current (I
REFERENCE
Note 2)
0.5
BIAS
o
I
I
I
+25 C
50
65
+0.15
-215
1.18
-460
9
80
µA
ADJ
ADJ
o
T
(Note 1)
I
I
= 1mA
Full
-
-
-
µA/ C
C
L
L
o
(Note 1)
= 1mA to 10mA
+25 C
-
nA/mA
V
ADJ LOAD REG
o
V
V
(Note 3)
+25 C
1.07
1.30
-
REF
REF
o
T
(Note 1)
I
= 1mA
Full
-
-
-
-
-
µV/ C
C
L
o
Line Regulation
V
50VDC to 400VDC
+25 C
14.5
29
5
µV/V
µV/V
REF LINE REG
Full
9
o
Load Regulation
V
I
= 1mA to 10mA
+25 C
3
mV/mA
mV/mA
OUT
REF LOAD REG
Full
3
6
PROTECTION CIRCUITS
o
Output Short Circuit Current Limit
V
V
= 50V
+25 C
35
-
45
mA
IN
IN
o
Thermal Shutdown T
= 400V
-
-
127
134
142
C
TS
(IC surface, not case temperature. Note 1)
o
Thermal Shutdown Hysteresis (Note 1)
V
= 400V
-
34
-
C
IN
NOTES:
1. Characterized not tested
2. Bias current ≡ input current with output pin floating.
3. V
REF
= V - V
OUT ADJ
65
HIP5600
Application Information
Introduction
V
RF1
3.6k
2.7k
1.8k
1.1k
RF2
5.6k
7.5k
15k
OUT(NOMINAL)
In many electronic systems the components operate at 3V to
15V but the system obtains power from a high voltage
source (AC or DC). When the current requirements are
small, less than 10mA, a linear regulator may be the best
supply provided that it is easy to design in, reliable, low cost
and compact. The HIP5600 is similar to other 3 terminal reg-
ulators but operates from much higher voltages. It protects
its load from surges +250V above its 400V operating input
voltage and has short circuit current limiting and thermal
shutdown self protection features.
HIP5600
3.3V
4.9V
AC/DC
12.0V
14.8V
12k
I
1
V
REF
RF1
V
OUT
I
ADJ
RF2
Output Voltage
AC/DC
FIGURE 2.
The HIP5600 provides a temperature independent 1.18V
reference, V
terminal (V
, between the output and the adjustment
REF
= V
Example: Given:
2mA to 12mA, θ
V
= 200V , V
= 15V, I
=
OUT
IN
DC OUT
- V ). This constant reference
o
REF
OUT
ADJ
= 10 C/W, RF1 = 1.1kΩ 5% low, RF2 =
equals 10mA and ∆Temp equals
SA
voltage is impressed across RF1 (see Figure 2) and results
in a constant current (I ) that flows through RF2 to ground.
The voltage across RF2 is the product of its resistance and
12kΩ 5% high, ∆I
OUT
+60 C (ambient temperature +25 C to +85 C). The worst
case ∆V for the given conditions is -1.13V. The shift in
o
o
o
1
OUT
is attributed to the following: -1.55V manufacturing tol-
the sum of I and I
The output voltage is given in Equa-
1
ADJ.
V
OUT
tions 1(A, B).
erances, +1.33V external resistors, -0.62V load regulation
RF1 + RF2
)------------------------------ + I
ADJ
RF1
and -0.29V temperature effects.
(EQ. 1A)
(EQ. 1B)
V
= (V
(RF2)
OUT
OUT
REF
Regulator With Zener
RF1 + RF2
V
= (1.18) × ------------------------------ + 65µA(RF2)
RF1
V
= 1.18 + V
Z
OUT
V
V
Z
OUT
HIP5600
3.7V
5.1V
2.5V
3.9V
9.1V
11V
15V
Error Budget
AC/DC
∆RF2
RF2
RF1 + RF2
T
T
∆V
= ∆V
------------------------ + ∆I
RF2 + I
ADJ
RF2-------------
ADJ
10.3V
REF
OUT
RF1
12.2V
∆RF2 ∆RF1
RF2 RF1
RF2
RF1
I
1
(EQ. 2A)
+V
--------- ----------- –-------------
V
REF
REF
RF1
16.2V
V
OUT
Where;
RF1 = 10k
I
ADJ
V
Z
T
REF
∆V
≡ ∆V
+ V
(∆I
) + V
TC(∆Temp)
REF
REF
REF
OUT
LOADREG
AC/DC
+V
TC(θ )∆(I
⋅ V ) + V
IN
REF
SA
OUT
REF
LINEREG
FIGURE 3.
(EQ. 2B)
T
The output voltage can be set by using a zener diode (Figure
3) instead of the resistor divider shown in Figure 2. The
zener diode improves the ripple rejection ratio and reduces
the value of the worst case output voltage, as illustrated in
the example to follow. The bias current of the zener diode is
∆I
≡ ∆I
+ I
(∆I
) + I
TC(∆Temp)
ADJ
ADJ
ADJ
ADJ
OUT
LOADREG
+I
TC(θ )∆(I
SA
⋅ V
)
IN
ADJ
OUT
(EQ. 2C)
Note:
set by the value of RF1 and I
.
ADJ
∆RFx
---------------
RFx
= % tolerance of resistor x
The regulator / zener diode becomes an attractive solution if
ripple rejection or the worst case tolerance of the output volt-
age is critical (i.e. one zener diode cost less than one 10µF
capacitor (C3) and one 1/4W resistor RF2). Minimum power
dissipation is possible by reducing I current, with little effect
on the output voltage regulation. The output voltage is given
in Equation 3.
Equations 2(A,B,C) are provided to determine the worst
case output voltage in relation to; manufacturing tolerances
(∆V
and ∆I
),% tolerance in external resistors
REF
REF
1
(∆RF1/RF1, ∆RF2/RF2), load regulation (V
,
REF LOAD REG
I
), line regulation (V
) and the
ADJ LOAD REG
effects of temperature (V
self heating (θ ).
REF LINE REG
TC), which includes
REF
TC, I
REF
SA
Equations 4(A,B,C) are provided to determine the worst
case output voltage in relation to; manufacturing tolerances
66
HIP5600
V
= V
+ V
Z
REF
OUT
(EQ. 3)
Error Budget
HIP5600
HIP5600
T
T
(EQ. 4A)
TC(∆Temp)
(EQ. 4B)
∆V
= ∆V
+ ∆V
Z
REF
OUT
AC/DC
AC/DC
T
∆V
≡ ∆V
+ V
(∆I
) + V
OUT REF
REF
REF
REF
LOADREG
R
S
R
S
+V
TC(θ )∆(I
SA
⋅ V ) + V
OUT IN
REF
T
REF
LINEREG
V
I
I
1
V
REF
1
REF
RF1
RF1
V
V
OUT
OUT
∆V ≡ V tolerance(V ) + V TC(∆Temp)
(EQ. 4C)
Z
Z
Z
Z
I
I
ADJ
ADJ
RF2
RF2
of HIP5600 and the zener diode (∆V
and ∆V ), load reg-
), and the effects of
REF
z
AC/DC
AC/DC
ulation of the HIP5600 (V
REF LOAD REG
(B)
(A)
temperature on the HIP5600 and the zener diode (V
TC,
FIGURE 4.
REF
V TC).
Z
Protection Diodes
Example: Given:
V
= 200V, V
= 14.18V (V
=
REF
IN
OUT
The HIP5600, unlike other voltage regulators, is internally
protected by input diodes in the event the input becomes
shorted to ground. Therefore, no external protection diode is
required between the input pin and the output pin to protect
against the output capacitor (C2) discharging through the
input to ground.
1.18V, V = 13V), ∆V = 5%, V TC = +0.079%/°C (assumes
Z
Z
Z
1N5243BPH), ∆I
equal 10mA and ∆Temp equal
OUT
o
+60 C. The worst case ∆V
is 0.4956V. The shift in
OUT
is attributed to the following: -0.2 (HIP5600) and 0.69
V
OUT
(zener diode).
The regulator/zener diode configuration gives a 3.5%
(0.49/14.18) worst case output voltage error where, for the
same conditions, the regulator/resistor configuration results
in an 7.5% (1.129/15) worst case output voltage error.
If the output is shorted in the absence of D1 (Figure 5), the
bypass capacitor voltage (C3) could exceed the absolute
maximum voltage rating of ±5V between V
and V .
OUT
IN
Note; No protection diode (D1) is needed for output voltages
less than 6V or if C3 is not used.
External Capacitors
A minimum10µF output capacitor (C2) is required for stability
of the output stage. Any increase of the load capacitance
greater than 10µF will merely improve the loop stability and
output impedance.
V
IN
HIP5600
C1
0.02µF
A 0.02µF input decoupling capacitor (C1) between V and
IN
D1 PROTECTS AGAINST C3
DISCHARGING WHEN THE
OUTPUT IS SHORTED.
ground may be required if the power source impedance is
not sufficiently low for the 1MHz - 10MHz band. Without this
capacitor, the HIP5600 can oscillate at 2.5MHz when driven
by a power source with a high impedance for the 1MHz -
10MHz band.
+ V
OUT
D1
RF1
C2
10µF
C3
10µF
An optional bypass capacitor (C3) from V
to ground
RF2
ADJ
improves the ripple rejection by preventing the ripple at the
Adjust pin from being amplified. Bypass capacitors larger
than 10µF do not appreciably improve the ripple rejection of
the part (see Figure 20 through Figure 25).
FIGURE 5. REGULATOR WITH PROTECTION DIODE
Selecting the Right Heat Sink
Load Regulation
Linear power supplies can dissipate a lot of power. This
power or heat must be safely dissipated to permit continuous
operation. This section will discuss thermal resistance and
show how to calculate heat sink requirements.
For improved load regulation, resistor RF1 (connected
between the adjustment terminal and V
) should be tied
OUT
directly to the output of the regulator (Figure 4A) rather than
near the load Figure 4B. This eliminates line drops (R ) from
S
appearing effectively in series with RF1 and degrading regu-
lation. For example, a 15V regulator with a 0.05Ω resistance
between the regulator and the load will have a load regula-
Electronic heat sinks are generally rated by their thermal
resistance. Thermal resistance is defined as the temperature
rise per unit of heat transfer or power dissipated, and is
expressed in units of degrees centigrade per watt. For a par-
tion due to line resistance of 0.05Ω x ∆I . If RF1 is con-
L
nected near the load the effective load regulation will be 11.9
times worse (1+R2/R1, where R2 = 12k, R1 = 1.1k).
ticular application determine the thermal resistance (θ
)
SA
which the heat sink must have in order to maintain a junction
temperature below the thermal shut down limit (T ).
TS
67
HIP5600
A thermal network that describes the heat flow from the inte-
Example,
grated circuit to the ambient air is shown in Figure 6. The
basic relation for thermal resistance from the IC surface, his-
Given: V = 400V
IN
V
T
= 15V
I
I
= 15mA
DC
OUT
LOAD
= 80µA
ADJ
o
ο
torically called “junction”, to ambient (θ ) is given in Equa-
θ
= 4.8 C/W
= +127 C
JA
JC
TS
tion 5. The thermal resistance of the heat sink (θ ) to
SA
o
T
= +50 C
RF1 = 1.1k
A
maintain a desired junction temperature is calculated using
Equation 6.
V
= 1.18V P = 6.2W = (V - V
IN
)(I )
OUT IN
REF
PD
V
REF
T
= JUNCTION
I
≡ I
+ ------------------ + I
J
ADJ
LOAD
IN
RF1
θJC
θCS
Find:
of the HIP5600 from exceeding T (+127 C).
Proper heat sink to keep the junction temperature
T
= CASE
C
o
TS
Solution:
Use Equation 6,
T
= HEAT SINK
S
HEAT SINK
θSA
T
– T
TS
A
θ
= --------------------------- – θ
T
= AMBIENT AIR
(EQ. 7)
(EQ. 8)
A
SA
JC
P
FIGURE 6.
= 1----2----7----°----C--6----.-–2----5----0----°----C--- – 4.8°C = 7.62°----C----
θ
SA
W
T
– T
J
A
°C
--------
W
θ
= ---------------------
(EQ. 5)
(EQ. 6)
JA
P
o
The selection of a heat sink with θ
less than +7.62 C/W
SA
Where:
would ensure that the junction temperature would not
exceed the thermal shut down temperature (T ) of
θ
= θ
+ θ
+ θ
TS
T
= T
JA
JC
CS
SA
and
J
TS
o
+127× C. A Thermalloy P/N7023 at 6.2W power dissipation
o
would meet this requirement with a θ of +5.7× C/W.
∴
SA
T
– T
TS
A
θ
+ θ
≈ θ
= --------------------------- – θ
Operation Without A Heatsink
SA
SA
JC
P
CS
o
The package has a
θ
of +60 C/W. This allows 0.7W
JA
o
power dissipation at +85 C in still air. Mounting the HIP5600
to a printed circuit board (see Figure 39 through Figure 41)
decreases the thermal impedance sufficiently to allow about
Where:
θ
= (Junction to Ambient Thermal Resistance) The sum of
the thermal resistances of the heat flow path.
JA
o
1.6W of power dissipation at +85 C in still air.
θ
= θ + θ
+ θ
JA
T = (Junction Temperature) The desired maximum junc-
JC CS
SA
Thermal Transient Operation
J
For applications such as start-up, the HIP5600 in the TO-220
package can operate at several watts -without a heat sink-
for a period of time before going into thermal shutdown.
tion temperature of the part. T = T
J
TS
T
= (Thermal Shutdown Temperature) The maximum
junction temperature that is set by the thermal pro-
tection circuitry of the HIP5600
TS
o
o
o
(min = +127 C, typ = +134 C and max = +142 C).
P
= I (V - V
IN IN
)
OUT
D
θ
= (Junction to Case Thermal Resistance) Describes the
JC
thermal resistance from the IC surface to its case.
o
T
= JUNCTION
J
θ
= 4.8 C/W
JC
0.6θ
0.4θ
JC
C
D
θ
= (Case to Mounting Surface Thermal Resistance) The
resistance of the mounting interface between the
transistor case and the heat sink.
CS
DIE/PACKAGE INTERFACE
0.5C
P
JC
For example, mica washer.
T
= HEAT SINK
OR CASE
S
θ
= (Mounting Surface to Ambient Thermal Resistance)
The resistance of the heat sink to the ambient air.
Varies with air flow.
SA
θ
SA
CS + 0.5C
P
T
= AMBIENT AIR
A
T
= Ambient Temperature
A
P = The power dissipated by the HIP5600 in watts.
P = (V - V )(I
FIGURE 7. THERMAL CAPACITANCE MODEL OF HIP5600
)
IN OUT OUT
Figure 7 shows the thermal capacitances of the TO-220
package, the integrated circuit and the heat sink, if used.
When power is initially applied, the mass of the package
absorbs heat which limits the rate of temperature rise of the
Worst case θ
is calculated using the minimum T
of
TS
SA
+127 C in Equation 6.
o
68
HIP5600
junction. With no heat sink C equals zero and θ equals the
S
SA
T (t) = T + T + T + T
(EQ. 11A)
difference between θ and θ . The following equations pre-
J
A
1
2
3
JA JC
dict the transient junction temperature and the time to thermal
o
shutdown for ambient temperatures up to +85 C and power
–t
τ1
-------
levels up to 8W. The output current limit temperature coeffi-
cient (Figure 39) precludes continuous operation above 8W.
T
≡ Pθ
1–e
1
SA
–t
----
τ
Where:
(EQ. 11B)
(EQ. 11C)
T (t) = T + Pθ + Pθ
1–e
J
A
JC
SA
(EQ. 9)
τ1 ≡ θ
(C + C
)
SA
P
S
Where:
–t
τ ≡ θ (C + C )
SA
P
S
-------
τ2
T
≡ 0.4Pθ
1–e
2
JC
P(θ + θ ) + T – T
JC
SA
A
TS
t = –τln ------------------------------------------------------------------
(EQ. 10)
Pθ
SA
Where:
(0.5C + C )0.5C
P
S
P
τ2 ≡ 0.7θ
-----------------------------------------------------------
For the TO-220, C is 0.9Ws to 1.1Ws per degree compared
JC
C
+ C
P
P
S
to about 2.6mWs per degree for the integrated circuit and C
is 0.9Ws per degree per gram for aluminum heat sinks.
S
–t
τ3
-------
Figure 8 shows the time to thermal shutdown versus power
T
≡ 0.6Pθ
1–e
(EQ. 11D)
3
JC
o
dissipation for a part in +22 C still air and at various elevated
o
ambient temperatures with a θ
flow.
of +27 C/W from forced air
Where:
SA
τ3 ≡ 0.6θ
C
JC D
For the shorter shutdown times, the θ
value is not impor-
Thermal Shutdown Hysteresis
SA
tant but the thermal capacitances are. A more accurate
equation for the transient silicon surface temperature can be
derived from the model shown in Figure 7. Due to the distrib-
uted nature of the package thermal capacitance, the second
time constant is 1.7 times larger than expected.
Figure 9 shows the HIP5600 thermal hysteresis curve with
V
= 100V , V = 5V and I = 10mA. Hysteresis is
IN
DC OUT OUT
added to the thermal shutdown circuit to prevent oscillations
as the junction temperature approaches the thermal shut-
down limit. The thermal shutdown is reset when the input
voltage is removed, goes negative (i.e. AC operation) or
when the part cools down.
2
10
10
HEATING
8.0
1
10
o
+22× C
6.0
4.0
SHUTDOWN
REGION
o
+70× C
o
0
+85× C
10
COOLING
2.0
0.0
o
+100× C
-1
10
10
98.0
105.0
113.0
120
127
135
142
o
CASE TEMPERATURE ( C)
o
+115× C
FIGURE 9. THERMAL HYSTERESIS CURVE
o
+120 ×C
-2
AC to DC Operation
0.0
2.0
4.0
6.0
8.0
10
POWER DISSIPATION (W)
Since the HIP5600 has internal high voltage diodes in series
with its input, it can be connected directly to an AC power
line. This is an improvement over typical low current supplies
constructed from a high voltage diode and voltage dropping
resistor to bias a low voltage zener. The HIP5600 provides
better line and load regulation, better efficiency and heat
FIGURE 8. TIME TO THERMAL SHUTDOWN vs POWER
DISSIPATION
69
HIP5600
transfer. The latter because the TO-220 package permits
easy heat sinking.
Referring again to Figure 10, Curve “A1” shows the input
current for a 10mA output load and curve “B1” with a 3mA
output load. The input current spike just before the negative
going zero crossing occurs while the input voltage is less
than the minimum operating voltage but is so short it has no
detrimental effect. The input current also includes the charg-
ing current for the 0.02µF input decoupling capacitor C1.
The efficiency of either supply is approximately the DC
output voltage divided by the RMS input voltage. The
resistor value, in the typical low current supply, is chosen
such that for maximum load at minimum line voltage there is
some current flowing into the zener. This resistor value
results in excess power dissipation for lighter loads or higher
line voltages.
The maximum load current cannot be greater than 1/2 of the
short circuit current because the HIP5600 only conducts over
1/2 of the line cycle. The short circuit current limit (Figure 38)
depends on the case temperature, which is a function of the
power dissipation. Figure 38 for a case temperature of
Using the circuit in Figure 3 with a 1000µF output capacitor
the HIP5600 only takes as much current from the power line
as the load requires. For light loads, the HIP5600 is even
more efficient due to it’s interaction with the output capacitor.
Immediately after the AC line goes positive, the HIP5600
tries to replace all the charge drained by the load during the
negative half cycle at a rate limited by the short circuit cur-
rent limit (see “A1” and “B1” Figure 10). Since most of this
charge is replaced before the input voltage reaches its RMS
value, the power dissipation for this charge is lower than it
would be if the charge were transferred at a uniform rate dur-
ing the cycle. When the product of the input voltage and cur-
rent is averaged over a cycle, the average power is less than
if the input current were constant. Figure 11 shows the
o
+100 C (i.e. no heat sink) indicates for AC operation the
maximum available output current is 10mA (1/2 x 20mA).
Operation from full wave rectified input will increase the
o
maximum output current to 20mA for the same +100 C case
temperature.
As a reminder, since the HIP5600 is off during the negative
half cycle, the output capacitor must be large enough to sup-
ply the maximum load current during this time with some
acceptable level of droop. Figure 10 also shows the output
ripple voltage, for both a 10mA and 3mA output loads “A2”
and “B2”, respectively.
HIP5600 efficiency as a function of load current for 80V
and 132VRMS inputs for a 15.6V output.
RMS
Do’s And Don’ts
DC Operation
120V
, 60Hz
RMS
1. Do not exceed the absolute maximum ratings.
2. The HIP5600 requires a minimum output current of 1mA.
Minimum output current includes current through RF1.
Warning: If there is less than 1mA load current, the out-
put voltage will rise. If the possibility of no load exists,
RF1 should be sized to sink 1mA under these conditions.
I
IN
20mA/DIV.
A1
B1
V
B2
REF
1.07V
1mA
RF1
= ------------------ = --------------- = 1kΩ
MIN
1mA
V
OUT
A2
100mV/DIV.
FIGURE 10. AC OPERATION
3. Do not “HOT” switch the input voltage without protecting
the input voltage from exceeding ±650V. Note: induc-
tance from supplies and wires along with the 0.02µF
decoupling capacitor can form an under damped tank cir-
cuit that could result in voltages which exceed the maxi-
mum ±650V input voltage rating. Switch arcing can
further aggravate the effects of the source inductance
creating an over voltage condition.
2ms/DIV.
25
V
= 80V
RMS
IN
23
21
19
18
16
14
12
10
Recommendation: Adequate protection means (such as
MOV, avalanche diode, surgector, etc.) may be needed
to clamp transients to within the ±650V input limit of the
HIP5600.
4. Do not operate the part with the input voltage below the
V
= 132V
RMS
IN
minimum 50V
recommended. Low voltage opera-
DC
tion: For input voltages between 0V
and +5V
noth-
DC
DC
ing happens (I
= 0), for input voltages between
there is not enough voltage for the
DC
OUT
and +35V
+5V
DC
V
= 15.6V
pass transistor to operate properly and therefore a high
frequency (2MHz) oscillation occurs. For input voltages
OUT
DC
0.0
5.0
10.0
15.0
+35V
to +50V
proper operation can occur with
DC
DC
some parts.
LOAD CURRENT (mA)
FIGURE 11. EFFICIENCY AS A FUNCTION OF LOAD CURRENT
70
HIP5600
5. Warning: the output voltage will approach the input volt-
minimized by connecting the test equipment ground as
age if the adjust pin is disconnected, resulting in perma-
nent damage to the low voltage output capacitor.
close to the circuit ground as possible.
CAUTION: Dangerous voltages may appear on exposed
metal surfaces of AC powered test equipment.
AC Operation
1. Do not exceed the absolute maximum ratings.
2. The HIP5600 requires a minimum output current of
0.5mA. Minimum output current includes current through
RF1. Warning: If there is less than 0.5mA output current,
the output voltage will rise. If the possibility of no load
exists, RF1 should be sized to sink 0.5mA under these
conditions.
Application Circuits
+ 50VDC TO 400VDC BUS
HIP5600
C1
0.02µF
V
REF
1.07V
0.5mA
±
RF1
= ------------------ = ----------------- = 2kΩ
MIN
0.5mA
+ V
OUT
3. If using a laboratory AC source (such as VARIACs or
step-up transformers, etc.) be aware that they contain
large inductances that can generate damaging high volt-
age transients when they are switched on or off.
RF1
RF2
C2
10µF
C3
10µF
Recommendations
(1) Preset VARIAC output voltage before applying power
to part.
FIGURE 12. DC/DC CONVERTER
(2) Adequate protection means (such as MOV, ava-
lanche diode, surgector, etc.) may be needed to clamp
transients to within the ±650V input limit of the HIP5600.
The HIP5600 can be configured in most common DC linear
regulator applications circuits with an input voltage between
50V
to 400V
(above the output voltage) see Figure 12.
4. Do not operate the part with the input voltage below the
DC
DC
minimum 50V
recommended. Low voltage opera-
RMS
A 10µF capacitor (C2) provides stabilization of the output
stage. Heat sinking may be required depending upon the
tion similar to DC operation (reference step 4 under
DC operation).
power dissipation. Normally, choose RF1 << V
/I .
REF ADJ
5. Warning: the output voltage will approach the input volt-
age if the adjust pin is disconnected, resulting in perma-
nent damage to the low voltage output capacitor.
(NOTE 1)
1kΩ
HIP5600
General Precautions
Instrumentation Effects
C1
0.02µF
Background: Input to output parasitic impedances exist in
most test equipment power supplies. The inter-winding
capacitance of the transformer may result in substantial cur-
rent flow (mA) from the equipment power lines to the DC
ground of the HIP5600. This “ground loop” current can result
in erroneous measurements of the circuits performance and
in some cases lead to overstress of the HIP5600.
SURGE
PROTECTION
+ V
OUT
NOTE 1. 200V
- 280V
RMS
RMS
RF1
Operation Only
C2
10µF
C3
10µF
RF2
Recommendations for Evaluation of the HIP5600
in the Lab
FIGURE 13. AC/DC CONVERTER
The HIP5600 can operate from an AC voltage between
a) The use of battery powered DVMs and scopes will elimi-
nate ground loops.
50V to 280V , see Figure 13. The combination of a
RMS
RMS
b) When connecting test equipment, locate grounds as
close to circuit ground as possible.
1kΩ (2W) input resistor and a V275LA10B MOV provides
input surge protection up to 6kV 1.2 x 50µs oscillating and
pulse waveforms as defined in IEEE/ANSI C62.41.1980.
c) Input current measurements should be made with a non-
contact current probe.
When operating from 120V , a V130LA10B MOV provides
AC
protection without the 1kΩ resistor.
If AC powered test equipment is used, then the use of an
isolated plug is recommended. The isolated plug eliminates
any voltage difference between earth ground and AC
ground. However, even though the earth ground is discon-
nected, ground loop currents can still flow through trans-
former of the test equipment. Ground loops can be
The output capacitor is larger for operation from AC than DC
because the HIP5600 only conducts current during the posi-
tive half cycle of the AC line. The efficiency is approximately
equal to V
/V (RMS), see Figure 11.
OUT IN
71
HIP5600
The HIP5600 provides an efficient and economical solution
as a start-up supply for applications operating from either AC
part, the amount of heat sinking (if any) and the ambient tem-
perature. For example; at 400V with no heat sink, it will
DC
(50V
to 280V
) or DC (50V
to 400V ).
provide 20mA for about 8s, see Figure 8.
RMS
RMS
DC DC
Power supply efficiency is improved by turning off the
HIP5600 when the SMPS is up and running. In this application
the output of the HIP5600 would be set via RF1 and RF2 to be
about 9V. The tickler winding would be adjusted to about 12V
to insure that the HIP5600 is kept off during normal operating
conditions.The input current under these conditions is approx-
HIP5600
+ 50V
TO 400V
DC
DC
BUS
±
imately equal to I
. (See Figure 27).
BIAS
The HIP5600 can supply a 450µA (±20%) constant current.
(See Figure 15). It makes use of the internal bias network.
See Figure 27 for bias current versus input voltage.
+12V
RF1
RF2
10µF
With the addition of a potentiometer and a 10µF capacitor the
HIP5600 will provide a constant current source. I
by Equation 13 in Figure 16.
is given
OUT
V
OUT
PWM
The HIP5600 can control a P-channel MOSFET or IGPT in a
self-oscillating buck regulator. The circuit shown (Figure 17)
shows the self-oscillating concept with a P-IGBT driving a
dedicated fan load. The output voltage is set by the resistor
combination of RF1, RF2, and RF3. Components C3 and
RF3 impresses the output ripple voltage across RF1 causing
the HIP5600 to oscillate and control the conduction of the
P-IGBT. The start-up protection components limit the initial
surge current in the P-IGBT by forcing this device into its
active region. The snubber circuit is recommended to reduce
the power dissipation of the P-IGBT.
FIGURE 14. START UP CIRCUIT
The HIP5600 has on chip thermal protection and output cur-
rent limiting circuitry. These features eliminate the need for
an in-line fuse and a large heat sink.
The HIP5600 can provide up to 40mA for short periods of time
to enable start up of a switch mode power supply‘s control cir-
cuit. The length of time that the HIP5600 will be on, prior to
thermal shutdown, is a function of the power dissipation in the
+50V
TO +400V
DC
DC
HIP5600
±
0.02µF
HIP5600
+20V
DC
TO +400V
DC
R1
1.21V
R1
I
OUT
I
I
=
OUT
(EQ. 13)
OUT
NOTES:
1. V
±
10µF
LOAD
Floating
OUT
2. Fixed 500µA Current Source
FIGURE 15. CONSTANT 450µA CURRENT SOURCE
FIGURE 16. ADJUSTABLE CURRENT SOURCE
72
HIP5600
START-UP PROTECTION
P-IGBT
HIP5600
SNUBBER CIRCUIT
RF1
+
DC
FAN
RF2
RF3
C3
-
FIGURE 17. HIGH CURRENT “BUCK” REGULATOR CONCEPT
Typical Performance Curves
-1
-2
-0.4
-0.6
-0.8
-1.0
-1.2
-1.4
-1.6
1mA TO 10mA
-3
1mA TO 10mA
-4
-5
1mA TO 20mA
-6
1mA TO 20mA
-7
-8
1mA TO 30mA
V
= 400V
-9
IN
DC
1mA TO 30mA
V
= 50V
IN
DC
100
-10
-40
-20
0
25
40
60
80
-40
-20
0
25
40
60
o
80
o
CASE TEMPERATURE ( C)
CASE TEMPERATURE ( C)
FIGURE 18. LOAD REGULATION vs TEMPERATURE
FIGURE 19. LOAD REGULATION VS. TEMPERATURE
90
85
o
o
V
= 400V , I = 10mA, f = 120Hz, T = +25 C
V
= 170V , I = 10mA, f = 120Hz, T = +25 C
IN
DC
L
C
IN
DC
L
C
80
75
70
65
60
55
50
45
80
70
60
50
40
30
1µF BYPASS CAPACITOR
1µF BYPASS CAPACITOR
10µF BYPASS CAPACITOR
10µF BYPASS CAPACITOR
NO BYPASS CAPACITOR
NO BYPASS CAPACITOR
0
10 20 30 40 50 60 70 80 90 100 110
OUTPUT VOLTAGE (V)
0
50
100
150
200
250
300
350
OUTPUT VOLTAGE (V)
FIGURE 20. RIPPLE REJECTION RATIO (OUTPUT VOLTAGE)
FIGURE 21. RIPPLE REJECTION RATIO (OUTPUT VOLTAGE)
73
HIP5600
Typical Performance Curves (Continued)
85
85
80
75
70
65
60
55
50
45
o
= 15V, T = +25 C
o
V
= 170V , I = 10mA, V
DC
IN
L
OUT
C
V
= 400V , I = 10mA, V
DC
= 15V, T = +25 C
OUT C
IN
L
80
75
70
65
60
55
50
45
10µF BYPASS
CAPACITOR
10µF BYPASS
CAPACITOR
1µF BYPASS CAPACITOR
NO BYPASS CAPACITOR
1µF BYPASS CAPACITOR
NO BYPASS CAPACITOR
100 1k 10k 100k
INPUT FREQUENCY (Hz)
10M
1
10
100
1k
10k
100k
1M
10M
1
10
1M
INPUT FREQUENCY (Hz)
FIGURE 22. RIPPLE REJECTION RATIO (INPUT FREQUENCY)
FIGURE 23. RIPPLE REJECTION RATIO (INPUT FREQUENCY)
85
85
o
o
V
= 400V , V
DC OUT
= 10mA, f = 120Hz, T = +25 C
C
V
= 170V , V
DC OUT
= 10mA, f = 120Hz, T = +25 C
C
IN
IN
80
75
70
65
60
55
50
80
75
70
65
60
55
50
(REFERENCE FIGURE 3)
(REFERENCE FIGURE 3)
1µF BYPASS CAPACITOR
10µF BYPASS CAPACITOR
1µF BYPASS CAPACITOR
10µF BYPASS CAPACITOR
NO BYPASS CAPACITOR
NO BYPASS CAPACITOR
0
5
10
15
20
25
30
35
0
5
10
15
20
25
30
35
OUTPUT CURRENT (mA)
OUTPUT CURRENT (mA)
FIGURE 24. RIPPLE REJECTION RATIO (OUTPUT CURRENT)
FIGURE 25. RIPPLE REJECTION RATIO (OUTPUT CURRENT)
520
I
= 0
OUT
510
500
490
480
470
460
450
440
430
420
o
T
T
= +100 C
C
100
C2 = 0.01µF, C3 = 0µF
o
= -40 C
10.0
C
C2 = 10µF, C3 = 0µF
o
T
= +25 C
C
1.0
C2 = 10µF, C3 = 10µF
0.1
50
100
200
INPUT VOLTAGE (V
300
400
10
100
1K
10K
100K
1M
)
DC
FREQUENCY (Hz)
FIGURE 26. OUTPUT IMPEDANCE
FIGURE 27. I
vs INPUT VOLTAGE
BIAS
74
HIP5600
Typical Performance Curves (Continued)
100mV/DIV
C3 = 10µF
C3 = 0µF
V
OUT
20mV/DIV
15V
C3 = 10µF
15V
400V
C3 = 0µF
100V/DIV
INPUT
VOLTAGE
5mA/DIV
10mA
5mA
V
= 15V
DC
OUT
I = 5mA
V
V
T
= 400V
IN
DC
= 15V
L
T
100V
0V
OUT
o
o
= +25 C
= +25 C
J
T = 100ms/DIV
T= 100ms/DIV
J
0mA
FIGURE 28. LINE TRANSIENT RESPONSE
FIGURE 29. LOAD TRANSIENT RESPONSE
1.21
1.20
1.19
1.18
1.17
1.16
1.15
1.14
1.13
1.12
1.11
1.10
1.25
1.20
1.15
1.10
1.05
1.00
V
= 50V
DC
IN
V
= 400V
DC
IN
1mA
1mA
5mA
5mA
10mA
10mA
30mA
20mA
40
20mA
30mA
-40
-20
0
25
60
80
-40
-20
0
25
40
60
80
100
o
o
CASE TEMPERATURE ( C)
CASE TEMPERATURE ( C)
FIGURE 30. REFERENCE VOLTAGE vs TEMPERATURE
FIGURE 31. REFERENCE VOLTAGE vs TEMPERATURE
1.20
1.18
1.20
I
= 10mA
OUT
1.19
1.18
1.17
1.16
1.15
1.14
1.13
1.12
1.11
1.10
1.09
1.08
o
1mA
T
= -40 C
C
1.16
5mA
1.14
1.12
1.10
1.08
1.06
1.04
10mA
o
T
= +25 C
C
20mA
o
T
= +100 C
C
30mA
0
100
200
INPUT VOLTAGE (V
300
400
0
100
200
300
400
)
INPUT VOLTAGE (V
)
DC
DC
FIGURE 32. REFERENCE VOLTAGE vs INPUT VOLTAGE
FIGURE 33. REFERENCE VOLTAGE vs V ; CASE TEMPERA-
IN
o
TURE OF +25 C
75
HIP5600
Typical Performance Curves (Continued)
80
80
75
70
65
60
55
50
45
V
= 400V
DC
IN
V
= 50V
DC
IN
75
70
65
60
55
50
45
1mA
10mA
5mA
20mA
1mA
20mA
30mA
30mA
-40
-20
0
25
40
60
80
-40
-20
0
25
40
60
80
100
o
CASE TEMPERATURE ( C)
o
CASE TEMPERATURE ( C)
FIGURE 34. I
ADJ
vs TEMPERATURE
FIGURE 35. I vs TEMPERATURE
ADJ
775
770
765
760
755
750
745
2000
1500
1000
500
0
V
= 100V
o
IN
= 25 C
DC
T
C
o
T
= +25 C
C
MINIMUM LOAD
CURRENT
BIAS CURRENT
o
T
= +100 C
C
I
IN
I
OUT
I
ADJ
1
2
3
4
5
50
100
200
INPUT VOLTAGE (V
300
400
V
- V
(V
)
OUT
ADJ
DC
)
DC
FIGURE 36. MINIMUM LOAD CURRENT vs V
FIGURE 37. TERMINAL CURRENTS vs FORCED V
IN
REF
55
50
45
40
35
30
o
T
= -40 C
C
o
T
= +25 C
C
o
T
= +100 C
C
25
20
50
100
150
200
250
300
350
400
INPUT-OUTPUT (V
)
DC
FIGURE 38. CURRENT LIMIT vs TEMPERATURE
76
HIP5600
Evaluation Boards
o
θ
= 22 C/W
HEAT SINK
SA
HIP5600
ADJ
V
IN
F1
V
OUT
RF1
+
-
R
S
C2
C1
MOV
C3
RF2
V
V
OUT
IN
HIP5600 EVALUATION BOARD
3.25”
FIGURE 40. EVALUATION BOARD METAL MASK (BOTTOM)
3.25”
FIGURE 39. EVALUATION BOARD (TOP)
HEAT SINK
ADJ
V
IN
V
OUT
+
-
V
V
OUT
IN
HIP5600 EVALUATION BOARD
3.25”
FIGURE 41. EVALUATION BOARD METAL MASK (TOP)
77
HIP5600
Single-In-Line Plastic Packages (SIP)
A
Z3.1B
ØP
E
3 LEAD PLASTIC SINGLE-IN-LINE PACKAGE
INCHES MILLIMETERS
MIN
F
Q
H1
SYMBOL
MAX
0.190
0.040
0.070
0.022
0.650
0.420
0.110
0.210
0.055
0.270
0.115
0.580
0.250
0.161
0.135
MIN
3.56
0.38
1.14
0.36
14.23
9.66
2.29
4.83
0.51
5.85
2.04
12.70
-
MAX
4.82
1.02
1.77
0.56
16.51
10.66
2.79
5.33
1.39
6.85
2.92
14.73
6.35
4.08
3.43
NOTES
A
b
0.140
0.015
0.045
0.014
0.560
0.380
0.090
0.190
0.020
0.230
0.080
0.500
-
-
D
-
b1
c1
D
1
1
-
L1
b1
E
-
L
b
e
2
c1
e1
F
2
-
1
2
e
e1
3
J1
H1
J1
L
-
3
-
NOTES:
L1
ØP
Q
1
1. Lead dimension and finish uncontrolled in zone L1.
0.139
0.100
3.53
2.54
-
2. Position of lead to be measured 0.250 inches (6.35mm) from bot-
tom of dimension D.
-
Rev. 1 2/95
3. Position of lead to be measured 0.100 inches (2.54mm) from bot-
tom of dimension D.
4. Controlling dimension: INCH.
78
相关型号：
©2020 ICPDF网 联系我们和版权申明