MC33341DR2 [ONSEMI]
Power Supply Battery Charger Regulation Control Circuit; 电源电池充电器调节控制电路
| 型号： | MC33341DR2 |
| 厂家： | 
ONSEMI |
| 描述： | Power Supply Battery Charger Regulation Control Circuit |
| 文件： | 总19页 (文件大小：243K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
MC33341
Power Supply Battery
Charger Regulation
Control Circuit
The MC33341 is a monolithic regulation control circuit that is
specifically designed to close the voltage and current feedback loops in
power supply and battery charger applications. This device features the
unique ability to perform source high−side, load high−side, source
low−side and load low−side current sensing, each with either an
internally fixed or externally adjustable threshold. The various current
sensing modes are accomplished by a means of selectively using the
internal differential amplifier, inverting amplifier, or a direct input path.
Positive voltage sensing is performed by an internal voltage amplifier.
The voltage amplifier threshold is internally fixed and can be externally
adjusted in all low−side current sensing applications. An active high
drive output is provided to directly interface with economical
optoisolators for isolated output power systems. This device is available
in 8−lead dual−in−line and surface mount packages.
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MARKING
DIAGRAMS
8
SOIC−8
D SUFFIX
CASE 751
33341
ALYW
G
1
1
8
PDIP−8
P SUFFIX
CASE 626
MC33341P
AWL
YYWWG
Features
• Differential Amplifier for High−Side Source and Load Current Sensing
• Inverting Amplifier for Source Return Low−Side Current Sensing
• Non−Inverting Input Path for Load Low−Side Current Sensing
• Fixed or Adjustable Current Threshold in All Current Sensing Modes
• Positive Voltage Sensing in All Current Sensing Modes
• Fixed Voltage Threshold in All Current Sensing Modes
• Adjustable Voltage Threshold in All Low−Side Current Sensing Modes
• Output Driver Directly Interfaces with Economical Optoisolators
• Operating Voltage Range of 2.3 V to 16 V
1
1
A
= Assembly Location
L, WL = Wafer Lot
Y, YY = Year
W, WW = Work Week
G or G = Pb−Free Package
(Note: Microdot may be in either location)
• Pb−Free Packages are Available
PIN CONNECTIONS
Current Sense Input B/ Voltage Sense
Drive Output
8
V
Voltage Threshold Adjust
Input
CC
Current Sense
7
6
5
Drive Output
1
2
3
4
8
7
6
5
Input A
Current Threshold
Adjust
V
CC
Differential
Amp
Current Sense Input B/
Voltage Threshold Adjust
Voltage and Current
Transconductance
Amp/Driver
Compensation
GND
1.0
Voltage Sense Input
V
1.2 V
0.2 V
(Top View)
#1.0
I
Inverting/
Noninverting Amp
ORDERING INFORMATION
See detailed ordering and shipping information in the package
Reference
dimensions section on page 17 of this data sheet.
1
2
3
4
Current Sense Input A
Current
Compensation
GND
Threshold Adjust
This device contains 114 active transistors.
Figure 1. Representative Block Diagram
© Semiconductor Components Industries, LLC, 2006
1
Publication Order Number:
August, 2006 − Rev. 4
MC33341/D
MC33341
MAXIMUM RATINGS
Rating
Symbol
Value
16
Unit
V
Power Supply Voltage (Pin 7)
V
CC
Voltage Range
V
IR
−1.0 to V
V
CC
Current Sense Input A (Pin 1)
Current Threshold Adjust (Pin 2)
Compensation (Pin 3)
Voltage Sense Input (Pin 5)
Current Sense Input B / Voltage Threshold Adjust (Pin 6)
Drive Output (Pin 8)
Drive Output Source Current (Pin 8)
I
50
mA
Source
Thermal Resistance, Junction−to−Air
P Suffix, DIP Plastic Package, Case 626
D Suffix, SO−8 Plastic Package, Case 751
R
°C/W
q
JA
100
178
Operating Junction Temperature (Note 1)
T
−25 to +150
−55 to +150
°C
°C
J
Storage Temperature
T
stg
NOTE: ESD data available upon request.
Stresses exceeding Maximum Ratings may damage the device. Maximum Ratings are stress ratings only. Functional operation above the
Recommended Operating Conditions is not implied. Extended exposure to stresses above the Recommended Operating Conditions may affect
device reliability.
1. Tested ambient temperature range for the MC33341: T = −25°C, T
= +85°C.
low
high
ELECTRICAL CHARACTERISTICS (V = 6.0 V, T = 25°C, for min/max values T is the operating junction temperature range that
CC
A
A
applies (Note 1), unless otherwise noted.)
Characteristic
Symbol
Min
Typ
Max
Unit
CURRENT SENSING (Pins 1, 2, 6)
High−Side Source and Load Sensing Pin 1 to Pin 6 (Pin 1 >1.6 V)
V
mV
th(I HS)
Internally Fixed Threshold Voltage (Pin 2 = V
)
CC
T = 25°C
187
183
−
197
−
10
207
211
−
A
T = T
to T
A
low
high
Externally Adjusted Threshold Voltage (Pin 2 = 0 V)
Externally Adjusted Threshold Voltage (Pin 2 = 200 mV)
−
180
−
Low−Side Load Sensing Pin 1 to Pin 4 (Pin 1 = 0 V to 0.8 V)
V
V
mV
mV
th(I LS+)
Internally Fixed Threshold Voltage (Pin 2 = V
)
CC
T = 25°C
194
192
−
200
−
10
206
208
−
A
T = T
to T
A
low
high
Externally Adjusted Threshold Voltage (Pin 2 = 0 V)
Externally Adjusted Threshold Voltage (Pin 2 = 200 mV)
−
180
−
Low−Side Source Return Sensing Pin 1 to 4 (Pin 1 = 0 V to −0.2 V)
th(I LS−)
Internally Fixed Threshold Voltage (Pin 2 = V
)
CC
T = 25°C
−195
−193
−
−201
−
−10
−180
−207
−209
−
A
T = T
to T
A
low
high
Externally Adjusted Threshold Voltage (Pin 2 = 0 V)
Externally Adjusted Threshold Voltage (Pin 2 = 200 mV)
−
−
Current Sense Input A (Pin 1)
Input Bias Current, High−Side Source and Load Sensing
I
−
−
−
40
10
10
−
−
−
mA
nA
kW
IB(A HS)
(Pin 2 = 0 V to V
V)
Pin 6
Input Bias Current, Low−Side Load Sensing
(Pin 2 = 0 V to 0.8 V)
I
IB(A LS+)
Input Resistance, Low−Side Source Return Sensing
(Pin 2 = −0.6 V to 0 V)
R
in(A LS−)
Current Sense Input B/Voltage Threshold Adjust (Pin 6)
Input Bias Current
I
IB(B)
High−Side Source and Load Current Sensing (Pin 6 > 2.0 V)
Voltage Threshold Adjust (Pin 6 < 1.2 V)
−
−
20
100
−
−
mA
nA
Current Sense Threshold Adjust (Pin 2)
Input Bias Current
I
−
10
−
nA
IB(I th)
Transconductance, Current Sensing Inputs to Drive Output
g
m(I)
−
6.0
−
mhos
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2
MC33341
ELECTRICAL CHARACTERISTICS (V = 6.0 V, T = 25°C, for min/max values T is the operating junction temperature range that
CC
A
A
applies (Note 1), unless otherwise noted.)
Characteristic
Symbol
Min
Typ
Max
Unit
DIFFERENTIAL AMPLIFIER DISABLE LOGIC (Pins 1, 6)
Logic Threshold Voltage Pin 1 (Pin 6 = 0 V)
V
Enabled, High−Side Source and Load Current Sensing
Disabled, Low−Side Load and Source Return Current Sensing
V
V
−
−
≥1.7
≤1.3
−
−
th(I HS)
th(I LS)
VOLTAGE SENSING (Pins 5, 6)
Positive Sensing Pin 5 to Pin 4
V
th(V)
Internally Fixed Threshold Voltage
T = 25°C
1.186
1.174
−
1.210
−
40
1.234
1.246
−
V
V
mV
V
A
T = T
to T
A
low
high
Externally Adjusted Threshold Voltage (Pin 6 = 0 V)
Externally Adjusted Threshold Voltage (Pin 6 = 1.2 V)
−
1.175
−
Voltage Sense, Input Bias Current (Pin 5)
Transconductance, Voltage Sensing Inputs to Drive Output
DRIVE OUTPUT (Pin 8)
I
−
−
10
−
−
nA
IB(V)
g
7.0
mhos
m(V)
High State Source Voltage (I
= 10 mA)
V
−
V − 0.8
CC
−
−
V
Source
OH
High State Source Current (Pin 8 = 0 V)
TOTAL DEVICE (Pin 7)
I
15
20
mA
Source
Operating Voltage Range
V
2.5 to 15
−
2.3 to 15
300
−
V
CC
Power Supply Current (V = 6.0 V)
I
600
mA
CC
CC
PIN FUNCTION DESCRIPTION
Pin
Name
Description
1
Current Sense Input A
This multi−mode current sensing input can be used for either source high−side, load high−side,
source−return low−side, or load low−side sensing. It is common to a Differential Amplifier, Inverting
Amplifier, and a Noninverting input path. Each of these sensing paths indirectly connect to the current
sense input of the Transconductance Amplifier. This input is connected to the high potential side of a
current sense resistor when used in source high−side, load high−side, or load low−side current
sensing modes. In source return low−side current sensing mode, this pin connects to the low potential
side of a current sense resistor.
2
3
Current Threshold Adjust The current sense threshold can be externally adjusted over a range of 0 V to 200 mV with respect to
Pin 4, or internally fixed at 200 mV by connecting Pin 2 to V
.
CC
Compensation
This pin is connected to a high impedance node within the transconductance amplifier and is made
available for loop compensation. It can also be used as an input to directly control the Drive Output. An
active low at this pin will force the Drive Output into a high state.
4
5
Ground
This pin is the regulation control IC ground. The control threshold voltages are with respect to this pin.
Voltage Sense Input
This is the voltage sensing input of the Transconductance Amplifier. It is normally connected to the
power supply/battery charger output through a resistor divider. The input threshold is controlled by
Pin 6.
6
Current Sense Input B /
This is a dual function input that is used for either high−side current sensing, or as a voltage threshold
Voltage Threshold Adjust adjustment for Pin 5. This input is connected to the low potential side of a current sense resistor when
used in source high−side or load high−side current sensing modes. In all low−side current sensing
modes, Pin 6 is available as a voltage threshold adjustment for Pin 5. The threshold can be externally
adjusted over a range of 0 V to 1.2 V with respect to Pin 4, or internally fixed at 1.2 V by connecting
Pin 6 to V
.
CC
7
8
V
This is the positive supply voltage for the regulation control IC. The typical operating voltage range is
2.3 V to 15 V with respect to Pin 4.
CC
Drive Output
This is a source−only output that normally connects to a linear or switching regulator control circuit.
This output is capable of 15 mA, allowing it to directly drive an optoisolator in primary side control
applications where galvanic isolation is required.
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3
MC33341
4.0
0
1.0
V
CC
= 6.0 V
V
CC
= 6.0 V
0
−1.0
−2.0
−3.0
−4.0
−8.0
−12
3
2
1
1 − Source High−Side and Load High−Side
2 − Source Return Low−Side
3 − Load Low−Side
−50
−25
0
25
50
75
100
125
−50
−25
0
25
50
75
100
125
T , AMBIENT TEMPERATURE (°C)
A
T , AMBIENT TEMPERATURE (°C)
A
Figure 3. Current Sensing
Figure 2. Voltage Sensing
Threshold Change versus Temperature
Threshold Change versus Temperature
1.6
1.4
1.2
1.0
0.8
0.6
0.4
0.2
0
0
−40
16
0
V
V
I
= 6.0 V
= 1.0 V
= 1.0 mA
CC
V
CC
14
12
10
8.0
6.0
4.0
2.0
0
2.0
4.0
6.0
8.0
10
12
14
O
V
−V
Pin 1 Pin 6
O
T = 25°C
A
−80
V
V
I
= 6.0 V
= 1.0 V
= 1.0 mA
CC
O
V
Pin 6
−120
−160
−200
−240
−280
O
Pin 1 = V
T = 25°C
A
V
CC
Pin 5
Differential Amplifier is active for
source high−side and load high−side
current sensing. Both vertical axis are
V
−V
Pin 6 Pin 5
expressed in millivolts down to V
.
CC
0
0.2
0.4
0.6
0.8
1.0
1.2
1.4
1.6
0
40
80
120
160
200
240
280
V , VOLTAGE THRESHOLD ADJUST (V)
Pin 6
V , CURRENT THRESHOLD ADJUST (V)
Pin 2
Figure 4. Closed−Loop Voltage Sensing Input
versus Voltage Threshold Adjust
Figure 5. Closed−Loop Current Sense Input B
versus Current Threshold Adjust
280
240
200
0
−40
14
12
10
8.0
6.0
4.0
2.0
0
14
12
10
8.0
6.0
4.0
2.0
0
Noninverting input path is active
for load low−side current sensing.
V
V
I
= 6.0 V
= 1.0 V
= 1.0 mA
CC
GND
O
V
V
V
= 6.0 V
= 1.0 V
O
Pin 5
CC
−80
T = 25°C
A
O
I
O
= 1.0 mA
160 T = 25°C
−120
−160
−200
−240
−260
A
120
80
40
0
V
Pin 5
V
−|V
Pin 2 Pin 1
|
V
−V
Pin 2 Pin 1
Inverting Amplifier is
active for source return
low−side current sensing.
GND
240
0
40
80
120
160
200
280
0
40
80
120
160
200
240
280
V , CURRENT THRESHOLD ADJUST (mV)
Pin 2
V , CURRENT THRESHOLD ADJUST (mV)
Pin 2
Figure 6. Closed−Loop Current Sensing Input A
versus Current Threshold Adjust
Figure 7. Closed−Loop Current Sensing Input A
versus Current Threshold Adjust
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MC33341
60
50
40
30
20
10
0
60
80
80
Phase
Low−Side Sensing
50
40
30
20
10
0
Phase
High−Side Sensing
Phase
100
120
140
160
180
100
120
140
160
180
Gain
Gain
V
V
= 6.0 V
= 1.0 V
V
= 6.0 V
CC
= 1.0 V
R = 1.0 k
Pin 3 = 1.8 nF
CC
V
O
O
R = 1.0 k
Pin 3 = 1.0 nF
T = 25°C
A
L
L
T = 25°C
A
1.0 k
1.0 k
10 k
100 k
1.0 M
10 k
100 k
1.0 M
f, FREQUENCY (Hz)
f, FREQUENCY (Hz)
Figure 9. Bode Plot
Current Sensing Inputs to Drive Output
Figure 8. Bode Plot
Voltage Sensing Inputs to Drive Output
8.0
6.0
4.0
2.0
0
8.0
6.0
4.0
2.0
0
V
V
= 6.0 V
= 1.0 V
V
= 6.0 V
CC
= 1.0 V
CC
V
O
O
T = 25°C
A
T = 25°C
A
0.1
0.2 0.3
0.5
1.0
2.0 3.0
5.0
10
0.1
0.2 0.3
0.5
1.0
2.0 3.0
5.0
10
I , DRIVE OUTPUT LOAD CURRENT (mA)
O
I , DRIVE OUTPUT LOAD CURRENT (mA)
O
Figure 10. Transconductance
Figure 11. Transconductance
Voltage Sensing Inputs to Drive Output
Current Sensing Inputs to Drive Output
0
−0.4
−0.8
−1.2
−1.6
−2.0
1.0
0.8
0.6
0.4
0.2
0
V
= 6.0 V
CC
Drive Output High State
V
CC
T = 25°C
A
I
= 0 mA
O
T = 25°C
A
Drive Output Low State
0
4.0
8.0
12
16
20
0
4.0
8.0
, SUPPLY VOLTAGE (V)
CC
12
16
I , OUTPUT LOAD CURRENT (mA)
V
L
Figure 12. Drive Output High State
Source Saturation versus Load Current
Figure 13. Supply Current
versus Supply Voltage
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MC33341
INTRODUCTION
current sensing modes, Pin 6 is available, and can be used to
lower the regulation threshold of Pin 5. This threshold can
be externally adjusted over a range of 0 V to 1.2 V with
respect to the IC ground at Pin 4.
Power supplies and battery chargers require precise
control of output voltage and current in order to prevent
catastrophic damage to the system load. Many present day
power sources contain a wide assortment of building blocks
and glue devices to perform the required sensing for proper
regulation. Typical feedback loop circuits may consist of a
voltage and current amplifier, level shifting circuitry,
summing circuitry and a reference. The MC33341 contains
all of these basic functions in a manner that is easily
adaptable to many of the various power source−load
configurations.
Current Sensing
Current sensing is accomplished by monitoring the
voltage that appears across sense resistor R level shifting
S,
it with respect to Pin 4 if required, and applying it to the
noninverting I input of the transconductance amplifier. In
sen
order to allow for maximum circuit flexibility, there are
three methods of current sensing, each with different
internal paths.
In source high−side (Figures 14 and 15) and load
high−side (Figures 18 and 19) current sensing, the
Differential Amplifier is active with a gain of 1.0. Pin 1
connects to the high potential side of current sense resistor
OPERATING DESCRIPTION
The MC33341 is an analog regulation control circuit that
is specifically designed to simultaneously close the voltage
and current feedback loops in power supply and battery
charger applications. This device can control the feedback
loop in either constant−voltage or constant−current mode
with automatic crossover. A concise description of the
integrated circuit blocks is given below. Refer to the block
diagram in Figure 14.
R while Pin 6 connects to the low side. Logic circuitry is
S
provided to disable the Differential Amplifier output
whenever low−side current sensing is required. This circuit
clamps the Differential Amplifier output high which
disconnects it from the I input of the Transconductance
sen
Amplifier. This happens if Pin 1 is less than 1.2 V or if Pin 1
is less than Pin 6.
Transconductance Amplifier
With source return low−side current sensing (Figures 16
and 17), the Inverting Amplifier is active with a gain of −1.0.
Pin 1 connects to the low potential side of current sense
A quad input transconductance amplifier is used to control
the feedback loop. This amplifier has separate voltage and
current channels, each with a sense and a threshold input.
Within a given channel, if the sense input level exceeds that
of the threshold input, the amplifier output is driven high.
The channel with the largest difference between the sense
and threshold inputs will set the output source current of the
amplifier and thus dominate control of the feedback loop.
The amplifier output appears at Pin 8 and is a source−only
type that is capable of 15 mA.
A high impedance node within the transconductance
amplifier is made available at Pin 3 for loop compensation.
This pin can sink and source up to 10 mA of current. System
stability is achieved by connecting a capacitor from Pin 3 to
ground. The Compensation Pin signal is out of phase with
respect to the Drive Output. By actively clamping Pin 3 low,
the Drive Output is forced into a high state. This, in effect,
will shutdown the power supply or battery charger, by
forcing the output voltage and current regulation threshold
down towards zero.
resistor R while Pin 4 connects to the high side. Note that
S
a negative voltage appears across R with respect to Pin 4.
S
In load low−side current sensing (Figures 20 and 21) a
Noninverting input path is active with a gain of 1.0. Pin 1
connects to the high potential side of current sense resistor
R while Pin 4 connects to the low side. The Noninverting
S
input path lies from Pin 1, through the Inverting Amplifier
input and feedback resistors R, to the cathode of the output
diode. With load low−side current sensing, Pin 1 will be
more positive than Pin 4, forcing the Inverting Amplifier
output low. This causes the diode to be reverse biased, thus
preventing the output stage of the amplifier from loading the
input signal that is flowing through the feedback resistors.
The regulation threshold in all of the current sensing
modes is internally fixed at 200 mV with Pin 2 connected to
V . Pin 2 can be used to externally adjust the threshold
CC
over a range of 0 to 200 mV with respect to the IC ground
at Pin 4.
Voltage Sensing
Reference
The voltage that appears across the load is monitored by
An internal band gap reference is used to set the 1.2 V
voltage threshold and 200 mV current threshold. The
reference is initially trimmed to a 1.0% tolerance at
the noninverting V
input of the transconductance
sen
amplifier. This voltage is resistively scaled down and
connected to Pin 5. The threshold at which voltage
regulation occurs is set by the level present at the inverting
T = 25°C and is guaranteed to be within 2.0% over an
A
ambient operating temperature range of −25° to 85°C.
V
th
input of the transconductance amplifier. This level is
controlled by Pin 6. In source high−side and load high−side
current sensing modes, Pin 6 must be connected to the low
Applications
Each of the application circuits illustrate the flexibility of
this device. The circuits shown in Figures 14 through 21
contain an optoisolator connected from the Drive Output at
potential side of current sense resistor R . Under these
S
conditions, the voltage regulation threshold is internally
fixed at 1.2 V. In source return low−side and load low−side
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6
MC33341
Pin 8 to ground. This configuration is shown for ease of
understanding and would normally be used to provide an
isolated control signal to a primary side switching regulator
controller. In non−isolated, primary or secondary side
applications, a load resistor can be placed from Pin 8 to
ground. This resistor will convert the Drive Output current
to a voltage for direct control of a regulator.
drop across R could exceed 1.6 V. Depending upon the
current sensing configuration used, this will result in
S
forward biasing of either the internal V clamp diode,
CC
Pin 6, or the device substrate, Pin 1. Under these conditions,
input series resistor R3 is required. The peak input current
should be limited to 20 mA. Excessively large values for R3
will degrade the current sensing accuracy. Figure 22 shows
In applications where excessively high peak currents are
possible from the source or load, the load induced voltage
a method of bounding the voltage drop across R without
sacrificing current sensing accuracy.
S
R
S
Source
Load
R2
R3
8
7
6
5
V
CC
V
CC
V
CC
V
CC
R1
1.2 V
Differential Amp
Disable Logic
1.2 V
0.4 V
V
sen
Transconductance
Amp
Opto
Isolator
V
V
CC
V
th
V
Differential Amp
R
I
sen
R
R
I
I
th
V
CC
R
R
Reference
0.2 V 0.4 V 1.2 V
Battery or
Resistive
Load
CC
V
CC
R
V
CC
0.2 V
Inverting Amp
1
2
3
4
Comp
Source
Return
Load
The above figure shows the MC33341 configured for source high−side current sensing allowing a common ground path between Load − and
Source Return −. The Differential Amplifier inputs, Pins 1 and 6, are used to sense the load induced voltage drop that appears across resistor
R . The internal voltage and current regulation thresholds are selected by the respective external connections of Pins 2 and 6. Resistor R3
S
is required in applications where a high peak level of reverse current is possible if the source inputs are shorted. The resistor value should
be chosen to limit the input current of the internal V clamp diode to less than 20 mA. Excessively large values for R3 will degrade the
CC
current sensing accuracy.
V
R2
R1
th(IꢀHS)
ǒ
) 1Ǔ
ǒI Ǔꢀ–ꢀ0.6
V
+ V
R
reg
th(V)
I
+
+
pkꢀ S
0.02
reg
R
S
R3 +ꢀ
0.2
R
R2
+ 1.2ꢀǒ ) 1Ǔ
R1
S
Figure 14. Source High−Side Current Sensing with
Internally Fixed Voltage and Current Thresholds
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7
MC33341
R
S
Source
Load
R2
R3
8
7
6
5
V
CC
V
CC
V
CC
V
CC
R1
1.2 V
Differential Amp
Disable Logic
1.2 V
0.4 V
V
sen
Transconductance
Amp
Opto
Isolator
V
V
CC
V
th
V
Differential Amp
R
I
sen
R
R
I
I
th
V
CC
R
R
Reference
0.2 V 0.4 V 1.2 V
Battery or
Resistive
Load
CC
V
CC
R
V
CC
0.2 V
Inverting Amp
1
2
3
4
Current
Control
Comp
Source
Return
Load
The above figure shows the MC33341 configured for source high−side current sensing with an externally adjustable current threshold.
Operation of this circuit is similar to that of Figure 14. The current regulation threshold can be adjusted over a range of 0 V to 200 mV with
respect to Pin 4.
V
R2
ǒ
R1
th(Pinꢀ2)
) 1Ǔ
ǒI Ǔꢀ–ꢀ0.6
V
+ V
R
reg
th(V)
I
+
pkꢀ S
0.02
reg
R
S
R3 +ꢀ
R2
+ 1.2ꢀǒ ) 1Ǔ
R1
Figure 15. Source High−Side Current Sensing with
Externally Adjustable Current and Internally Fixed Voltage Thresholds
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8
MC33341
Source
Load
R2
8
7
6
5
V
CC
V
CC
V
CC
V
CC
R1
1.2 V
Differential Amp
Disable Logic
1.2 V
0.4 V
V
sen
Transconductance
Amp
Opto
Isolator
V
V
CC
V
th
V
Differential Amp
R
I
sen
R
R
I
I
th
V
CC
R
R
Reference
0.2 V 0.4 V 1.2 V
Battery or
Resistive
Load
CC
V
CC
R
V
CC
0.2 V
Inverting Amp
1
2
3
4
Comp
R3
R
S
Source
Return
Load
The above figure shows the MC33341 configured for source return low−side current sensing allowing a common power path between
Source + and Load +. This configuration is especially suited for negative output applications where a common ground path, Source + to
Load +, is desired. The Inverting Amplifier inputs, Pins 1 and 4, are used to sense the load induced voltage drop that appears across resistor
R . The internal voltage and current regulation thresholds are selected by the respective external connections of Pins 2 and 6. Resistor R3
S
is required in applications where high peak levels of inrush current are possible. The resistor value should be chosen to limit the negative
substrate current to less than 20 mA. Excessively large values for R3 will degrade the current sensing accuracy.
V
R2
R1
th(IꢀLS–)
ǒ
) 1Ǔ
ǒI Ǔꢀ–ꢀ0.6
V
+ V
R
reg
th(V)
I
+
+
pkꢀ S
0.02
reg
R
S
R3 +ꢀ
–0.2
R
R2
+ 1.2ꢀǒ ) 1Ǔ
R1
S
Figure 16. Source Return Low−Side Current Sensing with
Internally Fixed Current and Voltage Thresholds
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9
MC33341
Source
Load
R2
Voltage
Control
8
7
6
5
V
CC
V
CC
V
CC
V
CC
R1
1.2 V
Differential Amp
Disable Logic
1.2 V
0.4 V
V
sen
Transconductance
Amp
Opto
Isolator
V
V
CC
V
th
V
Differential Amp
R
I
sen
R
R
I
I
th
V
CC
R
R
Reference
0.2 V 0.4 V 1.2 V
Battery or
Resistive
Load
CC
V
CC
R
V
CC
0.2 V
Inverting Amp
1
2
3
4
Current
Control
Comp
R3
R
S
Source
Return
Load
The above figure shows the MC33341 configured for source return low−side current sensing with externally adjustable voltage and current
thresholds. Operation of this circuit is similar to that of Figure 16. The respective voltage and current regulation threshold can be adjusted
over a range of 0 to 1.6 V and 0 V to 200 mV with respect to Pin 4.
V
R2
ǒ
R1
th(Pinꢀ2)ꢀ
) 1Ǔ
ǒI Ǔꢀ–ꢀ0.6
V
+ V
R
reg
th(Pinꢀ6)
I
+ –ꢀ
pkꢀ S
0.02
reg
R
S
R3 +ꢀ
Figure 17. Source Return Low−Side Current Sensing with
Externally Adjustable Current and Voltage Thresholds
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10
MC33341
Source
Load
R
S
R2
R3
8
7
6
5
V
CC
V
CC
V
CC
V
CC
R1
1.2 V
Differential Amp
Disable Logic
1.2 V
0.4 V
V
sen
Transconductance
Amp
Opto
Isolator
V
V
CC
V
th
V
Differential Amp
R
I
sen
R
R
I
I
th
V
CC
R
R
Reference
0.2 V 0.4 V 1.2 V
Battery or
Resistive
Load
CC
V
CC
R
V
CC
0.2 V
Inverting Amp
1
2
3
4
Comp
Source
Return
Load
The above figure shows the MC33341 configured for load high−side current sensing allowing common paths for both power and ground,
between the source and load. The Differential Amplifier inputs, Pins 1 and 6, are used to sense the load induced voltage drop that appears
across resistor R . The internal voltage and current regulation thresholds are selected by the respective external connections of Pins 2 and
S
6. Resistor R3 is required in applications where high peak levels of load current are possible from the battery or load bypass capacitor. The
resistor value should be chosen to limit the input current of the internal V clamp diode to less than 20 mA. Excessively large values for
CC
R3 ill degrade the current sensing accuracy.
V
R2
R1
th(IꢀHS)
ǒ
) 1Ǔ
ǒI Ǔꢀ–ꢀ0.6
V
+ V
R
reg
th(V)
I
+
+
pkꢀ S
0.02
reg
R
S
R3 +ꢀ
0.2
R
R2
+ 1.2ꢀǒ ) 1Ǔ
R1
S
Figure 18. Load High−Side Current Sensing with
Internally Fixed Current and Voltage Thresholds
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11
MC33341
Source
Load
R2
R
S
R3
8
7
6
5
V
CC
V
CC
V
CC
V
CC
R1
1.2 V
Differential Amp
Disable Logic
1.2 V
0.4 V
V
sen
Transconductance
Amp
Opto
Isolator
V
V
CC
V
th
V
Differential Amp
R
I
sen
R
R
I
I
th
V
CC
R
R
Reference
0.2 V 0.4 V 1.2 V
Battery or
Resistive
Load
CC
V
CC
R
V
CC
0.2 V
Inverting Amp
1
2
3
4
Current
Control
Comp
Source
Return
Load
The above figure shows the MC33341 configured for load high−side current sensing with an externally adjustable current threshold. Opera-
tion of this circuit is similar to that of Figure 18. The current regulation threshold can be adjusted over a range of 0 V to 200 mV with respect
to Pin 4.
V
R2
ǒ
R1
th(Pinꢀ2)
) 1Ǔ
ǒI Ǔꢀ–ꢀ0.6
V
+ V
R
reg
th(V)
I
+
pkꢀ S
0.02
reg
R
S
R3 +ꢀ
R2
+ 1.2ꢀǒ ) 1Ǔ
R1
Figure 19. Load High−Side Current Sensing with
Externally Adjustable Current and Internally Fixed Voltage Thresholds
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12
MC33341
Source
Load
R2
8
7
6
5
V
CC
V
CC
V
CC
V
CC
R1
1.2 V
Differential Amp
Disable Logic
1.2 V
0.4 V
V
sen
Transconductance
Amp
Opto
Isolator
V
V
CC
V
th
V
Differential Amp
R
I
sen
R
R
I
I
th
V
CC
R
R
Reference
0.2 V 0.4 V 1.2 V
Battery or
Resistive
Load
CC
V
CC
R
V
CC
0.2 V
Inverting Amp
1
2
3
4
R3
R
S
Comp
Source
Return
Load
The above figure shows the MC33341 configured for load low−side current sensing allowing common paths for both power and ground,
between the source and load. The Noninverting input paths, Pins 1 and 4, are used to sense the load induced voltage drop that appears
across resistor R . The internal voltage and current regulation thresholds are selected by the respective external connections of Pins 2 and
S
6. Resistor R3 is required in applications where high peak levels of load current are possible from the battery or load bypass capacitor. The
resistor value should be chosen to limit the negative substratecurrent to less than 20 mA. Excessively large values for R3 will degrade the
current sensing accuracy.
V
R2
R1
th(IꢀLS))
ǒ
) 1Ǔ
ǒI Ǔꢀ–ꢀ0.6
V
+ V
R
reg
th(V)
I
+
+
pkꢀ S
0.02
reg
R
R3 +ꢀ
S
0.2
R
R2
+ 1.2ꢀǒ ) 1Ǔ
R1
S
Figure 20. Load Low−Side Current Sensing with
Internally Fixed Current and Voltage Thresholds
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13
MC33341
Source
Load
R2
Voltage
Current
8
7
6
5
V
CC
V
CC
V
CC
V
CC
R1
1.2 V
Differential Amp
Disable Logic
1.2 V
0.4 V
V
sen
Transconductance
Amp
Opto
Isolator
V
V
CC
V
th
V
Differential Amp
R
I
sen
R
R
I
I
th
V
CC
R
R
Reference
0.2 V 0.4 V 1.2 V
Battery or
Resistive
Load
CC
V
CC
R
V
CC
0.2 V
Inverting Amp
1
2
3
4
R3
Current
Control
R
S
Comp
Source
Return
Load
The above figure shows the MC33341 configured for load low−side current sensing with an externally adjustable voltage and current
threshold. Operation of this circuit is similar to that of Figure 20. The respective voltage and current regulation threshold can be adjusted
over a range of 0 to 1.2 V and 0 V to 200 mV, with respect to Pin 4.
V
R2
ǒ
R1
th(Pinꢀ2)ꢀ
) 1Ǔ
ǒI Ǔꢀ–ꢀ0.6
V
+ V
R
reg
th(Pinꢀ6)
I
+
pkꢀ S
0.02
reg
R
S
R3 +ꢀ
Figure 21. Load Low−Side Current Sensing with
Externally Adjustable Current and Voltage Thresholds
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14
MC33341
Source
Load
R
S
8
1
7
6
5
4
Input
Short
Output
Short
MC33341
2
3
Source
Return
Load
NOTE: An excessive load induced voltage across R can occur if either the source input or load output is shorted. This voltage can
S
easily be bounded with the addition of the diodes shown without degrading the current sensing accuracy. This bounding technique
can be used in any of the MC33341 applications where high peak currents are anticipated.
Figure 22. Current Sense Resistor Bounding
Source
Load
Load
Load
Output 2
8
1
7
6
5
4
MC33341
2 3
Source
Output 1
Opto
Isolator
8
1
7
6
5
4
MC33341
2
3
Source
Return
Output Common
NOTE: Multiple outputs can be controlled by summing the error signal into a common optoisolator. The converter output with the largest
voltage or current error will dominate control of the feedback loop.
Figure 23. Multiple Output Current and Voltage Regulation
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15
MC33341
0.2
MTP2955
Input
Output
12 V to 16 V
10 V/1.0 A
82.5 k
8
7
6
5
V
CC
V
CC
V
CC
V
CC
11.1 k
1.2 V
Differential Amp
Disable Logic
1.2 V
0.4 V
V
sen
Transconductance
Amp
V
V
10
10
CC
V
th
V
Differential Amp
R
I
sen
R
R
I
I
th
V
CC
R
R
Reference
0.2 V 0.4 V 1.2 V
Variable
Resistive
Load
CC
V
CC
R
V
CC
0.2 V
Inverting Amp
1
2
3
4
0.01
3.0 k
Input
Output
Ground
Ground
Figure 24. 10 V/1.0 A Constant−Voltage Constant−Current Regulator
10
8.0
6.0
4.0
2.0
0
0
0.2
0 4
0.6
0.8
1.0
I , OUTPUT LOAD CURRENT (A)
O
Figure 24 shows the MC33341 configured as a source high−side constant−voltage constant−current regulator. The regulator is designed for
an output voltage of 10 V at 1.0 A. Figure 25 shows the regulator’s output characteristics as the load is varied. Source return low−side, load
high−side, and load low−side configurations will each exhibit a nearly identical load regulation characteristic. A heatsink is required for the
MTP2955 series pass element.
Figure 25. Output Load Regulation
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16
MC33341
200 mH
MTP2955
0.25
Input
12 V
Output
5.87 V/800 mA
1N5821
100
68 k
3.0 k
8
7
6
5
V
CC
V
CC
V
CC
V
CC
1.2 V
Differential Amp
Disable Logic
1.2 V
0.4 V
V
sen
Transconductance
Amp
V
V
100
CC
V
th
V
Differential Amp
R
I
sen
R
R
I
I
th
V
CC
R
R
Reference
0.2 V 0.4 V 1.2 V
CC
V
CC
R
V
CC
0.2 V
Inverting Amp
1
2
3
4
12 k
Input
Output
Ground
Ground
Figure 26 shows that the MC33341 can be configured as a high−side constant−current constant−voltage switch mode charger. This circuit
operates as a step down converter. With a nominal input voltage and output load current as stated above, the switching frequency is
approximately 28 kHz with and an associated conversion efficiency of 86 percent. The switching frequency will vary with changes in input
voltage and load current.
Figure 26. Constant−Current Constant−Voltage Switch Mode Charger
ORDERING INFORMATION
†
Device
MC33341D
Operating Temperature Range
Package
Shipping
SOIC−8
98 Units / Rail
98 Units / Rail
MC33341DG
SOIC−8
(Pb−Free)
MC33341DR2
SOIC−8
2500 / Tape & Reel
2500 / Tape & Reel
T = −25° to +85°C
A
MC33341DR2G
SOIC−8
(Pb−Free)
MC33341P
PDIP−8
50 Units / Rail
50 Units / Rail
MC33341PG
PDIP−8
(Pb−Free)
†For information on tape and reel specifications, including part orientation and tape sizes, please refer to our Tape and Reel Packaging
Specifications Brochure, BRD8011/D.
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17
MC33341
PACKAGE DIMENSIONS
SOIC−8 NB
D SUFFIX
PLASTIC PACKAGE
CASE 751−07
ISSUE AH
NOTES:
−X−
1. DIMENSIONING AND TOLERANCING PER
ANSI Y14.5M, 1982.
2. CONTROLLING DIMENSION: MILLIMETER.
3. DIMENSION A AND B DO NOT INCLUDE
MOLD PROTRUSION.
4. MAXIMUM MOLD PROTRUSION 0.15 (0.006)
PER SIDE.
5. DIMENSION D DOES NOT INCLUDE DAMBAR
PROTRUSION. ALLOWABLE DAMBAR
PROTRUSION SHALL BE 0.127 (0.005) TOTAL
IN EXCESS OF THE D DIMENSION AT
MAXIMUM MATERIAL CONDITION.
6. 751−01 THRU 751−06 ARE OBSOLETE. NEW
STANDARD IS 751−07.
A
8
5
4
S
M
M
B
0.25 (0.010)
Y
1
K
−Y−
G
MILLIMETERS
DIM MIN MAX
INCHES
MIN
MAX
0.197
0.157
0.069
0.020
C
N X 45
_
A
B
C
D
G
H
J
K
M
N
S
4.80
3.80
1.35
0.33
5.00 0.189
4.00 0.150
1.75 0.053
0.51 0.013
SEATING
PLANE
−Z−
1.27 BSC
0.050 BSC
0.10 (0.004)
0.10
0.19
0.40
0
0.25 0.004
0.25 0.007
1.27 0.016
0.010
0.010
0.050
8
0.020
0.244
M
J
H
D
8
0
_
_
_
_
M
S
S
0.25 (0.010)
Z
Y
X
0.25
5.80
0.50 0.010
6.20 0.228
SOLDERING FOOTPRINT*
1.52
0.060
7.0
0.275
4.0
0.155
0.6
0.024
1.270
0.050
mm
inches
ǒ
Ǔ
SCALE 6:1
*For additional information on our Pb−Free strategy and soldering
details, please download the ON Semiconductor Soldering and
Mounting Techniques Reference Manual, SOLDERRM/D.
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18
MC33341
PACKAGE DIMENSIONS
PDIP−8
P SUFFIX
PLASTIC PACKAGE
CASE 626−05
ISSUE L
NOTES:
1. DIMENSION L TO CENTER OF LEAD WHEN
FORMED PARALLEL.
8
5
2. PACKAGE CONTOUR OPTIONAL (ROUND OR
SQUARE CORNERS).
3. DIMENSIONING AND TOLERANCING PER ANSI
Y14.5M, 1982.
−B−
1
4
MILLIMETERS
INCHES
MIN
DIM MIN
MAX
10.16
6.60
4.45
0.51
1.78
MAX
0.400
0.260
0.175
0.020
0.070
A
B
C
D
F
9.40
6.10
3.94
0.38
1.02
0.370
0.240
0.155
0.015
0.040
F
−A−
NOTE 2
L
G
H
J
2.54 BSC
0.100 BSC
0.76
0.20
2.92
1.27
0.30
3.43
0.030
0.008
0.115
0.050
0.012
0.135
K
L
C
7.62 BSC
0.300 BSC
M
N
−−−
0.76
10
1.01
−−−
0.030
10
0.040
_
_
J
−T−
SEATING
PLANE
N
M
D
K
G
H
M
M
M
0.13 (0.005)
T
A
B
ON Semiconductor and
are registered trademarks of Semiconductor Components Industries, LLC (SCILLC). SCILLC reserves the right to make changes without further notice
to any products herein. SCILLC makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does SCILLC assume any liability
arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation special, consequential or incidental damages.
“Typical” parameters which may be provided in SCILLC data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All
operating parameters, including “Typicals” must be validated for each customer application by customer’s technical experts. SCILLC does not convey any license under its patent rights
nor the rights of others. SCILLC products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other applications
intended to support or sustain life, or for any other application in which the failure of the SCILLC product could create a situation where personal injury or death may occur. Should
Buyer purchase or use SCILLC products for any such unintended or unauthorized application, Buyer shall indemnify and hold SCILLC and its officers, employees, subsidiaries, affiliates,
and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees arising out of, directly or indirectly, any claim of personal injury or death
associated with such unintended or unauthorized use, even if such claim alleges that SCILLC was negligent regarding the design or manufacture of the part. SCILLC is an Equal
Opportunity/Affirmative Action Employer. This literature is subject to all applicable copyright laws and is not for resale in any manner.
PUBLICATION ORDERING INFORMATION
LITERATURE FULFILLMENT:
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USA/Canada
Europe, Middle East and Africa Technical Support:
Phone: 421 33 790 2910
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Phone: 81−3−5773−3850
ON Semiconductor Website: www.onsemi.com
Order Literature: http://www.onsemi.com/orderlit
Literature Distribution Center for ON Semiconductor
P.O. Box 5163, Denver, Colorado 80217 USA
Phone: 303−675−2175 or 800−344−3860 Toll Free USA/Canada
Fax: 303−675−2176 or 800−344−3867 Toll Free USA/Canada
Email: orderlit@onsemi.com
For additional information, please contact your local
Sales Representative
MC33341/D
相关型号：
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