MP28303EN-Z [MPS]
Switching Regulator, Current-mode, 6A, 380kHz Switching Freq-Max, PDSO8, SOIC-8;
| 型号： | MP28303EN-Z |
| 厂家： | 
MONOLITHIC POWER SYSTEMS |
| 描述： | Switching Regulator, Current-mode, 6A, 380kHz Switching Freq-Max, PDSO8, SOIC-8 开关 光电二极管 |
| 文件： | 总11页 (文件大小：400K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
TM
MP28303
3A, 28V, 340KHz Synchronous Rectified
Step-Down Converter
TM
The Future of Analog IC Technology
DESCRIPTION
FEATURES
The MP28303 is a monolithic synchronous buck
regulator. The device integrates 120mΩ
MOSFETS that provide 3A continuous load
current over a wide operating input voltage of
4.75V to 28V. Current mode control provides
fast transient response and cycle-by-cycle
current limit.
•
•
•
•
•
•
•
•
•
•
•
3A Output Current
Wide 4.75V to 28V Operating Input Range
Integrated 120mΩ Power MOSFET Switches
Output Adjustable from 0.8V to 25V
Up to 95% Efficiency
Programmable Soft-Start
Stable with Low ESR Ceramic Output Capacitors
Fixed 340KHz Frequency
Cycle-by-Cycle Over Current Protection
Input Under Voltage Lockout
Thermally Enhanced 8-Pin SOIC Package
An adjustable soft-start prevents inrush current
at turn-on. In shutdown mode, the supply
current drops to 1μA.
This device, available in an 8-pin SOIC
package, provides a very compact system
solution with minimal reliance on external
components.
APPLICATIONS
•
•
•
Distributed Power Systems
Pre-Regulator for Linear Regulators
Notebook Computers
“MPS” and “The Future of Analog IC Technology” are Trademarks of Monolithic
Power Systems, Inc.
TYPICAL APPLICATION
Efficiency vs
Load Current
C1
10nF
100
V
IN = 5V
1
2
8
7
BS
IN
SS
EN
90
80
70
60
50
VIN
4.75V-28V
MP28303
SW
6
5
3
4
COMP
C3
4.7nF
V
IN = 12V
V
IN = 24V
GND
FB
C10
470pF
V
OUT = 3.3V
VOUT
3.3V/3A
0
0.5 1.0 1.5 2.0 2.5 3.0 3.5
LOAD CURRENT (A)
MP28303_TAC01
MP28303-EC01
MP28303 Rev. 0.1
12/13/2007
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1
TM
MP28303 – 3A, 28V, 340KHz SYNCHRONOUS RECTIFIED, STEP-DOWN CONVERTER
PACKAGE REFERENCE
ABSOLUTE MAXIMUM RATINGS (1)
Supply Voltage VIN.......................–0.3V to +32V
Switch Voltage VSW................. –1V to VIN + 0.3V
Boost Voltage VBS..........VSW – 0.3V to VSW + 6V
All Other Pins.................................–0.3V to +6V
Junction Temperature...............................150°C
Lead Temperature....................................260°C
Storage Temperature .............–65°C to +150°C
Recommended Operating Conditions (2)
Input Voltage VIN............................ 4.75V to 28V
Output Voltage VOUT ........................ 0.8V to 25V
Ambient Operating Temperature ... –20°C to +85°C
TOP VIEW
BS
IN
1
2
3
4
8
7
6
5
SS
EN
SW
GND
COMP
FB
MP28303_PD01_SOIC8N
Thermal Resistance (3)
θJA
θJC
SOIC8N ..................................50...... 10... °C/W
Part Number*
Package
SOIC8N
(Exposed Pad)
Temperature
Notes:
MP28303EN
–20°C to +85°C
1) Exceeding these ratings may damage the device.
2) The device is not guaranteed to function outside of its
operating conditions.
For Tape & Reel, add suffix –Z (eg. MP28303EN–Z)
For Lead Free, add suffix –LF (eg. MP28303EN–LF–Z)
*
3) Measured on approximately 1” square of 1 oz copper.
ELECTRICAL CHARACTERISTICS
VIN = 12V, TA = +25°C, unless otherwise noted.
Parameter
Symbol Condition
Min
Typ (4)
0.3
Max
3.0
Units
μA
Shutdown Supply Current
Supply Current
VEN = 0V
VEN = 2.7V, VFB = 1.0V
1.3
1.5
mA
4.75V ≤ VIN ≤ 28V,
Feedback Voltage
VFB
0.78
0.95
0.80
0.82
1.05
V
V
COMP < 2V
Feedback Overvoltage Threshold
Error Amplifier Voltage Gain
1.0
400
820
120
120
0
V
V/V
μA/V
mΩ
mΩ
μA
AEA
Error Amplifier Transconductance
High Side Switch On Resistance
Low Side Switch On Resistance
High Side Switch Leakage Current
Upper Switch Current Limit
GEA
550
1100
10
ΔIC = ±10μA
RDS(ON)1
RDS(ON)2
VEN = 0V, VSW = 0V
5.0
6.0
A
Lower Switch Current Limit
From Drain to Source
1.25
A
COMP to Current Sense
Transconductance
GCS
5
6
A/V
Oscillation Frequency
Fosc1
Fosc2
300
340
110
90
380
1.5
KHz
KHz
%
Short Circuit Oscillation Frequency
Maximum Duty Cycle
VFB = 0V
DMAX VFB = 0.7V
Minimum On Time
220
1.3
ns
EN Shutdown Threshold Voltage
VEN Rising
1.1
V
EN Shutdown Threshold Voltage
Hysteresis
220
mV
MP28303 Rev. 0.1
12/13/2007
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TM
MP28303 – 3A, 28V, 340KHz SYNCHRONOUS RECTIFIED, STEP-DOWN CONVERTER
ELECTRICAL CHARACTERISTICS (continued)
VIN = 12V, TA = +25°C, unless otherwise noted.
Parameter
Symbol Condition
Min
Typ (4)
2.5
Max
Units
V
EN Lockout Threshold Voltage
EN Lockout Hysteresis
2.2
2.7
210
mV
Input Under Voltage Lockout
Threshold
VIN Rising
3.80
4.05
210
4.30
V
Input Under Voltage Lockout
Threshold Hysteresis
mV
Soft-Start Current
Soft-Start Period
Thermal Shutdown
VSS = 0V
6
μA
ms
°C
CSS = 0.1μF
15
160
Note:
4) Guaranteed by design, not tested.
PIN FUNCTIONS
Pin # Name Description
High-Side Gate Drive Boost Input. BS supplies the drive for the high-side N-Channel MOSFET
switch. Connect a 0.01μF or greater capacitor from SW to BS to power the high side switch.
Power Input. IN supplies the power to the IC, as well as the step-down converter switches.
Drive IN with a 4.5V to 28V power source. Bypass IN to GND with a suitably large capacitor to
eliminate noise on the input to the IC. See Input Capacitor.
1
2
BS
IN
Power Switching Output. SW is the switching node that supplies power to the output. Connect
the output LC filter from SW to the output load. Note that a capacitor is required from SW to
BS to power the high-side switch.
3
4
5
SW
GND Ground (Connect Exposed Pad to Pin 4)
Feedback Input. FB senses the output voltage to regulate that voltage. Drive FB with a
resistive voltage divider from the output voltage. The feedback reference voltage is 0.8V. See
FB
Setting the Output Voltage.
Compensation Node. COMP is used to compensate the regulation control loop. Connect a
series RC network from COMP to GND to compensate the regulation control loop. In some
cases, an additional capacitor from COMP to GND is required. See Compensation
Components.
6
COMP
Enable Input. EN is a digital input that turns the regulator on or off. Drive EN high to turn on
the regulator, drive it low to turn it off. Pull up with 100kΩ resistor for automatic startup.
Soft-start Control Input. SS controls the soft-start period. Connect a capacitor from SS to GND
to set the soft-start period. A 0.1μF capacitor sets the soft-start period to 15ms. To disable the
soft-start feature, leave SS unconnected.
7
8
EN
SS
MP28303 Rev. 0.1
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TM
MP28303 – 3A, 28V, 340KHz SYNCHRONOUS RECTIFIED, STEP-DOWN CONVERTER
TYPICAL PERFORMANCE CHARACTERISTICS
VIN = 12V, VO = 3.3V, L = 10µH, CIN = 10µF, COUT = 22µF x 2, TA = +25°C, unless otherwise noted.
Steady State Test
Rising Edge Dead Time
Falling Edge Dead Time
V
= 12V, V
OUT
= 3.3V, I
OUT
= 1A
V
= 12V, V
OUT
= 3.3V, I
OUT
= 2A
V = 12V, V
IN OUT
= 3.3V, I = 1A
OUT
IN
IN
V
IN
200mV/div.
I
L
500mA/div.
V
OUT
AC Coupled
10mV/div.
V
V
SW
SW
2V/div.
2V/div.
20ns/div.
20ns/div.
MP28303-TPC01
MP28303-TPC02
MP28303-TPC03
Load Transient Test
V
I
= 24V, V = 3.3V,
OUT
Power Up
Power Off through Enable
IN
= 0A-1A step with C = 470pF
V
= 24V, V
OUT
= 3.3V, I
OUT
= 2A
V
= 24V, V
IN OUT
= 3.3V, I = 2A
OUT
OUT
FF
IN
V
OUT
1V/div.
V
COMP
200mV/div.
V
OUT
V
100mV/div.
EN
5V/div.
V
OUT
1V/div.
I
L
1A/div.
I
L
1A/div.
I
L
V
SW
1A/div.
10V/div.
V
SW
20V/div.
4ms/div.
MP28303-TPC04
MP28303-TPC05
MP28303-TPC06
Short Circuit Entry
Short Circuit Recovery
V
= 24V, V
OUT
= 3.3V, I
OUT
= 0A
V
= 24V, V
IN OUT
= 3.3V, I = 0A
OUT
IN
V
OUT
V
OUT
1V/div.
1V/div.
V
COMP
V
COMP
1V/div.
1V/div.
I
L
I
L
2A/div.
1A/div.
MP28303-TPC07
MP28303-TPC08
MP28303 Rev. 0.1
12/13/2007
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TM
MP28303 – 3A, 28V, 340KHz SYNCHRONOUS RECTIFIED, STEP-DOWN CONVERTER
BLOCK DIAGRAM
+
CURRENT
SENSE
2
IN
OVP
AMPLIFIER
+
--
--
+
1.0V
0.3V
0.8V
5V
RAMP
CLK
OSCILLATOR
110KHz/340KHz
5
8
FB
SS
1
3
BS
--
S
Q
Q
--
+
--
+
+
SW
R
CURRENT
COMPARATOR
ERROR
AMPLIFIER
6
7
COMP
EN
4
GND
--
EN OK
OVP
IN < 4.05V
1.2V
LOCKOUT
COMPARATOR
2.5V
1.3V
+
+
IN
INTERNAL
REGULATORS
--
SHUTDOWN
COMPARATOR
MP28303_BD01
Figure 1—Functional Block Diagram
OPERATION
The converter uses internal N-Channel
MOSFET switches to step-down the input
voltage to the regulated output voltage. Since
the high side MOSFET requires a gate voltage
greater than the input voltage, a boost capacitor
connected between SW and BS is needed to
drive the high side gate. The boost capacitor is
charged from the internal 5V rail when SW is low.
FUNCTIONAL DESCRIPTION
The MP28303 is a synchronous rectified,
current-mode, step-down regulator. It regulates
input voltages from 4.75V to 28V down to an
output voltage as low as 0.8V, and supplies up
to 3A of load current.
The MP28303 uses current-mode control to
regulate the output voltage. The output voltage
is measured at FB through a resistive voltage
divider and amplified through the internal
transconductance error amplifier. The voltage at
COMP pin is compared to the switch current
measured internally to control the output
voltage.
When the MP28303 FB pin exceeds 20% of the
nominal regulation voltage of 0.8V, the over
voltage comparator is tripped; the COMP pin
and the SS pin are discharged to GND, forcing
the high-side switch off.
MP28303 Rev. 0.1
12/13/2007
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TM
MP28303 – 3A, 28V, 340KHz SYNCHRONOUS RECTIFIED, STEP-DOWN CONVERTER
APPLICATIONS INFORMATION
Choose an inductor that will not saturate under
the maximum inductor peak current. The peak
inductor current can be calculated by:
COMPONENT SELECTION
Setting the Output Voltage
The output voltage is set using a resistive
voltage divider from the output voltage to FB pin.
The voltage divider divides the output voltage
down to the feedback voltage by the ratio:
⎛
⎞
⎟
⎟
⎠
VOUT
VOUT
VIN
⎜
ILP = ILOAD
+
× 1−
⎜
⎝
2× fS ×L
Where ILOAD is the load current.
R2
VFB = VOUT
R1+ R2
Optional Schottky Diode
During the transition between high-side switch
and low-side switch, the body diode of the low-
side power MOSFET conducts the inductor
current. The forward voltage of this body diode
is high. An optional Schottky diode may be
paralleled between the SW pin and GND pin to
improve overall efficiency. Table 2 lists example
Schottky diodes and their Manufacturers.
Thus the output voltage is:
R1+ R2
VOUT = 0.8 ×
R2
Where VFB is the feedback voltage and VOUT is
the output voltage.
A typical value for R2 can be as high as 100kΩ,
but a typical value is 10kΩ. Using that value, R1
is determined by:
Table 2—Diode Selection Guide
Voltage/Current
R1 = 12.5 × (VOUT − 0.8)(kΩ)
Part Number
B130
Rating
30V, 1A
30V, 1A
Vendor
For example, for a 3.3V output voltage, R2 is
10kΩ, and R1 is 31.3kΩ.
Diodes, Inc.
Diodes, Inc.
SK13
International
Rectifier
Inductor
MBRS130
30V, 1A
The inductor is required to supply constant
current to the output load while being driven by
the switched input voltage. A larger value
inductor will result in less ripple current that will
result in lower output ripple voltage. However,
the larger value inductor will have a larger
physical size, higher series resistance, and/or
lower saturation current. A good rule for
determining the inductance to use is to allow
the peak-to-peak ripple current in the inductor
to be approximately 30% of the maximum
switch current limit. Also, make sure that the
peak inductor current is below the maximum
switch current limit. The inductance value can
be calculated by:
Input Capacitor
The input current to the step-down converter is
discontinuous, therefore a capacitor is required
to supply the AC current to the step-down
converter while maintaining the DC input
voltage. Use low ESR capacitors for the best
performance. Ceramic capacitors are preferred,
but tantalum or low-ESR electrolytic capacitors
may also suffice. Choose X5R or X7R
dielectrics when using ceramic capacitors.
Since the input capacitor absorbs the input
switching current it requires an adequate ripple
current rating. The RMS current in the input
capacitor can be estimated by:
⎛
⎜
⎝
⎞
⎟
⎟
⎠
VOUT
VOUT
⎜
L =
× 1−
⎛
⎞
⎟
VOUT
VOUT
⎜
IC1 = ILOAD
×
× 1−
fS × ΔI
V
IN
⎜
⎝
⎟
⎠
V
V
IN
IN
Where VIN is the input voltage, fS is the 340KHz
switching frequency, and ΔIL is the peak-to-
peak inductor ripple current.
The worst-case condition occurs at VIN = 2VOUT
,
where IC1 = ILOAD/2. For simplification, choose
the input capacitor whose RMS current rating
greater than half of the maximum load current.
MP28303 Rev. 0.1
12/13/2007
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TM
MP28303 – 3A, 28V, 340KHz SYNCHRONOUS RECTIFIED, STEP-DOWN CONVERTER
The input capacitor can be electrolytic, tantalum
or ceramic. When using electrolytic or tantalum
capacitors, a small, high quality ceramic
capacitor, i.e. 0.1μF, should be placed as close
to the IC as possible. When using ceramic
capacitors, make sure that they have enough
capacitance to provide sufficient charge to
prevent excessive voltage ripple at input. The
input voltage ripple caused by capacitance can
be estimated by:
Compensation Components
MP28303 employs current mode control for
easy compensation and fast transient response.
The system stability and transient response are
controlled through the COMP pin. COMP pin is
the output of the internal transconductance
error amplifier. A series capacitor-resistor
combination sets a pole-zero combination to
control the characteristics of the control system.
The DC gain of the voltage feedback loop is
given by:
⎛
⎜
⎝
⎞
⎟
⎟
⎠
ILOAD
VOUT
VIN
VOUT
VIN
⎜
ΔVIN
=
×
× 1−
VFB
fS × C1
AVDC = RLOAD × GCS × AVEA
×
VOUT
Where AVEA is the error amplifier voltage gain,
400V/V; GCS is the current sense
Where C1 is the input capacitance value.
Output Capacitor
transconductance, 6.0A/V; RLOAD is the load
resistor value.
The output capacitor is required to maintain the
DC output voltage. Ceramic, tantalum, or low
ESR electrolytic capacitors are recommended.
Low ESR capacitors are preferred to keep the
output voltage ripple low. The output voltage
ripple can be estimated by:
The system has 2 poles of importance. One is
due to the compensation capacitor (C3) and the
output resistor of error amplifier, and the other
is due to the output capacitor and the load
resistor. These poles are located at:
GEA
⎛
⎞
⎟
⎟
⎛
⎜
⎝
⎞
⎟
⎟
⎠
VOUT
VOUT
VIN
1
⎜
⎜
ΔVOUT
=
× 1−
× RESR
+
⎜
⎝
fS × L
8 × fS × C2
fP1
=
⎠
2π× C3× AVEA
Where C2 is the output capacitance value and
RESR is the equivalent series resistance (ESR)
value of the output capacitor.
1
fP2
GEA
=
2π × C2× RLOAD
Where,
is
the
error
amplifier
In the case of ceramic capacitors, the
impedance at the switching frequency is
dominated by the capacitance. The output
voltage ripple is mainly caused by the
capacitance. For simplification, the output
voltage ripple can be estimated by:
transconductance, 820μA/V, and RLOAD is the load
resistor value.
The system has one zero of importance, due to the
compensation
capacitor
(C3)
and
the
compensation resistor (R3). This zero is located at:
1
⎛
⎜
⎝
⎞
⎟
⎟
⎠
VOUT
8 × fS2 × L × C2
VOUT
fZ1
=
⎜
ΔVOUT
=
× 1−
2π × C3×R3
V
IN
The system may have another zero of
importance, if the output capacitor has a large
capacitance and/or a high ESR value. The zero,
due to the ESR and capacitance of the output
capacitor, is located at:
In the case of tantalum or electrolytic capacitors,
the ESR dominates the impedance at the
switching frequency. For simplification, the
output ripple can be approximated to:
VOUT
VOUT
VIN
⎛
⎞
ΔVOUT
=
× ⎜1−
⎟ ×RESR
1
⎜
⎟
fESR
=
fS ×L
⎝
⎠
2π × C2× RESR
The characteristics of the output capacitor also
affect the stability of the regulation system. The
MP28303 can be optimized for a wide range of
capacitance and ESR values.
MP28303 Rev. 0.1
12/13/2007
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TM
MP28303 – 3A, 28V, 340KHz SYNCHRONOUS RECTIFIED, STEP-DOWN CONVERTER
In this case (as shown in Figure 2), a third pole
set by the compensation capacitor (C6) and the
compensation resistor (R3) is used to
compensate the effect of the ESR zero on the
loop gain. This pole is located at:
Table 3—Compensation Values for Typical
Output Voltage/Capacitor Combinations
VOUT
L
C2
R3
C3
C4
1.8V 4.7μH
100μF
5.6kΩ 5.6nF None
Ceramic
1
2.5V 4.7μH - 47μF Ceramic 3.65kΩ 8.2nF None
6.8μH
fP3
=
2π× C6×R3
3.3V 6.8μH -
10μH
22μFx2
Ceramic
4.42kΩ 4.7nF None
6.98kΩ 3.3nF None
16.5kΩ 1.8nF None
8.4kΩ 2.2nF None
5.6kΩ 3.3nF None
6.8kΩ 2.2nF None
10kΩ 2.2nF None
The goal of compensation design is to shape
the converter transfer function to get a desired
loop gain. The system crossover frequency
where the feedback loop has the unity gain is
important.
5V
10μH -
15μH
22μFx2
Ceramic
12V 15μH -
22μH
22μFx2
Ceramic
1.8
4.7μH 100μF/100mΩ
Lower crossover frequencies result in slower
line and load transient responses, while higher
crossover frequencies could cause system
unstable. A good rule of thumb is to set the
crossover frequency to approximately one-tenth
of the switching frequency. Switching frequency
for the MP28303 is 340KHz, so the desired
crossover frequency is 34KHz.
SP-CAP
2.5V 4.7μH -
6.8μH
47μF
SP-CAP
3.3V 6.8μH -
10μH
47μF
SP-CAP
5V
10μH -
15μH
47μF
SP CAP
2.5V 4.7μH -
6.8μH
560μF Al.
30mΩ ESR
10kΩ
10kΩ
12nF 1.8nF
10nF 1.5nF
Table 3 lists the typical values of compensation
components for some standard output voltages
with various output capacitors and inductors. The
values of the compensation components have
been optimized for fast transient responses and
good stability at given conditions.
3.3V 6.8μH -
10μH
560μF Al
30mΩ ESR
5V
10μH -
15μH
470μF Al.
30mΩ ESR
15kΩ 8.2nF
1nF
12V 15μH -
22μH
220μF Al.
30mΩ ESR
15kΩ 10nF 390pF
MP28303 Rev. 0.1
12/13/2007
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TM
MP28303 – 3A, 28V, 340KHz SYNCHRONOUS RECTIFIED, STEP-DOWN CONVERTER
To optimize the compensation components for
conditions not listed in Table 2, the following
procedure can be used.
External Bootstrap Diode
It is recommended that an external bootstrap
diode be added when the system has a 5V
fixed input or the power supply generates a 5V
output. This helps improve the efficiency of the
regulator. The bootstrap diode can be a low
cost one such as IN4148 or BAT54.
1. Choose the compensation resistor (R3) to set
the desired crossover frequency. Determine the
R3 value by the following equation:
2π × C2× fC VOUT
5V
R3 =
×
GEA × GCS
VFB
Where fC is the desired crossover frequency,
34KHz.
BS
10nF
MP28303
2. Choose the compensation capacitor (C3) to
achieve the desired phase margin. For
applications with typical inductor values, setting
the compensation zero, fZ1, below one forth of
the crossover frequency provides sufficient
phase margin. Determine the C3 value by the
following equation:
SW
MP28303_F02
Figure 2—External Bootstrap Diode
This diode is also recommended for high duty
VOUT
cycle operation (when
>65%) and high
VIN
output voltage (VOUT>12V) applications.
4
C3 >
2π × R3 × fC
3. Determine if the second compensation
capacitor (C6) is required. It is required if the
ESR zero of the output capacitor is located at
less than half of the 340KHz switching
frequency, or the following relationship is valid:
fS
2
1
<
2π × C2× RESR
If this is the case, then add the second
compensation capacitor (C6) to set the pole fP3
at the location of the ESR zero. Determine the
C6 value by the equation:
C2 × RESR
C4 =
R3
MP28303 Rev. 0.1
12/13/2007
www.MonolithicPower.com
MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.
© 2007 MPS. All Rights Reserved.
9
TM
MP28303 – 3A, 28V, 340KHz SYNCHRONOUS RECTIFIED, STEP-DOWN CONVERTER
TYPICAL APPLICATION CIRCUITS
C5
10nF
INPUT
4.75V to 28V
1
2
IN
EN
BS
SW
OUTPUT
2.5V
3A
7
3
5
MP28303
8
SS
GND
FB
COMP
4
6
D1
B130
C3
4.7nF
(optional)
C6
(optional)
MP28303_F03
Figure 3—MP28303 with AVX 47μF, 6.3V Ceramic Output Capacitor
C5
10nF
INPUT
4.75V to 28V
2
1
IN
EN
BS
SW
OUTPUT
2.5V
3A
3
5
7
8
MP28303
SS
FB
GND
COMP
4
6
D1
C3
3.3nF
B130
(optional)
C6
(optional)
MP28303_F04
Figure 4—MP28303 with Panasonic 47μF, 6.3V Solid Polymer Output Capacitor
MP28303 Rev. 0.1
12/13/2007
www.MonolithicPower.com
MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.
© 2007 MPS. All Rights Reserved.
10
TM
MP28303 – 3A, 28V, 340KHz SYNCHRONOUS RECTIFIED, STEP-DOWN CONVERTER
B130
INPUT
6V
C5
10nF
1
2
IN
EN
BS
SW
OUTPUT
5V
3A
7
8
3
5
MP28303
SS
FB
GND
COMP
4
6
D1
B130
(optional)
C3
3.3nF
C6
(optional)
MP28303_F05
Figure 5—MP28303 Application Circuit with VIN = 6V and VO = 5V
PACKAGE INFORMATION
SOIC8N (EXPOSED PAD)
PIN 1 IDENT.
0.229(5.820)
0.244(6.200)
0.0075(0.191)
0.0098(0.249)
0.150(3.810)
0.157(4.000)
SEE DETAIL "A"
NOTE 2
0.011(0.280)
0.020(0.508)
x 45o
0.013(0.330)
0.020(0.508)
0.050(1.270)BSC
0.189(4.800)
0.197(5.004)
0o-8o
0.016(0.410)
0.050(1.270)
DETAIL "A"
0.049(1.250)
0.060(1.524)
0.053(1.350)
0.068(1.730)
SEATING PLANE
0.001(0.030)
0.004(0.101)
NOTE:
1) Control dimension is in inches. Dimension in bracket is millimeters.
2) Exposed Pad Option Only (N-Package) ; 2.55+/- 0.25mm 3.38 +/- 0.44mm.
Recommended Solder Board Area: 2.80mm x 3.82mm = 10.7mm2 (16.6mil2)
x
NOTICE: The information in this document is subject to change without notice. Please contact MPS for current specifications.
Users should warrant and guarantee that third party Intellectual Property rights are not infringed upon when integrating MPS
products into any application. MPS will not assume any legal responsibility for any said applications.
MP28303 Rev. 0.1
12/13/2007
www.MonolithicPower.com
MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.
© 2007 MPS. All Rights Reserved.
11
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