LT1011A [Linear]
Voltage Comparator; 电压比较器
| 型号： | LT1011A |
| 厂家： | 
Linear |
| 描述： | Voltage Comparator |
| 文件： | 总16页 (文件大小：209K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
LT1011/LT1011A
Voltage Comparator
U
FEATURES
DESCRIPTIO
The LT®1011 is a general purpose comparator with sig-
nificantly better input characteristics than the LM111.
Although pin compatible with the LM111, it offers four
timeslowerbiascurrent,sixtimesloweroffsetvoltageand
five times higher voltage gain. Offset voltage drift, a
previously unspecified parameter, is guaranteed at
15µV/°C. Additionally, the supply current is lower by a
factor of two with no loss in speed. The LT1011 is several
times faster than the LM111 when subjected to large
overdrive conditions. It is also fully specified for DC
parameters and response time when operating on a single
5V supply. These parametric improvements allow the
LT1011 to be used in high accuracy (≥12-bit) systems
withouttrimming. Ina12-bitA/Dapplication, forinstance,
using a 2mA DAC, the offset error introduced by the
LT1011 is less than 0.5LSB. The LT1011 retains all the
versatile features of the LM111, including single 3V to
±18V supply operation, and a floating transistor output
with 50mA source/sink capability. It can drive loads refer-
enced to ground, negative supply or positive supply, and
isspecifiedupto50VbetweenV– andthecollectoroutput.
A differential input voltage up to the full supply voltage is
allowed, even with ±18V supplies, enabling the inputs to
be clamped to the supplies with simple diode clamps.
■
Pin Compatible with LM111 Series Devices
■
Guaranteed Max 0.5mV Input Offset Voltage
■
Guaranteed Max 25nA Input Bias Current
■
■
■
■
■
■
Guaranteed Max 3nA Input Offset Current
Guaranteed Max 250ns Response Time
Guaranteed Min 200,000 Voltage Gain
50mA Output Current Source or Sink
±30V Differential Input Voltage
Fully Specified for Single 5V Operation
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APPLICATIO S
■
SAR A/D Converters
■
Voltage-to-Frequency Converters
■
Precision RC Oscillator
■
Peak Detector
■
Motor Speed Control
■
Pulse Generator
■
Relay/Lamp Driver
, LTC and LT are registered trademarks of Linear Technology Corporation.
U
TYPICAL APPLICATIO
10µs 12-Bit A/D Converter
3.9k
R1
1k
15V
LM329
7V
Response Time vs Overdrive
FULL-SCALE
TRIM
*R2 AND R4
SHOULD TC TRACK
500
450
400
350
–15V
R2*
6.49k
R3
6.98k
0.001µF
15V
20
14
15
16
17
INPUT
0V TO 10V
5V
19
6012
12-BIT
D/A CONVERTER
R4*
R5
1k
300
250
2.49k
FALLING
OUTPUT
2
3
13
18
+
7
R6
820Ω
200
150
100
50
LT1011A
RISING
OUTPUT
12 11 10
9
7
8
7
6
5
4
3
2
1
–
PARALLEL
OUTPUTS
PARALLEL
OUTPUTS
SERIAL OUTPUT
4
5
6
8
9
16 17 18 19 20 21
D
0
0.1
7475
LATCH
1
10
100
AM2504
24
OVERDRIVE (mV)
5V
SAR REGISTER
CC
S
1011 TA02
E
S
CP
12
START
CLOCK f = 1.4MHz
1011 TA01
1
LT1011/LT1011A
W W U W
ABSOLUTE MAXIMUM RATINGS
(Note 1)
Input Voltage (Note 2) ....................... Equal to Supplies
Output Short-Circuit Duration.............................. 10 sec
Operating Temperature Range (Note 3)
LT1011AC, LT1011C ............................... 0°C to 70°C
LT1011AI, LT1011I ........................... –40°C to 85°C
LT1011AM, LT1011M ..................... –55°C to 125°C
Storage Temperature Range ................. – 65°C to 150°C
Lead Temperature (Soldering, 10 sec).................. 300°C
Supply Voltage (Pin 8 to Pin 4) .............................. 36V
Output to Negative Supply (Pin 7 to Pin 4)
LT1011AC, LT1011C .......................................... 40V
LT1011AI, LT1011I ............................................ 40V
LT1011AM, LT1011M ........................................ 50V
Ground to Negative Supply (Pin 1 to Pin 4) ............ 30V
Differential Input Voltage ...................................... ±36V
Voltage at STROBE Pin (Pin 6 to Pin 8) .................... 5V
U
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PACKAGE/ORDER INFORMATION
ORDER PART
NUMBER
ORDER PART
NUMBER
TOP VIEW
LT1011ACH
LT1011ACJ8
TOP VIEW
+
LT1011CH
LT1011CJ8
V
GND
INPUT
INPUT
1
2
3
4
V+
8
7
6
5
8
LT1011AMH
LT1011MH
LT1011ACN8
LT1011CN8
LT1011CS8
LT1011AIS8
LT1011IS8
LT1011AMJ8
LT1011MJ8
OUTPUT
BALANCE/
STROBE
GND
INPUT
INPUT
1
3
7
5
OUTPUT
BALANCE/
+
–
+
–
2
6
–
STROBE
V
BALANCE
BALANCE
J8 PACKAGE
8-LEAD CERDIP
N8 PACKAGE
8-LEAD PDIP
4
–
V
S8 PACKAGE
8-LEAD PLASTIC SO
H PACKAGE
8-LEAD TO-5 METAL CAN
TJMAX = 150°C, θJA = 100°C/ W(J8)
TJMAX = 150°C, θJA = 150°C/ W, θJC = 45°C/ W
T
JMAX = 150°C, θJA = 130°C/ W(N8)
S8 PART MARKING
TJMAX = 150°C, θJA = 150°C/ W(S8)
1011
1011AI
1011I
ELECTRICAL CHARACTERISTICS
The ● denotes the specifications which apply over the full operating temperature range, otherwide specifications are at TA = 25°C.
VS = ±15V, VCM = 0V, RS = 0Ω, V1 = –15V, output at pin 7 unless otherwise noted.
LT1011AC/AI/AM
LT1011C/I/M
TYP
SYMBOL PARAMETER
CONDITIONS
MIN
TYP
MAX
MIN
MAX
UNITS
VOS
Input Offset Voltage
(Note 4)
0.3
0.5
1.0
0.6
1.5
3.0
mV
mV
●
●
●
*Input Offset Voltage
*Input Offset Current
RS ≤ 50k (Note 5)
0.75
1.50
2.0
3.0
mV
mV
IOS
IB
(Note 5)
0.2
3
5
0.2
4
6
nA
nA
Input Bias Current
*Input Bias Current
(Note 4)
(Note 5)
15
20
25
20
25
50
nA
35
50
65
80
nA
nA
●
Indicates parameters which are guaranteed for all supply voltages, including a single 5V supply. See Note 5.
*
2
LT1011/LT1011A
ELECTRICAL CHARACTERISTICS
The ● denotes the specifications which apply over the full operating temperature range, otherwide specifications are at TA = 25°C.
VS = ±15V, VCM = 0V, RS = 0Ω, V1 = –15V, output at pin 7 unless otherwise noted.
LT1011AC/AI/AM
LT1011C/I/M
TYP MAX UNITS
SYMBOL PARAMETER
CONDITIONS
MIN ≤ T ≤ TMAX
MIN
TYP
MAX
MIN
∆VOS
∆T
Input Offset Voltage Drift
(Note 6)
*Large-Signal Voltage Gain RL = 1k to 15V,
–10V ≤ VOUT ≤ 14.5V
T
●
4
15
4
25
µV/°C
V/mV
V/mV
dB
AVOL
200
50
500
300
115
200
50
500
300
115
RL = 500Ω to 5V,
0.5V ≤ VOUT ≤ 4.5V
CMRR
Common Mode
Rejection Ratio
94
90
*Input Voltage Range
(Note 9)
VS = ±15V
VS = Single 5V
●
●
–14.5
0.5
13
3
–14.5
0.5
13
3
V
V
tD
*Response Time
(Note 7)
150
250
150
250
ns
VOL
*Output Saturation Voltage, VIN = 5mV, ISINK = 8mA, TJ ≤ 100°C
0.25
0.25
0.70
0.40
0.45
1.50
0.25
0.25
0.70
0.40
0.45
1.50
V
V
V
V1 = 0
VIN = 5mV, ISINK = 8mA
VIN = 5mV, ISINK = 50mA
●
●
*Output Leakage Current
VIN = 5mV, V1 = –15V,
VOUT = 35V (25V for LT1011C/I)
0.2
10
500
0.2
10
500
nA
nA
●
*Positive Supply Current
*Negative Supply Current
3.2
1.7
4.0
2.5
3.2
1.7
4.0
2.5
mA
mA
µA
*Strobe Current
(Note 8)
Minimum to Ensure Output
Transistor is Off
500
500
Input Capacitance
6
6
pF
Indicates parameters which are guaranteed for all supply voltages, including a single 5V supply. See Note 5.
*
Note 1: Absolute Maximum Ratings are those values beyond which the
life of a device may be impaired.
Note 6: Drift is calculated by dividing the offset voltage difference
measured at min and max temperatures by the temperature difference.
Note 2: Inputs may be clamped to supplies with diodes so that
maximum input voltage actually exceeds supply voltage by one diode
drop. See Input Protection in the Applications Information section.
Note 7: Response time is measured with a 100mV step and 5mV
overdrive. The output load is a 500Ω resistor tied to 5V. Time
measurement is taken when the output crosses 1.4V.
Note 3: TJMAX = 150°C.
Note 4: Output is sinking 1.5mA with VOUT = 0V.
Note 8: Do not short the STROBE pin to ground. It should be current
driven at 3mA to 5mA for the shortest strobe time. Currents as low as
500µA will strobe the LT1011A if speed is not important. External
leakage on the STROBE pin in excess of 0.2µA when the strobe is “off”
can cause offset voltage shifts.
Note 5: These specifications apply for all supply voltages from a single
5V to ±15V, the entire input voltage range, and for both high and low
output states. The high state is ISINK ≥ 100µA, VOUT ≥ (V+ – 1V) and
the low state is ISINK ≤ 8mA, VOUT ≤ 0.8V. Therefore, this specification
defines a worst-case error band that includes effects due to common
mode signals, voltage gain and output load.
Note 9: See graph “Input Offset Voltage vs Common Mode Voltage.”
3
LT1011/LT1011A
TYPICAL PERFOR A CE CHARACTERISTICS
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Input Bias Current
Input Offset Current
Worst-Case Offset Error
100
10
1
45
40
35
30
25
20
15
10
5
0.9
0.8
0.7
0.6
0.5
0.4
0.3
0.2
0.1
0
I
FLOWS OUT
B
OF INPUTS
LM311
(FOR COMPARISON)
LT1011M
LT1011C
LT1011AM
LT1011AC
0.1
0
1k
10k
100k
1M
0
0
150
25 50 75 100 125
–50 –25
25 50 75 100 125 150
TEMPERATURE (°C)
1011 G01
–50 –25
SOURCE RESISTANCE (Ω)
TEMPERATURE (°C)
1011 G03
1011 G01
Input Characteristics*
Common Mode Limits
Transfer Function (Gain)
+
50
40
30
20
10
0
V
5
0
T
= 25°C
A
*EITHER INPUT.
–0.5
–1.0
–1.5
–2.0
0.4
REMAINING INPUT GROUNDED.
CURRENT FLOWS OUT OF INPUT.
COLLECTOR
OUTPUT
POSITIVE LIMIT
–5
V
S
= ±15V
R
L
= 1k
–10
–15
–20
–25
–30
–35
–40
REFERRED TO SUPPLIES
NEGATIVE LIMIT
0.3
0.2
EMITTER
OUTPUT
0.1
R
L
= 600Ω
–
V
–10
–50 –25
0
25 50 75 100 125 150
TEMPERATURE (°C)
1011 G05
– 0.5
–0.3
–0.1
0.1
0.3
0.5
–20 –15
–5
0
5
10 15 20
INPUT VOLTAGE (V)
DIFFERENTIAL INPUT VOLTAGE (mV)
1011 G04
1011 G06
Collector Output Saturation
Voltage
Response Time—Collector Output
Response Time—Collector Output
6
5
4
3
2
1
0
6
5
4
3
2
1
0
1.0
0.9
0.8
0.7
0.6
0.5
0.4
0.3
0.2
0.1
0
V
= ±15V
V = ±15V
S
PIN 1 GROUNDED
S
15V
5V
500Ω
V
–
+
IN
OVERDRIVE
20mV
5mV
2mV
T
= 125°C
OVERDRIVE
A
20mV
5mV
2mV
15V
5V
T
= 25°C
A
500Ω
V
–
+
–15V
IN
T
= –55°C
A
–15V
100mV
0
100mV
0
INPUT = 100mV STEP
INPUT = 100mV STEP
0
50 100 150 200 250 300 350 400 450
0
50 100 150 200 250 300 350 400 450
0
5
10 15 20 25 30 35 40 45 50
SINK CURRENT (mA)
1011 G09
TIME (ns)
TIME (ns)
1011 G07
1011 G08
4
LT1011/LT1011A
U W
TYPICAL PERFOR A CE CHARACTERISTICS
Response Time Using GND Pin
as Output
Response Time Using GND Pin
as Output
Output Limiting Characteristics*
140
120
100
80
0.7
+
V
T = 25°C
A
15
10
15
10
20mV
5mV
2mV
0.6
0.5
0.4
0.3
0.2
0.1
0
V
IN
+
POWER
V
DISSIPATION
5
5
V
V
IN
OUT
0
0
2k
–5
–10
–15
0
–5
–10
–15
0
V
OUT
–
V
2k
60
SHORT-CIRCUIT
CURRENT
5mV
2mV
20mV
–
V
40
V
= ±15V
= 25°C
S
A
–50
–100
–50
–100
T
20
V
= ±15V
= 25°C
S
A
*MEASURED 3 MINUTES
AFTER SHORT
T
0
0
2
TIME (µs)
3
4
0
2
3
4
0
5
10
OUTPUT VOLTAGE (V)
15
1
1
TIME (µs)
1011 G10
1011 G11
1011 G12
Supply Current vs Supply Voltage
Supply Current vs Temperature
Output Leakage Current
–7
–8
–9
5
4
3
2
10
10
10
6
5
4
3
V
S
= ±15V
POSITIVE SUPPLY
COLLECTOR OUTPUT “LO”
POSITIVE SUPPLY
COLLECTOR OUTPUT “LO”
V
OUT
V
GND
= 35V
= –15V
POSITIVE AND NEGATIVE SUPPLY
COLLECTOR OUTPUT “HI”
2
1
0
–10
–11
10
10
1
0
POSITIVE AND NEGATIVE SUPPLY
COLLECTOR OUTPUT “HI”
0
10
15
20
25
30
5
50
TEMPERATURE (˚C)
100 125
–50 –25
0
25
75
25
45
65
85
105
125
SUPPLY VOLTAGE (V)
TEMPERATURE (°C)
1011 G15
1011 G13
1011 G14
Output Saturation—
Ground Output
Output Saturation Voltage
Response Time vs Input Step Size
0.6
5
4
3
2
1
0
1000
800
+
I
= 8mA
V
= ±15V
S
L
REFERRED TO V
SINK
+
V
2
8
R
= 500Ω TO 5V
+
0.5
0.4
0.3
0.2
0.1
0
OVERDRIVE = 5mV
7
LT1011
T = 125°C
J
5V
3
1
R
L
–
3
500Ω
7
INPUT
4
–
V
600
OUT
V
T
= –55°C
J
T = 25°C
J
2
+
1
400
200
0
T
= 25°C
J
RISING INPUT
FALLING INPUT
T = –55°C
J
T
= 125°C
J
5
6
0
1
2
3
4
7
8
0
10
20
30
40
50
0
1
2
3
4
5
6
7
8
9
10
INPUT OVERDRIVE (mV)
OUTPUT CURRENT (mA)
INPUT STEP (V)
1011 G17
1011 G16
1011 G18
5
LT1011/LT1011A
U W
TYPICAL PERFOR A CE CHARACTERISTICS
Input Offset Voltage
vs Common Mode Voltage
Offset Pin Characteristics
2.5
2.0
0.8
0.6
0.4
0.2
0
T
= 25°C
J
1.5
CHANGE IN V FOR CURRENT
OS
1.0
UPPER
INTO PINS 5 OR 6
COMMON MODE
+
0.5
LIMIT = V – (1.5V)
0
VOLTAGE ON PINS 5 AND 6
–0.5
–1.0
–1.5
–2.0
–2.5
+
WITH RESPECT TO V
–150mV
–100mV
–50mV
–
V
(OR GND WITH
SINGLE SUPPLY)
0
–
+
25
150
50 75 100 125
V
0.1 0.2 0.3 0.4 0.5 0.6 0.7
COMMON MODE VOLTAGE (V)
V
–50 –25
0
TEMPERATURE (°C)
1011 G19
1011 G20
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APPLICATIONS INFORMATION
Preventing Oscillation Problems
BALANCE pins, which are nearly as sensitive as the
inputs.
Oscillation problems in comparators are nearly always
caused by stray capacitance between the output and
inputs or between the output and other sensitive pins on
the comparator. This is especially true with high gain
bandwidth comparators like the LT1011, which are
designed for fast switching with millivolt input signals.
The gain bandwidth product of the LT1011 is over 10GHz.
Oscillation problems tend to occur at frequencies around
5MHz, where the LT1011 has a gain of ≈2000. This
implies that attenuation of output signals must be at
least 2000:1 at 5MHz as measured at the inputs. If the
source impedance is 1kΩ, the effective stray capaci-
tance between output and input must have a reactance
of more than (2000)(1kΩ) = 2MΩ, or less than 0.02pF.
The actual interlead capacitance between input and out-
put pins on the LT1011 is less than 0.002pF when cut to
printed circuit mount length. Additional stray capaci-
tance due to printed circuit traces must be minimized by
routing the output trace directly away from input lines
and, if possible, running ground traces next to input
traces to provide shielding. Additional steps to ensure
oscillation-free operation are:
2. Bypass the negative supply (Pin 4) with a 0.1µF
ceramic capacitor close to the comparator. 0.1µF can
also be used for the positive supply (Pin 8) if the pull-
up load is tied to a separate supply. When the pull-up
load is tied directly to Pin 8, use a 2µF solid tantalum
bypass capacitor.
3. Bypass any slow moving or DC input with a capacitor
(≥0.01µF) close to the comparator to reduce high
frequency source impedance.
4. Keep resistive source impedance as low as possible. If
a resistor is added in series with one input to balance
source impedances for DC accuracy, bypass it with a
capacitor. The low input bias current of the LT1011
usually eliminates any need for source resistance bal-
ancing. A 5kΩ imbalance, for instance, will create only
0.25mV DC offset.
5. Use hysteresis. This consists of shifting the input
offset voltage of the comparator when the output
changes state. Hysteresis forces the comparator to
move quickly through its linear region, eliminating
oscillations by “overdriving” the comparator under all
input conditions. Hysteresis may be either AC or DC.
AC techniques do not shift the apparent offset voltage
1. Bypass the STROBE/BALANCE pins with a 0.01µF
capacitor connected from Pin 5 to Pin 6. This elimi-
nates stray capacitive feedback from the output to the
6
LT1011/LT1011A
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APPLICATIONS INFORMATION
8
7
6
5
C8 TO C6 = 0.003µF
of the comparator, but require a minimum input signal
slew rate to be effective. DC hysteresis works for all
input slew rates, but creates a shift in offset voltage
dependent on the previous condition of the input sig-
nal. The circuit shown in Figure 1 is an excellent
compromise between AC and DC hysteresis.
4
3
2
1
OUTPUT “LO” TO “HI”
15V
0
OUTPUT “HI” TO “LO”
(5kHz)
+
–1
–2
2µF
(50kHz)
10
C1
R
TANT
L
R2
15M
0.003µF
8
1
100
1000
–
+
3
2
6
TIME/FREQUENCY (µs)
5
7
1011 F02
OUTPUT
INPUTS
LT1011
1
Figure 2. Input Offset Voltage vs Time to Last Transition
4
–15V
0.1µF
error is created by the AC hysteresis. The high
frequency error can be reduced by reducing CH, but
lower values may not provide clean switching with
very low slew rate input signals.
1011 F01
Figure 1. Comparator with Hysteresis
This circuit is especially useful for general purpose
comparator applications because it does not force any
signals directly back onto the input signal source.
Instead, it takes advantage of the unique properties of
the BALANCE pins to provide extremely fast, clean
output switching even with low frequency input sig-
nals in the millivolt range. The 0.003µF capacitor from
Pin 6 to Pin 8 generates AC hysteresis because the
voltage on the BALANCE pins shifts slightly, depend-
ing on the state of the output. Both pins move about
4mV. If one pin (6) is bypassed, AC hysteresis is
created. It is only a few millivolts referred to the in-
puts, but is sufficient to switch the output at nearly the
maximum speed of which the comparator is capable.
To prevent problems from low values of input slew
rate, a slight amount of DC hysteresis is also used. The
sensitivity of the BALANCE pins to current is about
0.5mV input referred offset for each microampere of
BALANCE pin current. The 15M resistor tied from
OUTPUT to Pin 5 generates 0.5mV DC hysteresis. The
combination of AC and DC hysteresis creates clean
oscillation-free switching with very small input errors.
Figure 2 plots input referred error versus switching
frequency for the circuit as shown.
Input Protection
The inputs to the LT1011 are particularly suited to general
purpose comparator applications because large differen-
tial and/or common mode voltages can be tolerated with-
out damage to the comparator. Either or both inputs can
be raised 40V above the negative supply, independent of
thepositivesupplyvoltage.Internalforwardbiaseddiodes
will conduct when the inputs are taken below the negative
supply. In this condition, input current must be limited to
1mA. If very large (fault) input voltages must be accom-
modated, series resistors and clamp diodes should be
used (see Figure 3).
+
V
R3*
D1
D3
D2
R1**
R2**
300Ω
3
2
8
LT1011
4
–
+
R4*
300Ω
INPUTS
D4
D1 TO D4: 1N4148
*MAY BE ELIMINATED FOR I
**SELECT ACCORDING TO ALLOWABLE
FAULT CURRENT AND POWER DISSIPATION
–
V
≤ 1mA
FAULT
1011 F03
Note that at low frequencies, the error is simply the DC
hysteresis, while at high frequencies, an additional
Figure 3. Limiting Fault Input Currents
7
LT1011/LT1011A
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APPLICATIONS INFORMATION
15V
8
5V
The input resistors should limit fault current to a reason-
able value (0.1mA to 20mA). Power dissipation in the
resistors must be considered for continuous faults, espe-
cially when the LT1011 supplies are off. One final caution:
lightlyloadedsuppliesmaybeforcedtohighervoltagesby
large fault currents flowing through D1-D4.
R
L
–
+
7
LT1011
OUTPUT
1
6
4
TTL OR
CMOS DRIVE
(5V SUPPLY)
–15
R3 and R4 limit input current to the LT1011 to less than
1mA when the input signals are held below V–. They may
be eliminated if R1 and R2 are large enough to limit fault
current to less than 1mA.
3k
1011 F04
Figure 4. Typical Strobe Circuit
Input Slew Rate Limitations
The response time of a comparator is typically measured
with a 100mV step and a 5mV to 10mV overdrive. Unfor-
tunately, thisdoesnotsimulatemanyrealworldsituations
where the step size is typically much larger and overdrive
can be significantly less. In the case of the LT1011, step
size is important because the slew rate of internal nodes
will limit response time for input step sizes larger than 1V.
At5Vstepsize,forinstance,responsetimeincreasesfrom
150ns to 360ns. See the curve “Response Time vs Input
Step Size for more detail.
level inputs. A 1pF capacitor between the output and Pin 5
will greatly reduce oscillation problems without reducing
strobe speed.
DC hysteresis can also be added by placing a resistor from
output to Pin 5. See step 5 under “Preventing Oscillation
Problems.”
Thepin(6)usedforstrobingisalsooneoftheoffsetadjust
pins.CurrentflowintooroutofPin6mustbekeptverylow
(<0.2µA)whennotstrobingtopreventinputoffsetvoltage
shifts.
If response time is critical and large input signals are
expected, clamp diodes across the inputs are recom-
mended. The slew rate limitation can also affect perfor-
mance when differential input voltage is low, but both
inputs must slew quickly. Maximum suggested common
mode slew rate is 10V/µs.
Output Transistor
The LT1011 output transistor is truly floating in the sense
that no current flows into or out of either the collector or
emitter when the transistor is in the “off” state. The
equivalent circuit is shown in Figure 5.
Strobing
+
V
The LT1011 can be strobed by pulling current out of the
STROBE pin. The output transistor is forced to an “off”
state, giving a “hi” output at the collector (Pin 7). Currents
as low as 250µA will cause strobing, but at low strobe
currents, strobe delay will be 200ns to 300ns. If strobe
current is increased to 3mA, strobe delay drops to about
60ns.ThevoltageattheSTROBEpinisabout150mVbelow
V+ at zero strobe current and about 2V below V+ for 3mA
strobe current. Do not ground the STROBE pin. It must be
current driven. Figure 4 shows a typical strobe circuit.
I
1
0.5mA
D1
D2
COLLECTOR
(OUTPUT)
Q1
R1
170Ω
OUTPUT
TRANSISTOR
Q2
–
V
R2
470Ω
EMITTER
(GND PIN) 1011 F05
Note that there is no bypass capacitor between Pins 5 and
6. This maximizes strobe speed, but leaves the compara-
tor more sensitive to oscillation problems for slow, low
Figure 5. Output Transistor Circuitry
8
LT1011/LT1011A
U
W U U
APPLICATIONS INFORMATION
Inthe“off”state,I1 isswitchedoffandbothQ1andQ2turn
off. The collector of Q2 can be now held at any voltage
above V– without conducting current, including voltages
above the positive supply level. Maximum voltage above
V– is50VfortheLT1011Mand40VfortheLT1011C/I. The
emitter can be held at any voltage between V+ and V– as
long as it is negative with respect to the collector.
designations must be reversed. When the collector is tied
to V+, the voltage at the emitter in the “on” state is about
2V below V+ (see curves).
Input Signal Range
The common mode input voltage range of the LT1011 is
about 300mV above the negative supply and 1.5V below
the positive supply, independent of the actual supply
voltages (see curve in the Typical Performance Character-
istics). This is the voltage range over which the output will
respond correctly when the common mode voltage is
applied to one input and a higher or lower signal is applied
to the remaining input. If one input is inside the common
mode range and one is outside, the output will be correct.
If the inputs are outside the common mode range in
opposite directions, the output will still be correct. If both
inputs are outside the common mode range in the same
direction, the output will not respond to the differential
input;itwillremainunconditionallyhigh(collectoroutput)
except at –40°C where it is undefined.
In the “on” state, I1 is connected, turning on Q1 and Q2.
Diodes D1 and D2 prevent deep saturation of Q2 to
improve speed and also limit the drive current of Q1. The
R1/R2 divider sets the saturation voltage of Q2 and pro-
vides turn-off drive. Either the collector or emitter pin can
be held at a voltage between V+ and V–. This allows the
remaining pin to drive the load. In typical applications, the
emitter is connected to V– or ground and the collector
drives a load tied to V+ or a separate positive supply.
When the emitter is used as the output, the collector is
typically tied to V+ and the load is connected to ground or
V–. Note that the emitter output is phase reversed with
respecttothecollectoroutputsothatthe“+”and“–”input
U
TYPICAL APPLICATIONS
Offset Balancing
Driving Load Referenced
to Positive Supply
Driving Load Referenced
to Negative Supply
R2
3k
+
+
++
V
V
V
V
R1
3
2
2
3
8
8
+
R
–
+
LOAD
–
+
20k
V
7
5
7
LT1011
INPUTS*
LT1011
2
3
6
1
1
+
–
8
4
7
R
LT1011
LOAD
4
V
V
OR
GROUND
1011 TA03
V
1011 TA06
++
+
V
CAN BE GREATER OR LESS THAN V
*INPUT POLARITY IS REVERSED
WHEN USING PIN 1 AS OUTPUT
1011 TA05
9
LT1011/LT1011A
U
TYPICAL APPLICATIONS
Strobing
Driving Ground Referred Load
Window Detector
+
++**
+
V
V
V
2
+
2
3
R
HIGH
7
L
2
3
+
–
8
LT1011
LIMIT
–
+
7
7
3
7
LT1011
–
INPUTS*
LT1011
6
OUTPUT HIGH
1
1
INSIDE “WINDOW”
AND LOW ABOVE
HIGH LIMIT OR
TTL
STROBE
L1
4
–
V
IN
BELOW LOW LIMIT
2
3
1k
V
1011 TA07
+
–
*INPUT POLARITY IS REVERSED
1011 TA04
LT1011
WHEN USING PIN 1 AS OUTPUT
LOW
LIMIT
++
–
++
NOTE: DO NOT GROUND STROBE PIN
**V MAY BE ANY VOLTAGE ABOVE V .
1
PIN 1 SWINGS TO WITHIN ≈2V OF V
1011 TA08
Crystal Oscillator
Using Clamp Diodes to Improve Frequency Response*
CURRENT MODE
5V
2
3
10k
INPUT
+
–
(DAC, ETC)
7
LT1011
OUTPUT
D1
D2
1k
50k
2
3
8
+
–
VOLTAGE
INPUT
7
85kHz
100pF
LT1011
OUT
4
R1
GROUND OR
LOW IMPEDANCE
REFERENCE
1
10k
*SEE CURVE, “RESPONSE TIME vs INPUT STEP SIZE”
1011 TA09
10k
1011 TA10
Noise Immune 60Hz Line Sync**
High Efficiency** Motor Speed Controller
15V
5V
+
R3
1k
C1
50µF
R2
75k
R1
1k
Q1
2V
TO
25V
RMS
2N6667
5V
R1*
RMS
330k
3
2
60Hz
INPUT
8
1N4002
–
+
7
MOTOR-TACH
GLOBE 397A120-2
OUTPUT
60Hz
C1
0.22µF
LT1011
1
R2
R3*
10k
470Ω
R4
4
MOTOR TACH
27k
R6
27k
15V
8
R6
2k
R5
1011 TA11
5V
100k
2
3
R5
10k
+
–
*INCREASE R1 FOR LARGER INPUT VOLTAGES
7
C2*
C3
0.1µF
R7
1k
**LT1011 SELF OSCILLATES AT ≈60Hz CAUSING
LT1011
0.1µF
IT TO “LOCK” ONTO INCOMING LINE SIGNAL
1
1011 TA12
R4
1k
4
*R3/C2 DETERMINES OSCILLATION
FREQUENCY OF CONTROLLER
**Q1 OPERATES IN SWITCH MODE
– 5V TO
–15V
0V TO 10V
INPUT
10
LT1011/LT1011A
U
TYPICAL APPLICATIONS
Combining Offset Adjust and Strobe
Combining Offset Adjustment and Hystersis
+
V
+
V
5k
R *
10k
2R **
H
H
*HYSTERESIS IS ≈0.45mV/µA OF
CURRENT CHANGE IN R
20k
H
20k
5
6
**
THIS RESISTOR CAUSES HYSTERESIS
R
TTL OR CMOS
5V
L
–
–
+
TO BE CENTERED AROUND V
OS
5
6
7
1011 TA15
LT1011
LT1011
1k
+
1
1011 TA13
Direct Strobe Drive When CMOS* Logic
Uses Same V+ Supply as LT1011
Low Drift R/C Oscillator†
+
V
**
8
15V
15V
–
74HC04
×6
6
2
3
8
1k
LT1011
+
C1
0.015µF
+
1011 TA14
7
BUFFERED
OUTPUT
LT1011
4
*NOT APPLICABLE FOR TTL LOGIC
–
1
Positive Peak Detector
15V
10k*
10k*
15V
2k
3
2
8
*1% METAL FILM
10k*
INPUT
**TRW TYPE MTR-5/120ppm/°C, 25k ≤ R ≤ 200k
S
7
C1: 0.015µF = POLYSTYRENE, –120ppm/°C,
±30ppm WESCO TYPE 32-P
NOTE: COMPARATOR CONTRIBUTES ≤10ppm/°C DRIFT
LT1011
1011 TA16
2
1
+
6
FOR FREQUENCIES BELOW 10kHz
OUTPUT
LT1008
4
10k
3
†
LOW DRIFT AND ACCURATE FREQUENCY ARE
OBTAINED BECAUSE THIS CONFIGURATION
REJECTS EFFECTS DUE TO INPUT OFFSET
VOLTAGE AND BIAS CURRENT OF THE
COMPARATOR
–
8
1M**
+
100pF
C1*
2µF
1011 TA17
–15V
*MYLAR
**SELECT FOR REQUIRED RESET TIME CONSTANT
Negative Peak Detector
15V
2
–
+
1M**
3
6
8
OUTPUT
–
LT1008
8
10k
7
3
LT1011
4
2k
2
1
+
100pF
INPUT
+
C1*
2µF
1011 TA18
*MYLAR
**SELECT FOR REQUIRED RESET TIME CONSTANT
–15V
11
LT1011/LT1011A
U
TYPICAL APPLICATIONS
4-Digit (10,000 Count) A/D Converter
15V
INPUT
0V TO 10V
15V
ZERO
TRIM
R1
1k
C4
R5
4.7k
5V
0.01µF
R2
18k
8
C5
0.01µF
R6
2
1
+
4.7K
6
1
7
LT1011
2
OUTPUT = 1 COUNT
PER mV, f = 1MHz
3
3
5
CLOCK
1MHz
LF398
4
–
6
R7
5V
4
7
22Ω
D1
D2
–15V
R3
8
3.9k
15V
–15V
C1*
0.1µF
C2**
15pF
C3
0.1µF
R11
6.8K
R4
5.6k
R8
3k
R10
D3
D4
1k
15V
R9
3.65k
FULL-SCALE
TRIM
R12
6.8k
2N3904
C6
50pF
LM329
ALL DIODES: 1N4148
*POLYSTYRENE
**NPO
1011 TA19
START
≥12ms
Capacitance to Pulse Width Converter
T
T
≥ [C
MAX
≥ 10 • C
(pF)][1µs/pF]
MAX
H
L
• (1µs/pF)
D1
TTL OR CMOS
(OPERATING
ON 5V)
GAIN ADJ
5V
R2
100k
R1
5k
R1 + R4
R1
*PW = (R2 + R3)(C)
, INPUT CAPACITANCE OF
(
)
R3
86.6k
8
0.01µF
R5
4.7k
LT1011 IS ≈6pF. THIS IS AN OFFSET TERM.
2
3
+
–
+
6
1
**TYPICAL 2 SECTIONS OF 365pF VARIABLE
CAPACITOR WHEN USED AS SHAFT ANGLE
INDICATION
†
7
OUTPUT
1µs/pF
10µF
LT1011
4
†
THESE COMPONENTS MAY BE ELIMINATED IF
NEGATIVE SUPPLY IS AVAILABLE (–1V TO –15V)
C**
†
D3
†
†
10µF
D2
+
1011 TA20
12
LT1011/LT1011A
U
TYPICAL APPLICATIONS
Fast Settling* Filter
100pF
1M
15V
7
2
3
1M
6
OUTPUT
LT1008C
4.7k
8
V
IN
1
4
4.7k
1µF
–15V 15V
4
OFM-1A**
1.5k
–15V 100pF
0.1µF
100k
2
3
8
–
7
1
LT1011
5
+
6
15V
15V
5k
THRESHOLD
5k
6
+
5
7
1
LT1011
–
8
4
10k
–15V 15V
1011 TA21
100kHz Precision Rectifier
0.033µF
100Ω
5V
5V
5V
5V
1k
2
8
AC INPUT
+
12k
74C04
5k
ZERO
CROSS
TRIM
820Ω
7
LT1011
HP5082-2800
×4
3
–
1
–5V
RECTIFIED
OUTPUT
4
5V
–5V
1k
820Ω
74C04
–5V
12k
–5V
1011 TA23
13
LT1011/LT1011A
W
W
SCHE ATIC DIAGRA
+
OFFSET
5
OFFSET/STROBE
6
V
8
R8
800Ω
R9
800Ω
Q6
Q10
R1
1.3k
R2
1.3k
R4
300Ω
R3
300Ω
R23
4k
R27
3k
R5
160Ω
Q11
Q5
Q31
Q12
R10
4k
R6
3.2k
R7
3.2k
Q13
D1 D2
Q30
R11
170Ω
INPUT
(+)
Q8
Q7
D4
OUTPUT
7
D6
Q29
Q14
2
Q3
Q20
R22
200Ω
Q1
Q15
Q9 Q19
Q28
R12
470Ω
INPUT
(–)
D5
Q4
D7
Q27
R16
800Ω
3
Q2
Q24
Q16
R17
200Ω
R24
400Ω
R13
4Ω
Q26
Q23
Q21
Q25
R15
700Ω
R20
940Ω
1
Q22
Q18
Q17
GND
R25
1.6k
R26
1.6k
R19
500Ω
R18
275Ω
R21
960Ω
R14
4.8k
D3
4
1011 SD
–
V
U
PACKAGE DESCRIPTION
Dimensions in inches (millimeters) unless otherwise noted.
H Package
8-Lead TO-5 Metal Can (0.230 PCD)
(LTC DWG # 05-08-1321)
0.335 – 0.370
(8.509 – 9.398)
DIA
0.027 – 0.045
(0.686 – 1.143)
0.305 – 0.335
(7.747 – 8.509)
0.040
45°TYP
PIN 1
0.028 – 0.034
(0.711 – 0.864)
0.050
(1.270)
MAX
(1.016)
MAX
0.165 – 0.185
(4.191 – 4.699)
0.230
(5.842)
REFERENCE
PLANE
SEATING
PLANE
TYP
GAUGE
PLANE
0.500 – 0.750
(12.700 – 19.050)
0.010 – 0.045*
(0.254 – 1.143)
0.016 – 0.021**
(0.406 – 0.533)
H8 (TO-5) 0.230 PCD 1197
0.110 – 0.160
(2.794 – 4.064)
INSULATING
STANDOFF
*LEAD DIAMETER IS UNCONTROLLED BETWEEN THE REFERENCE PLANE
AND 0.045" BELOW THE REFERENCE PLANE
0.016 – 0.024
**FOR SOLDER DIP LEAD FINISH, LEAD DIAMETER IS
(0.406 – 0.610)
14
LT1011/LT1011A
U
PACKAGE DESCRIPTION
Dimensions in inches (millimeters) unless otherwise noted.
J8 Package
8-Lead CERDIP (Narrow 0.300, Hermetic)
(LTC DWG # 05-08-1110)
CORNER LEADS OPTION
(4 PLCS)
0.023 – 0.045
(0.584 – 1.143)
HALF LEAD
OPTION
0.405
(10.287)
MAX
0.005
(0.127)
MIN
0.200
(5.080)
MAX
0.045 – 0.068
0.300 BSC
(1.143 – 1.727)
FULL LEAD
OPTION
(0.762 BSC)
6
5
4
8
7
0.015 – 0.060
(0.381 – 1.524)
0.025
(0.635)
RAD TYP
0.220 – 0.310
(5.588 – 7.874)
0.008 – 0.018
0° – 15°
(0.203 – 0.457)
1
2
3
J8 1197
0.045 – 0.068
(1.143 – 1.727)
0.125
3.175
MIN
0.100 ± 0.010
0.014 – 0.026
NOTE: LEAD DIMENSIONS APPLY TO SOLDER DIP/PLATE
OR TIN PLATE LEADS
(2.540 ± 0.254)
(0.360 – 0.660)
N8 Package
8-Lead PDIP (Narrow 0.300)
(LTC DWG # 05-08-1510)
0.400*
(10.160)
MAX
0.130 ± 0.005
(3.302 ± 0.127)
0.300 – 0.325
(7.620 – 8.255)
0.045 – 0.065
(1.143 – 1.651)
8
1
7
6
5
4
0.065
(1.651)
TYP
0.255 ± 0.015*
(6.477 ± 0.381)
0.009 – 0.015
(0.229 – 0.381)
0.125
0.020
(0.508)
MIN
(3.175)
MIN
+0.035
–0.015
2
3
0.325
N8 1197
0.100 ± 0.010
(2.540 ± 0.254)
0.018 ± 0.003
+0.889
8.255
(
)
(0.457 ± 0.076)
–0.381
*THESE DIMENSIONS DO NOT INCLUDE MOLD FLASH OR PROTRUSIONS.
MOLD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.010 INCH (0.254mm)
S8 Package
8-Lead Plastic Small Outline (Narrow 0.150)
(LTC DWG # 05-08-1610)
0.189 – 0.197*
(4.801 – 5.004)
0.010 – 0.020
(0.254 – 0.508)
7
5
8
6
× 45°
0.053 – 0.069
(1.346 – 1.752)
0.004 – 0.010
(0.101 – 0.254)
0.008 – 0.010
(0.203 – 0.254)
0°– 8° TYP
0.150 – 0.157**
(3.810 – 3.988)
0.228 – 0.244
(5.791 – 6.197)
0.016 – 0.050
0.406 – 1.270
0.050
(1.270)
TYP
0.014 – 0.019
(0.355 – 0.483)
*DIMENSION DOES NOT INCLUDE MOLD FLASH. MOLD FLASH
SHALL NOT EXCEED 0.006" (0.152mm) PER SIDE
SO8 0996
**DIMENSION DOES NOT INCLUDE INTERLEAD FLASH. INTERLEAD
FLASH SHALL NOT EXCEED 0.010" (0.254mm) PER SIDE
1
3
4
2
Information furnished by Linear Technology Corporation is believed to be accurate and reliable.
However, no responsibility is assumed for its use. Linear Technology Corporation makes no represen-
tationthattheinterconnectionofitscircuitsasdescribedhereinwillnotinfringeonexistingpatentrights.
15
LT1011/LT1011A
U
TYPICAL APPLICATION
10Hz to 100kHz Voltage to Frequency Converter
R7
4.7k
R4
1M
15V
15V
R1
C1
0.002µF
4.7k
POLYSTYRENE
LT1009
2.5V
15V
R2
5k
R5
R6
15V
8
2k
FULL-SCALE
TRIM
R3
2k
LINEARITY ≈0.01%
8.06k
3
2
INPUT
0V TO 10V
–
+
R8
4.7k
C2
0.68µF
7
LT1011
1
15V
–15V
4
†
1.5µs
R17
22M
6
R16
50k
10Hz TRIM
4.4V
–15V
15V
0.002µF
–15V
R9
5k
15V
TTL OUTPUT
10HZ TO 100kHz
–15V
R11
20k
10pF
1.5µs
Q2
R10
2.7k
ALL DIODES 1N4148
R15 R14
22k 1k
TRANSISTORS 2N3904
USED ONLY TO GUARANTEE
START-UP
*
†
R12
100k
1011 TA22
Q1*
MAY BE INCREASED FOR BETTER
10Hz TRIM RESOLUTION
+
R13
620k
2µF
–15V
RELATED PARTS
PART NUMBER
DESCRIPTION
UltraFastTM Precision Comparator
COMMENTS
LT1016
Industry Standard 10ns Comparator
Single Supply Version of the LT1016
7ns, 6mA Single Supply Comparator
450µA Single Supply Comparator
LT1116
12ns Single Supply Ground-Sensing Comparator
UltraFast Single Supply Comparator
60ns, Low Power Comparator
LT1394
LT1671
UltraFast is a trademark of Linear Technology Corporation.
1011fa LT/TP 0699 2K REV A • PRINTED IN USA
LINEAR TECHNOLOGY CORPORATION 1991
16 LinearTechnology Corporation
1630 McCarthy Blvd., Milpitas, CA 95035-7417
●
●
(408)432-1900 FAX:(408)434-0507 www.linear-tech.com
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