LT1011ACH#TR [Linear]
IC COMPARATOR, 1000 uV OFFSET-MAX, 150 ns RESPONSE TIME, MBCY8, METAL CAN, TO-5, 8 PIN, Comparator;
| 型号： | LT1011ACH#TR |
| 厂家： | 
Linear |
| 描述： | IC COMPARATOR, 1000 uV OFFSET-MAX, 150 ns RESPONSE TIME, MBCY8, METAL CAN, TO-5, 8 PIN, Comparator 放大器 |
| 文件： | 总16页 (文件大小：195K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
LT1011/LT1011A
Voltage Comparator
FEATURES
DESCRIPTION
The LT®1011 is a general purpose comparator with sig-
nificantly better input characteristics than the LM111.
Although pin compatible with the LM111, it offers four
times lower bias current, six times lower offset voltage
and five times higher voltage gain. Offset voltage drift,
a previously unspecified parameter, is guaranteed at
15μV/°C.Additionally,thesupplycurrentislowerbyafactor
of two with no loss in speed. The LT1011 is several times
faster than the LM111 when subjected to large overdrive
conditions. It is also fully specified for DC parameters and
responsetimewhenoperatingonasingle5Vsupply.These
parametric improvements allow the LT1011 to be used in
high accuracy (≥12-bit) systems without trimming. In a
12-bit A/D application, for instance, using a 2mA DAC, the
offset error introduced by the LT1011 is less than 0.5LSB.
The LT1011 retains all the versatile features of the LM111,
including single 3V to 1ꢀV supply operation, and a ꢁoat-
ing transistor output with 50mA source/sink capability. It
can drive loads referenced to ground, negative supply or
n
Pin Compatible with LM111 Series Devices
n
Guaranteed Max 0.5mV Input Offset Voltage
n
Guaranteed Max 25nA Input Bias Current
n
Guaranteed Max 3nA Input Offset Current
n
Guaranteed Max 250ns Response Time
n
Guaranteed Min 200,000 Voltage Gain
n
50mA Output Current Source or Sink
n
30V Differential Input Voltage
n
Fully Specified for Single 5V Operation
n
Available in ꢀ-Lead PDIP and SO Packages
APPLICATIONS
n
SAR A/D Converters
n
Voltage-to-Frequency Converters
n
Precision RC Oscillator
n
Peak Detector
n
Motor Speed Control
n
Pulse Generator
–
n
Relay/Lamp Driver
positive supply, and is specified up to 50V between V and
the collector output. A differential input voltage up to the
full supply voltage is allowed, even with 1ꢀV supplies,
enabling the inputs to be clamped to the supplies with
simple diode clamps.
L, LT, LTC and LTM are registered trademarks of Linear Technology Corporation. All other
trademarks are the property of their respective owners.
TYPICAL APPLICATION
10μs 12-Bit A/D Converter
3.9k
Response Time vs Overdrive
R1
1k
15V
LM329
7V
500
450
400
350
FULL-SCALE
TRIM
*R2 AND R4
SHOULD TC TRACK
–15V
R2*
6.49k
R3
6.9ꢀk
0.001μF
15V
INPUT
0V TO 10V
5V
300
250
FALLING
OUTPUT
6012
12-BIT
D/A CONVERTER
R4*
2.49k
R5
1k
200
150
100
50
RISING
OUTPUT
+
R6
LT1011A
ꢀ20Ω
–
PARALLEL
OUTPUTS
PARALLEL
OUTPUTS
0
0.1
1
10
100
SERIAL OUTPUT
OVERDRIVE (mV)
1011 TA02
7475
LATCH
D
AM2504
SAR REGISTER
5V
CC
S
E
S
CP
START
CLOCK f = 1.4MHz
1011 TA01
1011afc
1
LT1011/LT1011A
ABSOLUTE MAXIMUM RATINGS
(Note 1)
Supply Voltage (Pin ꢀ to Pin 4).................................36V
Output to Negative Supply (Pin 7 to Pin 4)
Input Voltage (Note 2)..........................Equal to Supplies
Output Short-Circuit Duration ...............................10 sec
Operating Temperature Range (Note 3)
LT1011AC, LT1011C................................. 0°C to 70°C
LT1011AI, LT1011I............................... –40°C to ꢀ5°C
LT1011AM, LT1011M (OBSOLETE).... –55°C to 125°C
Storage Temperature Range................... –65°C to 150°C
Lead Temperature (Soldering, 10 sec) .................. 300°C
LT1011AC, LT1011C..............................................40V
LT1011AI, LT1011I................................................40V
LT1011AM, LT1011M (OBSOLETE).......................50V
Ground to Negative Supply (Pin 1 to Pin 4) ..............30V
Differential Input Voltage......................................... 36V
Voltage at STROBE Pin (Pin 6 to Pin ꢀ) ......................5V
PACKAGE/ORDER INFORMATION
ORDER PART NUMBER
ORDER PART NUMBER
TOP VIEW
LT1011ACH
LT1011ACN8
TOP VIEW
+
V
LT1011CH
LT1011CN8
ꢀ
GND
INPUT
INPUT
1
2
3
4
V+
ꢀ
7
6
5
GND
INPUT
INPUT
1
3
7
5
OUTPUT
BALANCE/
LT1011AMH
LT1011MH
LT1011CS8
LT1011AIS8
LT1011IS8
OUTPUT
BALANCE/
STROBE
+
–
+
–
2
6
STROBE
–
V
BALANCE
BALANCE
4
Nꢀ PACKAGE
ꢀ-LEAD PDIP
Sꢀ PACKAGE
ꢀ-LEAD PLASTIC SO
S8 PART MARKING
–
V
H PACKAGE
ꢀ-LEAD TO-5 METAL CAN
= 150°C, θ = 150°C/W, θ = 45°C/W
T
= 150°C, θ = 130°C/W(Nꢀ)
JA
= 150°C, θ = 150°C/W(Sꢀ)
JA
JMAX
1011
1011AI
1011I
T
JMAX
T
JMAX
JA
JC
Jꢀ PACKAGE ꢀ-LEAD CERDIP
= 150°C, θ = 100°C/W(Jꢀ)
ORDER PART NUMBER
T
JMAX
JA
LT1011ACJ8 LT1011AMJ8
LT1011CJ8 LT1011MJ8
OBSOLETE PACKAGES
Consider the Nꢀ or Sꢀ Packages for Alternate Source
Order Options Tape and Reel: Add #TR
Lead Free: Add #PBF Lead Free Tape and Reel: Add #TRPBF
Lead Free Part Marking: http://www.linear.com/leadfree/
Consult LTC Marketing for parts specified with wider operating temperature ranges.
ELECTRICAL CHARACTERISTICS The l denotes the specifications which apply over the full operating
temperature range, otherwise specifications are at TA = 25°C. VS = 15V, VCM = 0V, RS = 0Ω, VGND = –15V, output at pin 7 unless
otherwise noted.
LT1011AC/AI/AM
LT1011C/I/M
SYMBOL PARAMETER
CONDITIONS
MIN
TYP
MAX
MIN
TYP
MAX UNITS
V
Input Offset Voltage
(Note 4)
0.3
0.5
1
0.6
1.5
3
mV
mV
OS
●
●
*Input Offset Voltage
R ≤ 50k (Note 5)
S
0.75
1.5
2
3
mV
mV
*Indicates parameters which are guaranteed for all supply voltages, including a single 5V supply. See Note 5.
1011afc
2
LT1011/LT1011A
ELECTRICAL CHARACTERISTICS The l denotes the specifications which apply over the full operating
temperature range, otherwise specifications are at TA = 25°C. VS = 15V, VCM = 0V, RS = 0Ω, VGND = –15V, output at pin 7 unless
otherwise noted.
LT1011AC/AI/AM
LT1011C/I/M
SYMBOL PARAMETER
CONDITIONS
MIN
TYP
MAX
MIN
TYP
MAX UNITS
I
*Input Offset Current
(Note 5)
0.2
3
5
0.2
4
6
nA
nA
OS
●
I
Input Bias Current
*Input Bias Current
(Note 4)
(Note 5)
15
20
25
20
25
50
nA
B
35
50
65
ꢀ0
nA
nA
●
●
ΔV
Input Offset Voltage Drift
(Note 6)
T
MIN
≤ T ≤ T
MAX
4
15
4
25
μV/°C
V/mV
V/mV
OS
ΔT
A
*Large-Signal Voltage Gain
R = 1k Connected to 15V,
200
50
500
300
200
50
500
300
VOL
L
–10V ≤ V
≤ 14.5V
OUT
R = 500Ω Connected to 5V,
L
V = Single 5V, V
= 0V,
S
GND
≤ 4.5V
0.5V ≤ V
OUT
CMRR
Common Mode Rejection Ratio
*Input Voltage Range (Note 9)
94
115
90
115
dB
●
●
V = 15V
S
–14.5
0.5
13
3
–14.5
0.5
13
3
V
V
S
V = Single 5V
t
D
*Response Time
(Note 7)
150
250
150
250
ns
V
*Output Saturation Voltage,
GND
V
V
V
= –5mV, I
= –5mV, I
= –5mV, I
= ꢀmA, T ≤ 100°C
0.25
0.25
0.7
0.4
0.45
1.5
0.25
0.25
0.7
0.4
0.45
1.5
V
V
V
OL
IN
IN
IN
SINK
SINK
SINK
J
V
= 0
= ꢀmA
●
●
= 50mA
*Output Leakage Current
V
V
= 5mV, V
OUT
= –15V,
0.2
10
500
0.2
10
500
nA
nA
IN
GND
= 20V
●
*Positive Supply Current
*Negative Supply Current
*Strobe Current (Note ꢀ)
V
V
= 0
3.2
1.7
4
3.2
1.7
4
mA
mA
μA
GND
GND
= 0
2.5
2.5
Minimum to Ensure Output Transistor is Off,
= 0
500
500
V
GND
Input Capacitance
6
6
pF
*Indicates parameters which are guaranteed for all supply voltages, including a single 5V supply. See Note 5.
Note 1: Stresses beyond those listed under Absolute Maximum Ratings
may cause permanent damage to the device. Exposure to any Absolute
Maximum Rating condition for extended periods may affect device
reliability and lifetime.
defines a worst-case error band that includes effects due to common
mode signals, voltage gain and output load.
Note 6: Drift is calculated by dividing the offset voltage difference
measured at min and max temperatures by the temperature difference.
Note 2: Inputs may be clamped to supplies with diodes so that
maximum input voltage actually exceeds supply voltage by one diode
drop. See Input Protection in the Applications Information section.
Note 7: Response time is measured with a 100mV step and 5mV
overdrive. The output load is a 500Ω resistor tied to 5V. Time
measurement is taken when the output crosses 1.4V.
Note 3: TJMAX = 150°C.
Note 4: Output is sinking 1.5mA with VOUT = 0V.
Note 5: These specifications apply for all supply voltages from a single
5V to 15V, the entire input voltage range, and for both high and low
output states. The high state is ISINK = 100μA, VOUT = (V+ – 1V) and
the low state is ISINK = ꢀmA, VOUT = 0.ꢀV. Therefore, this specification
Note 8: Do not short the STROBE pin to ground. It should be current
driven at 3mA to 5mA for the shortest strobe time. Currents as low
as 500μA will strobe the LT1011A if speed is not important. External
leakage on the STROBE pin in excess of 0.2μA when the strobe is “off”
can cause offset voltage shifts.
Note 9: See graph “Input Offset Voltage vs Common Mode Voltage.”
1011afc
3
LT1011/LT1011A
TYPICAL PERFORMANCE CHARACTERISTICS
Input Bias Current
Input Offset Current
Worst-Case Offset Error
100
10
1
0.9
0.ꢀ
0.7
0.6
0.5
0.4
0.3
0.2
0.1
0
45
40
35
30
25
20
15
10
5
I
FLOWS OUT
B
OF INPUTS
LM311
(FOR COMPARISON)
LT1011M
LT1011C
LT1011AM
LT1011AC
0.1
0
0
–50 –25
25 50 75 100 125 150
0
1k
10k
100k
1M
–50 –25
25 50 75 100 125 150
SOURCE RESISTANCE (Ω)
TEMPERATURE (°C)
TEMPERATURE (°C)
1011 G03
1011 G02
1011 G01
Input Characteristics*
Common Mode Limits
Transfer Function (Gain)
+
50
40
30
20
10
0
5
0
V
T
= 25°C
A
*EITHER INPUT.
–0.5
–1.0
–1.5
–2.0
0.4
REMAINING INPUT GROUNDED.
CURRENT FLOWS OUT OF INPUT.
COLLECTOR
OUTPUT
POSITIVE LIMIT
–5
V
= 15V
S
R
= 1k
L
–10
–15
–20
–25
–30
–35
–40
REFERRED TO SUPPLIES
NEGATIVE LIMIT
0.3
0.2
EMITTER
OUTPUT
0.1
R
= 600Ω
L
–
V
– 0.5
–0.3
–0.1
0.1
0.3
0.5
–10
0
150
–20 –15
–5
0
5
10 15 20
–50 –25
25 50 75 100 125
TEMPERATURE (°C)
DIFFERENTIAL INPUT VOLTAGE (mV)
INPUT VOLTAGE (V)
1011 G04
1011 G05
1011 G06
Collector Output Saturation
Voltage
Response Time—Collector Output
Response Time—Collector Output
6
5
4
3
2
1
0
6
5
4
3
2
1
0
1.0
0.9
0.ꢀ
0.7
0.6
0.5
0.4
0.3
0.2
0.1
0
V
=
15V
V
=
S
15V
PIN 1 GROUNDED
S
15V
5V
500Ω
V
IN
–
+
OVERDRIVE
20mV
T
= 125°C
OVERDRIVE
20mV
A
15V
5V
5mV
2mV
T
= 25°C
A
5mV
2mV
500Ω
V
IN
–
+
–15V
T
= –55°C
A
–15V
100mV
0
100mV
0
INPUT = 100mV STEP
INPUT = 100mV STEP
0
50 100 150 200 250 300 350 400 450
0
50 100 150 200 250 300 350 400 450
0
5
10 15 20 25 30 35 40 45 50
TIME (ns)
TIME (ns)
SINK CURRENT (mA)
1011 G07
1011 G0ꢀ
1011 G09
1011afc
4
LT1011/LT1011A
TYPICAL PERFORMANCE CHARACTERISTICS
Response Time Using GND Pin
as Output
Response Time Using GND Pin
as Output
Output Limiting Characteristics*
140
120
100
ꢀ0
0.7
+
V
T = 25°C
A
15
10
15
10
20mV
5mV
2mV
0.6
0.5
0.4
0.3
0.2
0.1
0
V
IN
+
POWER
DISSIPATION
V
5
5
V
V
OUT
IN
0
0
2k
–5
–5
V
OUT
–
V
–10
–15
0
–10
–15
0
2k
=
60
SHORT-CIRCUIT
CURRENT
5mV
2mV
20mV
–
V
40
V
=
15V
S
A
–50
–100
–50
–100
T
= 25°C
20
V
15V
S
A
*MEASURED 3 MINUTES
AFTER SHORT
T
= 25°C
0
0
2
TIME (μs)
3
4
0
2
3
4
0
10
5
OUTPUT VOLTAGE (V)
15
1
1
TIME (μs)
1011 G10
1011 G11
1011 G12
Supply Current vs Supply Voltage
Supply Current vs Temperature
Output Leakage Current
–7
–ꢀ
–9
5
4
3
2
6
5
4
3
10
10
10
V
= 15V
S
POSITIVE SUPPLY
COLLECTOR OUTPUT “LO”
POSITIVE SUPPLY
COLLECTOR OUTPUT “LO”
V
V
= 35V
= –15V
OUT
GND
POSITIVE AND NEGATIVE SUPPLY
COLLECTOR OUTPUT “HI”
2
1
0
–10
10
10
1
0
POSITIVE AND NEGATIVE SUPPLY
COLLECTOR OUTPUT “HI”
–11
50
TEMPERATURE (˚C)
100 125
0
10
15
20
25
30
–50 –25
0
25
75
5
25
45
65
ꢀ5
105
125
SUPPLY VOLTAGE (V)
TEMPERATURE (°C)
1011 G13
1011 G14
1011 G15
Output Saturation—
Ground Output
Output Saturation Voltage
Response Time vs Input Step Size
5
4
3
2
1
0
1000
ꢀ00
0.6
+
V
= 15V
REFERRED TO V
I
= ꢀmA
S
+
SINK
V
2
ꢀ
R = 500Ω TO 5V
L
+
OVERDRIVE = 5mV
0.5
0.4
0.3
0.2
0.1
0
7
LT1011
T = 125°C
J
5V
3
1
R
L
–
3
500Ω
7
INPUT
4
–
V
600
OUT
V
T = –55°C
J
2 +
T = 25°C
J
1
400
200
0
T = 25°C
J
RISING INPUT
FALLING INPUT
T = –55°C
J
T = 125°C
J
0
10
20
30
40
50
5
6
0
1
2
3
4
5
6
7
ꢀ
9
10
0
1
2
3
4
7
ꢀ
INPUT OVERDRIVE (mV)
OUTPUT CURRENT (mA)
INPUT STEP (V)
1011 G16
1011 G1ꢀ
1011 G17
1011afc
5
LT1011/LT1011A
TYPICAL PERFORMANCE CHARACTERISTICS
Input Offset Voltage
vs Common Mode Voltage
Offset Pin Characteristics
2.5
2.0
0.ꢀ
0.6
0.4
0.2
0
T = 25°C
J
1.5
CHANGE IN V FOR CURRENT
OS
1.0
UPPER
INTO PINS 5 OR 6
COMMON MODE
+
0.5
LIMIT = V – (1.5V)
0
VOLTAGE ON PINS 5 AND 6
–0.5
–1.0
–1.5
–2.0
–2.5
+
WITH RESPECT TO V
–150mV
–100mV
–50mV
–
V
(OR GND WITH
SINGLE SUPPLY)
0
–
+
V
0.1 0.2 0.3 0.4 0.5 0.6 0.7
COMMON MODE VOLTAGE (V)
V
25
150
50 75 100 125
–50 –25
0
TEMPERATURE (°C)
1011 G19
1011 G20
APPLICATIONS INFORMATION
Preventing Oscillation Problems
the BALANCE pins, which are nearly as sensitive as
the inputs.
Oscillation problems in comparators are nearly always
caused by stray capacitance between the output and
inputs or between the output and other sensitive pins
on the comparator. This is especially true with high
gain bandwidth comparators like the LT1011, which are
designed for fast switching with millivolt input signals.
The gain bandwidth product of the LT1011 is over 10GHz.
Oscillation problems tend to occur at frequencies around
5MHz, where the LT1011 has a gain of ≈2000. This implies
thatattenuationofoutputsignalsmustbeatleast2000:1at
5MHz as measured at the inputs. If the source impedance
is1kΩ, theeffectivestraycapacitancebetweenoutputand
input must have a reactance of more than (2000)(1kΩ) =
2MΩ, or less than 0.02pF. The actual interlead capacitance
between input and output pins on the LT1011 is less than
0.002pFwhencuttoprintedcircuitmountlength.Additional
stray capacitance due to printed circuit traces must be
minimized by routing the output trace directly away from
input lines and, if possible, running ground traces next
to input traces to provide shielding. Additional steps to
ensure oscillation-free operation are:
2. Bypass the negative supply (Pin 4) with a 0.1μF
ceramic capacitor close to the comparator. 0.1μF can
also be used for the positive supply (Pin ꢀ) if the
pull-up load is tied to a separate supply. When the
pull-up load is tied directly to Pin ꢀ, use a 2μF solid
tantalum bypass capacitor.
3. Bypass any slow moving or DC input with a capaci-
tor (≥0.01μF) close to the comparator to reduce high
frequency source impedance.
4. Keep resistive source impedance as low as possible.
If a resistor is added in series with one input to bal-
ance source impedances for DC accuracy, bypass
it with a capacitor. The low input bias current of the
LT1011 usually eliminates any need for source resis-
tance balancing. A 5kΩ imbalance, for instance, will
create only 0.25mV DC offset.
5. Use hysteresis. This consists of shifting the input
offset voltage of the comparator when the output
changes state. Hysteresis forces the comparator to
move quickly through its linear region, eliminating
oscillations by “overdriving” the comparator under all
input conditions. Hysteresis may be either AC or DC.
AC techniques do not shift the apparent offset voltage
1011afc
1. Bypass the STROBE/BALANCE pins with a 0.01μF
capacitor connected from Pin 5 to Pin 6. This elimi-
nates stray capacitive feedback from the output to
6
LT1011/LT1011A
APPLICATIONS INFORMATION
ꢀ
7
6
5
of the compara tor, but require a minimum input sig-
nal slew rate to be effective. DC hysteresis works for
all input slew rates, but creates a shift in offset volt-
age dependent on the previous condition of the input
signal. The circuit shown in Figure 1 is an excellent
compromise between AC and DC hysteresis.
Cꢀ TO C6 = 0.003μF
4
3
2
1
OUTPUT “LO” TO “HI”
15V
0
OUTPUT “HI” TO “LO”
+
2μF
–1
–2
C1
R
TANT
(50kHz)
10
(5kHz)
100
L
R2
15M
0.003μF
ꢀ
1
1000
–
+
3
2
6
TIME/FREQUENCY (μs)
5
7
1011 F02
OUTPUT
INPUTS
LT1011
1
Figure 2. Input Offset Voltage vs Time to Last Transition
4
error is created by the AC hysteresis. The high
–15V
0.1μF
frequency error can be reduced by reducing C , but
H
1011 F01
lower values may not provide clean switching with
very low slew rate input signals.
Figure 1. Comparator with Hysteresis
This circuit is especially useful for general purpose
comparator applications because it does not force
any signals directly back onto the input signal source.
Instead, it takes advantage of the unique proper-
ties of the BALANCE pins to provide extremely fast,
clean output switching even with low frequency input
signals in the millivolt range. The 0.003μF capacitor
from Pin 6 to Pin ꢀ generates AC hysteresis because
the voltage on the BALANCE pins shifts slightly,
depending on the state of the output. Both pins move
about 4mV. If one pin (6) is bypassed, AC hysteresis
is created. It is only a few millivolts referred to the
inputs, but is sufficient to switch the output at nearly
the maximum speed of which the comparator is ca-
pable. To prevent problems from low values of input
slew rate, a slight amount of DC hysteresis is also
used. The sensitivity of the BALANCE pins to current
is about 0.5mV input referred offset for each micro-
ampere of BALANCE pin current. The 15M resistor
tied from OUTPUT to Pin 5 generates 0.5mV DC
hysteresis. The combination of AC and DC hysteresis
creates clean oscillation-free switching with very
small input errors. Figure 2 plots input referred error
versus switching frequency for the circuit as shown.
Input Protection
The inputs to the LT1011 are particularly suited to general
purposecomparatorapplicationsbecauselargedifferential
and/or common mode voltages can be tolerated without
damage to the comparator. Either or both inputs can be
raised 40V above the negative supply, independent of the
positive supply voltage. Internal forward biased diodes
will conduct when the inputs are taken below the negative
supply. In this condition, input current must be limited to
1mA. If very large (fault) input voltages must be accom-
modated, series resistors and clamp diodes should be
used (see Figure 3).
+
V
R3*
D1
D3
D2
R1**
R2**
300Ω
3
2
ꢀ
LT1011
4
–
+
R4*
300Ω
INPUTS
D4
D1 TO D4: 1N414ꢀ
*MAY BE ELIMINATED FOR I
**SELECT ACCORDING TO ALLOWABLE
FAULT CURRENT AND POWER DISSIPATION
–
V
≤ 1mA
FAULT
1011 F03
Note that at low frequencies, the error is simply the
DC hysteresis, while at high frequencies, an additional
Figure 3. Limiting Fault Input Currents
1011afc
7
LT1011/LT1011A
APPLICATIONS INFORMATION
15V
ꢀ
5V
Theinputresistorsshouldlimitfaultcurrenttoareasonable
value (0.1mA to 20mA). Power dissipation in the resis-
tors must be considered for continuous faults, especially
when the LT1011 supplies are off. One final caution: lightly
loaded supplies may be forced to higher voltages by large
fault currents ꢁowing through D1-D4.
R
L
–
+
7
LT1011
OUTPUT
1
6
4
TTL OR
CMOS DRIVE
(5V SUPPLY)
–15
R3 and R4 limit input current to the LT1011 to less than
3k
–
1mA when the input signals are held below V . They may
1011 F04
be eliminated if R1 and R2 are large enough to limit fault
current to less than 1mA.
Figure 4. Typical Strobe Circuit
level inputs. A 1pF capacitor between the output and Pin
5 will greatly reduce oscillation problems without reduc-
ing strobe speed.
Input Slew Rate Limitations
The response time of a comparator is typically measured
with a 100mV step and a 5mV to 10mV overdrive. Unfor-
tunately, thisdoesnotsimulatemanyrealworldsituations
where the step size is typically much larger and overdrive
can be significantly less. In the case of the LT1011, step
size is important because the slew rate of internal nodes
will limit response time for input step sizes larger than
1V. At 5V step size, for instance, response time increases
from 150ns to 360ns. See the curve “Response Time vs
Input Step Size for more detail.
DC hysteresis can also be added by placing a resistor from
output to Pin 5. See step 5 under “Preventing Oscillation
Problems.”
Thepin(6)usedforstrobingisalsooneoftheoffsetadjust
pins. Current ꢁow into or out of Pin 6 must be kept very
low (<0.2μA) when not strobing to prevent input offset
voltage shifts.
Output Transistor
If response time is critical and large input signals are ex-
pected,clampdiodesacrosstheinputsarerecommended.
The slew rate limitation can also affect performance when
differential input voltage is low, but both inputs must slew
quickly. Maximum suggested common mode slew rate is
10V/μs.
The LT1011 output transistor is truly ꢁoating in the sense
that no current ꢁows into or out of either the collector
or emitter when the transistor is in the “off” state. The
equivalent circuit is shown in Figure 5.
+
V
Strobing
I
1
The LT1011 can be strobed by pulling current out of the
STROBE pin. The output transistor is forced to an “off”
state, giving a “hi” output at the collector (Pin 7). Currents
as low as 250μA will cause strobing, but at low strobe
currents, strobe delay will be 200ns to 300ns. If strobe
current is increased to 3mA, strobe delay drops to about
60ns.ThevoltageattheSTROBEpinisabout150mVbelow
0.5mA
D1
D2
COLLECTOR
(OUTPUT)
Q1
R1
170Ω
OUTPUT
Q2
+
+
TRANSISTOR
–
V at zero strobe current and about 2V below V for 3mA
strobe current. Do not ground the STROBE pin. It must be
current driven. Figure 4 shows a typical strobe circuit.
V
R2
470Ω
EMITTER
(GND PIN) 1011 F05
Figure 5. Output Transistor Circuitry
Note that there is no bypass capacitor between Pins 5 and
6. This maximizes strobe speed, but leaves the compara-
tor more sensitive to oscillation problems for slow, low
1011afc
8
LT1011/LT1011A
APPLICATIONS INFORMATION
+
In the “off” state, I is switched off and both Q1 and Q2
is tied to V , the voltage at the emitter in the “on” state is
1
+
turn off. The collector of Q2 can be now held at any voltage
about 2V below V (see curves).
–
above V without conducting current, including voltages
Input Signal Range
above the positive supply level. Maximum voltage above
–
V is 50V for the LT1011M and 40V for the LT1011C/I. The
The common mode input voltage range of the LT1011 is
about300mVabovethenegativesupplyand1.5Vbelowthe
positive supply, independent of the actual supply voltages
(seecurveintheTypicalPerformanceCharacteristics).This
is the voltage range over which the output will respond
correctly when the common mode voltage is applied to
one input and a higher or lower signal is applied to the
remaining input. If one input is inside the common mode
range and one is outside, the output will be correct. If the
inputs are outside the common mode range in opposite
directions, the output will still be correct. If both inputs are
outside the common mode range in the same direction,
the output will not respond to the differential input; for
temperatures of 25°C and above, the output will remain
unconditionally high (collector output), for temperatures
below 25°C, the output becomes undefined.
+
–
emitter can be held at any voltage between V and V as
long as it is negative with respect to the collector.
In the “on” state, I is connected, turning on Q1 and Q2.
1
DiodesD1andD2preventdeepsaturationofQ2toimprove
speed and also limit the drive current of Q1. The R1/R2
dividersetsthesaturationvoltageofQ2andprovidesturn-
off drive. Either the collector or emitter pin can be held at
+
–
a voltage between V and V . This allows the remaining
pin to drive the load. In typical applications, the emitter is
–
connected to V or ground and the collector drives a load
+
tied to V or a separate positive supply.
When the emitter is used as the output, the collector is
+
typically tied to V and the load is connected to ground
–
or V . Note that the emitter output is phase reversed with
respect to the collector output so that the “+” and “–”
input designations must be reversed. When the collector
TYPICAL APPLICATIONS
Offset Balancing
Driving Load Referenced
to Positive Supply
Driving Load Referenced
to Negative Supply
R2
3k
+
++
+
V
V
V
V
3
2
ꢀ
R1
2
3
ꢀ
R
–
+
LOAD
+
–
+
20k
V
7
7
LT1011
5
INPUTS*
LT1011
1
2
3
6
1
+
–
4
ꢀ
7
R
LOAD
LT1011
4
V
V
OR
GROUND
1011 TA03
V
1011 TA06
++
+
V
CAN BE GREATER OR LESS THAN V
*INPUT POLARITY IS REVERSED
WHEN USING PIN 1 AS OUTPUT
1011 TA05
1011afc
9
LT1011/LT1011A
TYPICAL APPLICATIONS
Strobing
Driving Ground Referred Load
Window Detector
++**
+
+
V
V
V
2
+
7
2
3
R
HIGH
L
LT1011
2
3
+
–
ꢀ
LIMIT
–
+
3
7
7
LT1011
–
6
INPUTS*
LT1011
OUTPUT HIGH
1
1
INSIDE “WINDOW”
AND LOW ABOVE
HIGH LIMIT OR
TTL
STROBE
L1
4
–
V
IN
BELOW LOW LIMIT
1k
2
3
V
1011 TA07
+
–
7
1011 TA04
*INPUT POLARITY IS REVERSED
WHEN USING PIN 1 AS OUTPUT
LT1011
LOW
LIMIT
NOTE: DO NOT GROUND STROBE PIN
++
–
**V MAY BE ANY VOLTAGE ABOVE V .
1
++
PIN 1 SWINGS TO WITHIN ≈2V OF V
1011 TA0ꢀ
Crystal Oscillator
Using Clamp Diodes to Improve Frequency Response*
CURRENT MODE
2
3
5V
INPUT
+
–
10k
(DAC, ETC)
7
LT1011
OUTPUT
D1
D2
1k
50k
2
ꢀ
+
VOLTAGE
INPUT
7
ꢀ5kHz
100pF
LT1011
OUT
R1
3
4
GROUND OR
LOW IMPEDANCE
REFERENCE
–
1
10k
*SEE CURVE, “RESPONSE TIME vs INPUT STEP SIZE”
1011 TA09
10k
1011 TA10
Noise Immune 60Hz Line Sync**
High Efficiency** Motor Speed Controller
5V
15V
R3
1k
R2
75k
+
C1
50μF
R1
1k
2V
RMS
Q1
TO
25V
5V
2N6667
R1*
RMS
330k
3
60Hz
INPUT
ꢀ
–
1N4002
7
OUTPUT
60Hz
C1
0.22μF
MOTOR-TACH
GLOBE 397A120-2
LT1011
2
1
+
R2
R3*
10k
R4
470Ω
4
27k
MOTOR TACH
R6
27k
15V
ꢀ
1011 TA11
R6
2k
5V
R5
100k
R5
10k
2
3
+
–
*INCREASE R1 FOR LARGER INPUT VOLTAGES
**LT1011 SELF OSCILLATES AT ≈60Hz CAUSING
IT TO “LOCK” ONTO INCOMING LINE SIGNAL
7
C2*
0.1μF
C3
0.1μF
R7
1k
LT1011
1
1011 TA12
R4
1k
4
*R3/C2 DETERMINES OSCILLATION
FREQUENCY OF CONTROLLER
**Q1 OPERATES IN SWITCH MODE
–5V TO
–15V
0V TO 10V
INPUT
1011afc
10
LT1011/LT1011A
TYPICAL APPLICATIONS
Combining Offset Adjust and Strobe
Combining Offset Adjustment and Hystersis
+
+
V
V
5k
R *
10k
2R **
H
H
*HYSTERESIS IS ≈0.45mV/μA OF
CURRENT CHANGE IN R
20k
H
6
20k
5
**THIS RESISTOR CAUSES HYSTERESIS
R
L
–
TTL OR CMOS
5V
TO BE CENTERED AROUND V
OS
–
+
5
7
1011 TA15
6
LT1011
LT1011
+
1k
1
1011 TA13
Direct Strobe Drive When CMOS* Logic
Uses Same V+ Supply as LT1011
Low Drift R/C Oscillator†
+
V
**
15V
15V
ꢀ
–
74HC04
s6
2
3
6
ꢀ
1k
+
LT1011
C1
0.015μF
7
BUFFERED
OUTPUT
+
1011 TA14
LT1011
4
–
*NOT APPLICABLE FOR TTL LOGIC
1
Positive Peak Detector
10k*
10k*
15V
15V
2k
*1% METAL FILM
3
2
10k*
ꢀ
INPUT
**TRW TYPE MTR-5/120ppm/°C, 25k ≤ R ≤ 200k
S
7
C1: 0.015μF = POLYSTYRENE, –120ppm/°C,
30ppm WESCO TYPE 32-P
1011 TA16
LT1011
2
1
+
NOTE: COMPARATOR CONTRIBUTES ≤10ppm/°C DRIFT
FOR FREQUENCIES BELOW 10kHz
LOW DRIFT AND ACCURATE FREQUENCY ARE
OBTAINED BECAUSE THIS CONFIGURATION
REJECTS EFFECTS DUE TO INPUT OFFSET
VOLTAGE AND BIAS CURRENT OF THE
COMPARATOR
6
OUTPUT
LT100ꢀ
†
4
10k
3
–
ꢀ
1M**
+
100pF
C1*
2μF
1011 TA17
–15V
*MYLAR
**SELECT FOR REQUIRED RESET TIME CONSTANT
Negative Peak Detector
15V
2
–
+
1M**
3
6
ꢀ
OUTPUT
–
LT100ꢀ
ꢀ
10k
7
3
LT1011
4
2k
2
1
+
100pF
INPUT
+
C1*
2μF
1011 TA1ꢀ
*MYLAR
**SELECT FOR REQUIRED RESET TIME CONSTANT
–15V
1011afc
11
LT1011/LT1011A
TYPICAL APPLICATIONS
4-Digit (10,000 Count) A/D Converter
15V
INPUT
0V TO 10V
15V
ZERO
TRIM
R1
1k
C4
0.01μF
R5
4.7k
5V
R2
1ꢀk
ꢀ
C5
0.01μF
R6
2
1
+
4.7K
6
1
7
LT1011
2
OUTPUT = 1 COUNT
PER mV, f = 1MHz
3
3
5
CLOCK
1MHz
LF39ꢀ
4
–
6
R7
5V
4
7
22Ω
D1
D2
–15V
R3
ꢀ
3.9k
15V
–15V
C1*
0.1μF
C2**
15pF
C3
0.1μF
R11
6.ꢀK
R4
5.6k
Rꢀ
3k
R10
D3
1k
15V
R9
3.65k
FULL-SCALE
TRIM
R12
6.ꢀk
D4
2N3904
C6
50pF
LM329
ALL DIODES: 1N414ꢀ
*POLYSTYRENE
**NPO
1011 TA19
START
≥12ms
Capacitance to Pulse Width Converter
T
H
T
L
≥ [C
(pF)][1μs/pF]
MAX
MAX
≥ 10 • C
• (1μs/pF)
D1
TTL OR CMOS
(OPERATING
ON 5V)
GAIN ADJ
5V
R2
100k
R1
5k
R1 + R4
R1
*PW = (R2 + R3)(C)
, INPUT CAPACITANCE OF
ꢀ
ꢁ
R3
ꢀ6.6k
ꢀ
0.01μF
7
R5
4.7k
LT1011 IS ≈6pF. THIS IS AN OFFSET TERM.
2
3
+
–
+
6
1
**TYPICAL 2 SECTIONS OF 365pF VARIABLE
CAPACITOR WHEN USED AS SHAFT ANGLE
INDICATION
†
OUTPUT
1μs/pF
10μF
LT1011
4
†
THESE COMPONENTS MAY BE ELIMINATED IF
NEGATIVE SUPPLY IS AVAILABLE (–1V TO –15V)
C**
†
D3
†
†
10μF
D2
+
1011 TA20
1011afc
12
LT1011/LT1011A
TYPICAL APPLICATIONS
Fast Settling* Filter
100pF
1M
15V
7
2
3
1M
6
OUTPUT
LT100ꢀC
4.7k
ꢀ
V
IN
1
4
4.7k
1μF
–15V 15V
4
OFM-1A**
1.5k
–15V 100pF
0.1μF
100k
2
3
ꢀ
–
7
1
LT1011
5
+
6
15V
15V
5k
THRESHOLD
5k
6
+
5
7
1
LT1011
–
ꢀ
4
10k
–15V 15V
1011 TA21
100kHz Precision Rectifier
0.033μF
100Ω
5V
5V
5V
5V
2
3
ꢀ
1k
AC INPUT
+
–
12k
74C04
5k
ꢀ20Ω
5V
7
LT1011
ZERO
CROSS
TRIM
HP50ꢀ2-2ꢀ00
s4
1
–5V
RECTIFIED
OUTPUT
4
–5V
1k
ꢀ20Ω
74C04
–5V
12k
–5V
1011 TA23
1011afc
13
LT1011/LT1011A
SCHEMATIC DIAGRAM
+
OFFSET
OFFSET/STROBE
6
V
5
ꢀ
Rꢀ
ꢀ00Ω
R9
ꢀ00Ω
Q6
Q10
R1
1.3k
R2
1.3k
R4
300Ω
R3
300Ω
R23
4k
R27
3k
R5
160Ω
Q11
Q5
Q31
Q12
R10
4k
R6
3.2k
R7
3.2k
Q13
D1 D2
Q30
R11
170Ω
INPUT
(+)
Qꢀ
Q7
D4
OUTPUT
7
D6
Q29
Q14
2
Q3
Q20
R22
200Ω
Q1
Q15
Q9 Q19
Q2ꢀ
R12
470Ω
INPUT
(–)
D5
Q4
D7
Q27
R16
ꢀ00Ω
3
Q2
Q24
Q16
R17
200Ω
R24
400Ω
R13
4Ω
Q26
Q23
Q21
Q25
R15
700Ω
R20
940Ω
1
Q22
Q1ꢀ
Q17
GND
R25
1.6k
R26
1.6k
R19
500Ω
R1ꢀ
275Ω
R21
960Ω
R14
4.ꢀk
D3
4
1011 SD
–
V
PACKAGE DESCRIPTION
H Package
8-Lead TO-5 Metal Can (.230 Inch PCD)
(Reference LTC DWG # 05-0ꢀ-1321)
0.335 – 0.370
(8.509 – 9.398)
DIA
OBSOLETE PACKAGE
0.027 – 0.045
(0.686 – 1.143)
0.305 – 0.335
(7.747 – 8.509)
0.040
45°TYP
PIN 1
0.028 – 0.034
(0.711 – 0.864)
0.050
(1.016)
MAX
0.165 – 0.185
(1.270)
MAX
(4.191 – 4.699)
0.230
(5.842)
TYP
REFERENCE
PLANE
SEATING
PLANE
GAUGE
PLANE
0.500 – 0.750
(12.700 – 19.050)
0.010 – 0.045*
(0.254 – 1.143)
0.016 – 0.021**
(0.406 – 0.533)
H8 (TO-5) 0.230 PCD 1197
0.110 – 0.160
(2.794 – 4.064)
INSULATING
STANDOFF
*LEAD DIAMETER IS UNCONTROLLED BETWEEN THE REFERENCE PLANE
AND 0.045" BELOW THE REFERENCE PLANE
0.016 – 0.024
**FOR SOLDER DIP LEAD FINISH, LEAD DIAMETER IS
(0.406 – 0.610)
1011afc
14
LT1011/LT1011A
PACKAGE DESCRIPTION
J8 Package
8-Lead CERDIP (Narrow .300 Inch, Hermetic)
(Reference LTC DWG # 05-0ꢀ-1110)
0.405
(10.287)
MAX
CORNER LEADS OPTION
(4 PLCS)
0.005
(0.127)
MIN
6
5
8
7
0.023 – 0.045
(0.584 – 1.143)
HALF LEAD
OPTION
0.025
0.220 – 0.310
(5.588 – 7.874)
0.045 – 0.068
(0.635)
RAD TYP
(1.143 – 1.727)
FULL LEAD
OPTION
1
2
3
4
0.200
(5.080)
MAX
0.300 BSC
(0.762 BSC)
0.015 – 0.060
(0.381 – 1.524)
0.008 – 0.018
(0.203 – 0.457)
0° – 15°
0.045 – 0.065
(1.143 – 1.651)
0.125
3.175
MIN
NOTE: LEAD DIMENSIONS APPLY TO SOLDER DIP/PLATE
OR TIN PLATE LEADS
0.014 – 0.026
(0.360 – 0.660)
0.100
(2.54)
BSC
J8 1298
OBSOLETE PACKAGE
N8 Package
8-Lead PDIP (Narrow .300 Inch)
(Reference LTC DWG # 05-0ꢀ-1510)
.400*
(10.160)
MAX
.130 .005
.045 – .065
.300 – .325
(3.302 0.127)
(1.143 – 1.651)
(7.620 – 8.255)
8
7
6
5
4
.065
(1.651)
TYP
.255 .015*
(6.477 0.381)
.008 – .015
(0.203 – 0.381)
.120
.020
(0.508)
MIN
(3.048)
MIN
+.035
–.015
1
2
3
.325
.018 .003
(0.457 0.076)
.100
(2.54)
BSC
+0.889
8.255
(
)
N8 1002
–0.381
NOTE:
INCHES
1. DIMENSIONS ARE
MILLIMETERS
*THESE DIMENSIONS DO NOT INCLUDE MOLD FLASH OR PROTRUSIONS.
MOLD FLASH OR PROTRUSIONS SHALL NOT EXCEED .010 INCH (0.254mm)
S8 Package
8-Lead Plastic Small Outline (Narrow .150 Inch)
(Reference LTC DWG # 05-0ꢀ-1610)
.189 – .197
(4.801 – 5.004)
NOTE 3
.010 – .020
(0.254 – 0.508)
7
5
8
6
× 45°
.053 – .069
(1.346 – 1.752)
.045 .005
.160 .005
.050 BSC
.004 – .010
(0.101 – 0.254)
.008 – .010
0°– 8° TYP
(0.203 – 0.254)
.150 – .157
(3.810 – 3.988)
NOTE 3
.228 – .244
(5.791 – 6.197)
.016 – .050
(0.406 – 1.270)
.245
MIN
.050
(1.270)
BSC
.014 – .019
(0.355 – 0.483)
TYP
NOTE:
INCHES
1. DIMENSIONS IN
(MILLIMETERS)
2. DRAWING NOT TO SCALE
3. THESE DIMENSIONS DO NOT INCLUDE MOLD FLASH OR PROTRUSIONS.
MOLD FLASH OR PROTRUSIONS SHALL NOT EXCEED .006" (0.15mm)
1
2
3
4
.030 .005
TYP
SO8 0303
RECOMMENDED SOLDER PAD LAYOUT
1011afc
Information furnished by Linear Technology Corporation is believed to be accurate and reliable.
However, no responsibility is assumed for its use. Linear Technology Corporation makes no representa-
tion that the interconnection of its circuits as described herein will not infringe on existing patent rights.
15
LT1011/LT1011A
TYPICAL APPLICATION
10Hz to 100kHz Voltage to Frequency Converter
R7
4.7k
R4
1M
15V
15V
R1
C1
0.002μF
4.7k
POLYSTYRENE
LT1009
2.5V
15V
R2
5k
R5
R6
15V
ꢀ
2k
FULL-SCALE
TRIM
R3
2k
LINEARITY ≈0.01%
ꢀ.06k
3
2
INPUT
0V TO 10V
–
+
Rꢀ
4.7k
C2
0.6ꢀμF
7
LT1011
1
15V
–15V
4
†
1.5μs
R17
22M
6
R16
50k
10Hz TRIM
4.4V
–15V
15V
15V
0.002μF
10pF
–15V
R9
5k
TTL OUTPUT
10HZ TO 100kHz
–15V
R11
20k
1.5μs
Q2
R10
2.7k
ALL DIODES 1N414ꢀ
R15 R14
22k 1k
TRANSISTORS 2N3904
USED ONLY TO GUARANTEE
START-UP
*
†
R12
100k
1011 TA22
Q1*
MAY BE INCREASED FOR BETTER
10Hz TRIM RESOLUTION
+
R13
620k
2μF
–15V
RELATED PARTS
PART NUMBER
LT1016
DESCRIPTION
COMMENTS
UltraFast™ Precision Comparator
Industry Standard 10ns Comparator
Single Supply Version of the LT1016
7ns, 6mA Single Supply Comparator
450μA Single Supply Comparator
LT1116
12ns Single Supply Ground-Sensing Comparator
UltraFast Single Supply Comparator
60ns, Low Power Comparator
LT1394
LT1671
UltraFast is a trademark of Linear Technology Corporation.
1011afc
LT 0308 REV C • PRINTED IN USA
LinearTechnology Corporation
1630 McCarthy Blvd., Milpitas, CA 95035-7417
16
●
●
© LINEAR TECHNOLOGY CORPORATION 1991
(40ꢀ) 432-1900 FAX: (40ꢀ) 434-0507 www.linear.com
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Linear
LT1011AMH#PBF
IC COMPARATOR, 1000 uV OFFSET-MAX, 150 ns RESPONSE TIME, MBCY8, METAL CAN, LEAD FREE, TO-5, 8 PIN, Comparator
Linear
LT1011AMH#TR
IC COMPARATOR, 1000 uV OFFSET-MAX, 150 ns RESPONSE TIME, MBCY8, METAL CAN, TO-5, 8 PIN, Comparator
Linear
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