AB20-3 [LUMILEDS]
Electrical Design Considerations for SuperFlux LEDs; 电气设计考虑食人鱼LED灯型号: | AB20-3 |
厂家: | LUMILEDS LIGHTING COMPANY |
描述: | Electrical Design Considerations for SuperFlux LEDs |
文件: | 总37页 (文件大小:2017K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
application brief AB20-3
replaces AN1149-3
Electrical Design
Considerations for
SuperFlux LEDs
Table of Contents
Overview
Summary
2
Electrical Design Process Overview
Circuit Design Overview
3
4
Worst-Case Circuit Analysis and Validation
Comparison of Different Methods of Worst-Case Circuit Analysis
Characterization of Prototype LED Signal Lamp
Validation of LED Signal Lamp
5
5
7
7
Key Concepts for Electrical Design of LED Signal Lamps
Resistor-Limited Drive Circuits
8
8
Effect of LED String Length on Forward Current Regulation
Forward Current Variations between LED Emitters in an Array
EMC Transient Protection Circuits
9
10
12
12
Stop/Tail Drive Circuits
Theory
Electrical, Optical, and Thermal Characteristics of LED Emitters
LED Emitter Modeling
13
16
17
18
19
Linear Forward Voltage Model
Luminous Flux Models Versus Forward Current and Temperature
Thermal Resistance Models
Applications
Resistive Current Limiting
CHMSL Design Example
EMC Transient Protection
Special Considerations for Dual Luminous Intensity Operation
Luminous Flux Variations at Low Currents
PWM Drive Circuit for Tail Functions
Current and Voltage Regulator Circuits
Operation of Shunt, Series-Pass, and Switching Regulators
21
24
27
29
29
30
31
32
Overview
Summary
The electrical design is part of the overall signal
The electrical design of an LED signal lamp has
several objectives. The first objective is to
operate the individual LED emitters at sufficient
drive current in order to generate sufficient
luminous flux to meet the lighting requirements.
The second objective should be to limit the
forward current through the individual LED
emitters so as not to exceed their maximum
internal junction temperatures and maximum dc
forward currents under worst-case conditions of
ambient temperature and input voltage. In
addition, the electrical design should protect the
LED array from automotive EMC transients.
Finally, the electrical design should provide
good intensity matching within the LED array.
The result of achieving these objectives will be a
maintenance-free LED signal light that operates
reliably for the lifetime of the passenger vehicle
or truck.
used in LED signal lamps and related circuit
design issues.
In addition to AB20-3, two companion electrical
design application notes are also available.
AB20-3A, titled “Advanced Electrical Design
Models,” discusses forward voltage models that
are more accurate and usable over a larger range
of forward currents than the simple linear models
shown in the “LED Emitter Modeling” section. In
addition, AB20-3A derives several additional
thermal-modeling equations from the basic
equations shown in the “LED Emitter Modeling”
section.
Application Note titled AB20-3B “SuperFlux LED
Forward Voltage Data” gives worst-case forward
voltage data for SuperFlux and SnapLED70
emitters. There are several potential electrical
models for LED emitters (linear, diode equation
models, etc.), each one optimized for an
Application Brief AB20-3 has been written to
simplify the electrical design of LED signal
lamps and is part of the Application Brief AB20
series. This application note has been divided
into three major blocks—Overview, Theory, and
Applications. The Overview consists of five
sections that discuss the electrical design
process and key electrical design concepts.
Theory consists of two sections that give an
in-depth overview of the electrical, optical,
and thermal properties of LED emitters and
mathematical modeling of their operation.
Applications consist of four sections that cover
specific types of circuit designs commonly
expected range of forward currents, and various
levels of “worst-casing” (i.e. min/max, average,
average ± one, two, three standard deviations,
etc.). In order to accommodate these various
needs, the data presented in AB20-3B gives the
nominal forward voltage and expected forward
voltage range for each SuperFlux LED
characterized over a range of forward currents
up to 70 mA. From this data, the desired
electrical model can easily be generated. The
latest forward voltage data for SuperFlux LED
emitters is available from your local Lumileds
Lighting or Agilent Technologies sales engineer
or from the following URL:
forward voltage can cause luminous intensity
matching variations within groups of
http://www.lumileds.com
SuperFlux emitters from the same luminous
flux and forward voltage category. For this
reason, Lumileds Lighting does not warrant
LED performance at currents less than 20 mA
(40 mA for SnapLED 150) and strongly
discourages these designs.
Note: For best matching within an array,
SuperFlux and SnapLED 70 emitters should
be operated at forward currents over 20 mA
(40 mA for SnapLED 150). At forward
currents below 20 mA (40 mA for SnapLED
150), variations in luminous efficiency and
Electrical Design Process
The electrical design is part of the overall signal
lamp design process described in AB20-1.
exceeded, portions of the electrical or thermal
design may need to be iterated in order to
reduce the forward current and/ or junction
temperature. Finally, additional prototypes of the
signal lamps should be constructed and
subjected to the appropriate reliability validation
tests.
The electrical design consists of several discrete
steps. The first step is to determine the circuit
topology and to generate an electrical
schematic of the overall circuit. First, the circuit
topology must be determined. Circuit topology
refers to the arrangement of electrical
The most important circuit topology
considerations include:
components on the electrical schematic. Next,
the circuit must be designed. Circuit design is
the process where the electrical components
are selected and component values are
• Number of LED emitters in series
• Whether LED emitters are connected in
individual series-strings, or in cross-
connected series strings
determined. Third, the operation of the circuit
must be analyzed. Circuit analysis refers to the
mathematical analysis of the variations in
voltage and current through the electrical
components due to variations in applied voltage
and component tolerances. The fourth step is
to create a breadboard of the circuit and to
measure the forward current, light output, and
thermal properties of the entire signal. If the
maximum junction temperature or the maximum
DC forward current of any of the LED emitters is
exceeded, the reliability of the LED signal lamp
may be compromised. Thus, if the circuit
validation tests indicate that these limits are
• Method of current limiting (i.e. resistors or
active circuit)
• Method of EMC protection (if any)
• Method of dimming, such as for a combined
Stop/ Tail signal
Circuit design is the solution of several
simultaneous linear equations that model the
forward current through each loop or node of the
circuit. The solution of these equations
determines the values of electrical components
that drive the LED array at the desired forward
current at the specified external supply voltage.
3
Different mathematical models can be used to
model the forward voltage of the LED emitters
depending on the accuracy and dynamic range
needed.
and LED emitters. With this technique, the
voltages and currents through each component
can be determined based on the expected
minimum and maximum limits of component
values in the circuit. Another technique is to use
a Monte Carlo simulation. With this method the
voltages and currents through each component
are determined for random combinations of
component values in the circuit. Then the results
for a large number of Monte Carlo simulations
are statistically tabulated. The Monte Carlo
simulation method gives a better estimate of the
expected manufacturing variations for the circuit.
Circuit analysis uses the same types of
simultaneous linear equations used in the
electrical design. However, circuit analysis
generally assumes that the external voltage
applied to the circuit, the values of electrical
components, and the ambient temperature can
vary over some predetermined range. Circuit
analysis can be done using “worst-case”
electrical models for the electronic components
Circuit Design Overview
As stated earlier, the first step in the electrical
design is to pick one of the circuit topologies.
Next, the operation of the circuit can be
modeled with a series of simultaneous linear
equations that describe the current through
each electronic component as a function of
component values and applied voltage. For
circuit design, it is usually assumed that all
LED emitters have the same electrical
characteristics, which greatly simplifies the
mathematical modeling.
As will be shown in the section “Key Concepts
for the Electrical Design of LED Signal Lamps”
the different circuit topologies provide different
levels of forward current regulation and overall
electrical power consumption. Circuits with poor
forward current regulation would require the LED
emitters to be driven at a lower forward current
at the nominal input voltage than would circuits
with better forward current regulation (so as not
to exceed the maximum forward current at the
maximum input voltage). Circuits with higher
amounts of power consumption would tend to
have higher internal self-heating (unless the
circuitry is located outside the signal lamp
In order to ensure reliable operation, the
maximum forward current through the LED
emitters should not exceed the maximum value
obtained from Figure 4 in the HPWx-xx00 data
sheet. Note that the maximum forward current
of the LED emitters is based on the maximum
ambient temperature, TA, the maximum input
voltage, and the thermal resistance, R qJA, of the
LED signal light assembly.
housing), which would also tend to reduce the
maximum forward current of the LED emitters. At
this point, it may be desirable to evaluate several
different circuit topologies on paper and see
which one gives the “best” overall results.
If the signal lamp will be exposed to high-voltage
EMC transients, then the appropriate protection
circuitry can be added to the basic circuit
4
chosen. Worst-case forward and reverse
transient currents can be estimated using the
linear forward current model for positive
transients and the minimum breakdown voltage
specification, VBR, on the data sheet for negative
transients.
Worst-Case Circuit Analysis and Validation
The next step in the electrical design should be
an analysis of the forward current through the
LED emitters at worst-case input voltage and
operating temperature extremes using worst-
case component tolerances. All of the active
and passive electronic components used in the
circuit design can be modeled with their worst-
case minimum and maximum values. This
analysis serves several purposes. First, it
determines whether the forward current is less
than the maximum dc forward current under all
operating conditions. Secondly, it determines
the change in light output of the signal lamp
under the same conditions. Finally, it can be
used to determine the worst-case matching
within the LED array.
circuit. Thus, the actual occurrence of these
worst-case conditions could be extremely small.
Another approach to worst-case analysis is to
characterize a number of LED emitters and
determine the appropriate forward voltage
model for each one. Then using a Monte-Carlo
simulation, random combinations of these
emitters can be assembled into a “paper”
circuit and the actual forward currents can
be calculated for the circuit based on the
corresponding forward voltage models. Then
the results from multiple simulations can be
tabulated. This approach provides a much better
understanding of the forward current variations
that would occur in actual practice.
This worst-case analysis can be done in several
different ways. One approach is to use worst-
case values for one or more LED emitters in the
array such as to cause worst-case current
matching between LED emitters or to establish
the maximum or minimum forward current
through individual LED emitters. The problem
with this approach is that probability of this
occurrence actually happening can be quite
low. If the probability of getting worst-case LED
emitters is very small, then the probability of
both minimum and maximum worst-case LED
emitters occurring in the same circuit assembly
is even lower. Furthermore, for the worst-case
variations in forward currents to actually occur,
these worst-case LED emitters must both be
randomly assembled into certain parts of the
In general, within arrays of LED emitters, the
maximum forward current occurs at the
maximum input voltage with the minimum value
of the current limiting resistor and minimum
forward voltage model for the LED emitters.
Likewise, the minimum forward current occurs
at the minimum input voltage with the maximum
value of the current limiting resistor and
maximum forward voltage model for the LED
emitters.
The worst-case forward current variations
for different LED emitters within the array is
determined by the circuit topology, the drive
current, and the variation in electrical
characteristics of the individual LED emitters
in the array. When several LED emitters are
5
connected in series, the worst-case minimum
forward current would occur when all LED
emitters in a given series string have the worst-
case maximum forward voltage. Likewise, the
worst-case maximum forward current would
occur when all LED emitters in another series-
string have the worst-case minimum forward
voltage. For these series-string circuits, the
likelihood of all LED emitters being at their
worst-case forward voltage extremes is quite
low. When LED emitters are connected in
parallel, the forward current through each LED
will vary somewhat from the average forward
current so as to generate the same forward
voltage across all LED emitters in the parallel
grouping. The worst-case forward current
variations occur when one LED emitter has
the worst-case minimum forward voltage and
another LED emitter in the same parallel
grouping has the worst-case maximum
forward voltage.
range of 35 to 70 mA (70 to 150 mA for the
SnapLED 150). These matching effects are
covered in more detail in the section “Key
Concepts for Electrical Design of LED Signal
Lamps.”
The reader will need to determine whether the
assumptions used for the worst-case designs are
reasonable. It is possible to design with such
large tolerances, that the worst-case design
results in an over-designed circuit. Over-
designing occurs if significant cost is added to
the assembly in order to protect against the
remote possibility of occurrences that might
never happen in practice. In the case of LED
signal lamps, over-designing might result in many
more LED emitters being added to the array than
needed. The best example might be where the
designer chooses an extremely high worst-case
input voltage and maximum ambient
temperature. Then, the use of the suggested
design process in the “Resistive Current Limiting”
section would result in a fairly small design
current at the design input voltage. This design
current would require a large number of LED
emitters to achieve the desired light output from
the array. Or the assumptions used for the worst-
case input voltage and ambient temperature
might require the use of a more expensive
constant current drive circuit, where with more
reasonable assumptions a resistive circuit could
have been used. These concerns about over-
designing by using excessive tolerances on input
voltage and ambient temperature also can be
applied to LED emitter tolerances. For example,
the probability of all LED emitters in a given array
being at their worst-case minimum or maximum
limits is very small but still is greater than zero. If
every LED emitter is assumed to be at the worst-
case minimum extreme, then the external current
SuperFlux and SnapLED 70 emitters are
categorized for forward voltage at 70 mA.
As might be expected, the smallest forward
current variations within an array of SuperFlux
or SnapLED 70 LED emitters occur at drive
current approaching 70 mA. Similarly, SnapLED
150 emitters are categorized for forward voltage
at 150 mA, so the best matching occurs at 150
mA. At lower forward currents, the variations in
forward current within the LED array become
larger—especially when LED emitters are
connected in parallel. For series-string circuits,
acceptable forward current variations can
usually be achieved over forward currents over
a range of 20 to 70 mA (40 to 150 mA for the
SnapLED 150). However, when LED emitters
are connected in parallel, acceptable forward
current variations can be achieved only over a
6
limiting resistor may be chosen to overly restrict
the forward current through the array. Another
possibility is that if the circuit is designed to
accommodate every LED emitter in a given
array being at their worst-case minimum or
maximum limits, then design might eliminate
several potential circuit topologies because of
excessive light output variations. In practice,
the likelihood of these conditions actually
occurring is so small, that the design process
might have eliminated more cost effective circuit
topologies. For this reason, Lumileds Lighting
recommends that worst-case design be used
as a development tool in conjunction with
characterization and validation of the signal
lamp assembly.
optical transmission losses. The prototype allows
these assumptions to be measured. Third, the
working prototype allows the thermal properties
of the LED signal light to be evaluated. The
thermal resistance, RqPIN A, can be measured by
attaching thermocouples to the cathode pins of
several LED emitters in the array.
Based on the electrical, optical, and thermal
measurements of the working prototype,
additional iterations of the design may be
required. These design iterations will further
refine the estimates for the electrical component
values, the number of LED emitters needed for
the signal lamp, and the thermal resistance of
the signal lamp. Also, it may be necessary to
evaluate improved optical designs and methods
for improving the thermal properties of the LED
signal lamp assembly. For more information on
thermal design, the reader is encouraged to
review AB20-4 “Thermal Management
Following this paper design, a working
prototype LED signal light can be constructed.
This prototype serves several purposes. First,
it allows verification of the electrical design. The
forward current can be measured at different
input voltages and compared with the paper
electrical design. Second, it allows verification
of the optical design. In AB20-1 section,
“Estimating the Number of LED Emitters
Needed,” assumptions were made for the
Considerations for SuperFlux LEDs.” For
more information on optics design, the reader
is encouraged to review AB20-5 “Secondary
Optic Design Considerations for SuperFlux
LEDs.”
7
Key Concepts for Electrical Design of LED Signal Lamps
Presently, most current LED signal lamp
designs use resistive current limiting for the LED
array. Since most LED signal lamps are driven
from 12 to 24 V dc and require several LED
emitters, the emitters can be connected in
series and share the same supply current.
Some of the most common circuit
Where:
VIN = input voltage applied to the circuit
VF = forward voltage of LED emitter at forward
current IF
VD = voltage drop across optional reverse
transient EMC protection diode
y = number of series connected LED emitters
x = number of paralleled strings
configurations are shown in Figure 3.1. The
series connected string circuit in Figure 3.1a
uses a separate current limiting resistor for each
string of y LED emitters. The paralleled-string
circuit in Figure 3.1b uses a single resistor for
the entire LED array. Note that this circuit uses x
strings with y LED emitters per string. The
cross-connected paralleled string circuit shown
in Figure 3.1c has one or more cross
Thus for a given IF , the value of R depends both
on the number of LED emitters per string as well
as the number of paralleled strings.
As shown later in the section “LED Emitter
Modeling” the forward voltage of an LED emitter
can be mathematically modeled by the following
equation:
connections between the strings of LED
emitters. A mechanical analogy to this circuit is
that the circuit looks like a “ladder” with each
cross connection being a “rung” on the
VF @?V O + RS IF
“ladder.” In the diagram, z, refers to the number
of series connected LED emitters between each
“rung” with 1 £ z £ y. Most CHMSL designs
use either several series connected strings
(Figure 3.1a) or several cross-connected series
strings (Figure 3.1c) with z =1. Note that in
order to obtain the same forward current for
all of LED emitters, both of the circuits
shown in Figure 3.1b and Figure 3.1c need
to have the same number of LED emitters in
each string and each “rung” for Figure 3.1c.
Where:
VO = turn-on voltage of each LED emitter
RS = series resistance of each LED emitter
This equation is known as the linear forward
voltage model since it models the forward
voltage of the LED with a straight line. In using
this model it is important to remember that it can
only be used over a specific range of forward
currents. Outside of this range, the model will
give misleading results. Using the linear forward
voltage model, this equation can be rewritten as:
Note that if all LED emitters have identical
electrical forward characteristics, then the value
of the external current limiting resistor, R, is
equal to:
8
The number of LED emitters selected per
string (y) affects the change in the forward
current of the LED emitters as the input
voltage varies over some range. In general,
as the value of y is increased, the change in
forward current becomes larger due to the
same input voltage variation. In addition, when
the input voltage is less than (yVO) the forward
current through each LED emitter is
through each string of LED emitters as a function
of input voltage. Figure 3.2 shows string lengths
ranging from 2 to 6 emitters. Note that series-
strings with 5 and 6 emitters have the largest
change in forward current and highest “threshold
voltage.” Since the forward voltage of the LED
emitters varies slightly over temperature, then the
forward current through each LED string will
change slightly over temperature. Circuits with
longer string lengths will have a slightly larger
forward current change over temperature.
approximately equal to zero. As the value of y is
increased, this “threshold” voltage increases.
Figure 3.2 shows the change in forward current
Figure 3.1 Circuit Configuration of LED Arrays Used in LED Signal Lamps.
9
Figure 3.2 Forward Current Through String of
HPWA-xHOO LED Emitters versus Applied
Voltage.
Figure 3.3 Total Supply Current versus Supply
Voltage for Sixty HPWA-xHOO Emitter LED
Signal Lamp Array Driven in Series Strings
with Two, Three, Four, Five, or Six Emitters
per String.
The number of LED emitters per string also
affects the total supply current. For a fixed
number of LED emitters longer string lengths
result in fewer total strings and thus a lower
total supply current. Figure 3.3 shows the
total supply current for the series-string
configurations in Figure 3.2. Figure 3.3 assumes
a total of 60 LED emitters, thus 2-LED strings
would require 30 strings, 3-LED strings would
require 20 strings, etc. Note that the total
supply current is much higher for series strings
with 2 and 3 emitters.
Variations in the forward voltage characteristics
of the individual LED emitters can lead to forward
current variations within the LED array. These
forward current variations directly affect the
luminous flux output of each LED emitter and can
cause noticeable luminous intensity variations
within the LED array. These random variations in
forward voltage characteristics affect the three
circuits shown in Figure 3.1 differently.
The “series-string” circuit shown in Figure 3.1a
is least affected by random forward voltage
variations between the LED emitters because the
forward voltages of all LED emitters in a given
string are averaged together. In many cases, one
emitter with a high forward voltage can cancel
out another emitter in the same series-string with
a low forward voltage. In addition, the voltage
drop across the current limiting resistor, R, is
much higher than the combined voltage drops
across the series resistors, yRS. Thus, small
variations in RS only cause small variations in the
forward current through the series string.
As shown by Figures 3.2 and 3.3, the choice of
the number of emitters per string is a tradeoff
between the regulation of forward current due
to input voltage variations and the total supply
current for the LED array. Small string lengths
give excellent forward current regulation, but
require a higher supply current. Long string
lengths provide poor forward current regulation
but require less supply current. For these
reasons, most 12 V resistive limited designs
use three or four LED emitters per series
string (y = 3 or 4).
Because SuperFlux and SnapLED 70 emitters
are categorized for forward voltage at 70 mA
(150 mA for the SnapLED 150), the smallest
10
Figure 3.4 Worst-Case and Typical Variations
in Forward Current Between Two Strings of
HPWT-xHOO LED Emitters Driven with
Individual Current-Limiting Resistors per
String (Figure 1a Circuit, with y=4).
Figure 3.5 Worst-Case and Typical Variations
in Forward Current Between 16 HPWT-xHOO
LED Emitters Driven in a Cross-Connected
Paralleled String Configuration (Figure 1c
Circuit with x = y = 4, z = 1).
forward current variations between adjacent
series-strings of LED emitters occur at a drive
current of 70 mA (150 mA for the SnapLED
150). However, the forward current matching
between adjacent strings is quite good even at
forward currents as low as 10 mA (20 mA for
the SnapLED 150). Figure 3.4 shows the worst-
case forward current variation between two LED
strings constructed using four LED emitters per
string. The worst-case calculations assume that
all HPWT-xH00 emitters are from the same
forward voltage category and one string uses
four “minimum” forward voltage emitters and
the other string uses four “maximum” forward
voltage emitters. The typical calculations
SuperFlux and SnapLED 70 emitters and 40
mA for SnapLED 150 emitters (see the section
“Electrical, Optical, and Thermal
Characteristics of LED Emitters).
The “paralleled-string” circuit shown in Figure
3.1b and the “cross-connected series string”
circuit shown in Figure 3.1c do not regulate the
forward current as well as the “series-string”
circuit. When two or more LED emitters are
connected in parallel, the forward current
through each emitter will be somewhat higher or
lower than the average forward current through
them so as to force the forward voltage across
them to be the same. Again, because SuperFlux
LED and SnapLED 70 emitters are categorized
for forward voltage at 70 mA (150 mA for the
SnapLED 150), the smallest forward current
variations between adjacent LED strings (Figure
3.1b circuit) or between LED emitters in the
same “rung” (Figure 3.1c circuit) occur at a drive
current of 70 mA (150 mA for SnapLED 150).
The variations in forward currents become much
worse at lower drive currents. These variations in
forward currents can cause unacceptable
assume that all HPWT-xH00 emitters are from
the same forward voltage category and one
string consists of two “minimum” forward
voltage emitters and two “typical” forward
voltage emitters and the other string consists of
two “maximum “forward voltage emitters and
two “typical” forward voltage emitters. Due to
potential variations in luminous flux output at
low currents, Lumileds Lighting recommends
a minimum forward current of 20 mA for
11
luminous intensity variations even using LED
emitters from the same forward voltage and
luminous flux category. Figure 3.5 shows the
worst-case forward current variations within the
LED array when the array is constructed using
LED emitters from the same forward voltage
category. The worst-case calculations assume
that the LED array consists of 16 HPWT-xH00
emitters constructed using four “minimum” LED
emitters, four “maximum” LED emitters, and
eight “typical” LED emitters. Then each
SuperFlux LED emitters from only one forward
voltage category within the same LED array.
paralleled grouping consists of one “max,” one
“min,” and two “typical” LED emitters. The
typical calculations assume that the LED array
consists of 16 HPWT-xH00 emitters
Figure 3.6 Typical EMC Transient Protection Circuits
for LED Signal Lamps.
constructed using two “minimum” LED emitters,
two “maximum” LED emitters, and twelve
“typical” LED emitters. Then two of the
LED emitters are susceptible to permanent
damage due to high voltage automotive EMC
transients. The addition of a high-voltage
silicon diode in series with the LED array can
effectively protect the array from high-voltage
negative transients. The LED array can be
protected from positive “Load Dump”
paralleled groupings consist of one “max,” one
“min,” and two “typical” LED emitters, and the
other two paralleled groupings consist of four
“typical” LED emitters. Lumileds Lighting
recommends a minimum forward current of
35 mA (70 mA for the SnapLED 150), for the
“paralleled-string” circuit in Figure 3.1b or the
“cross-connected parallel-string” circuit
shown in Figure 3.1c. At drive currents less
than 35 mA (70 mA for SnapLED 150), the
“worst-case” forward current variations
between adjacent LED emitters can exceed
2:1. Because of the averaging effects of several
series-connected LED emitters, the circuit in
Figure 3.1b has somewhat lower typical forward
current variations than the circuit shown in
Figure 3.1c. Note that the forward current
matching can be improved with the addition of
a small resistor (ROPT > RS) in series with each
string for the circuit shown in Figure 3.1b or
“rung” for the circuit shown in Figure 3.1c. For
these circuits, it is important to use
transients with the addition of a transient
suppressor connected in parallel with the LED
array. Figure 3.6 shows the addition of EMC
protection circuitry to the LED array. EMC
transient protection is covered in more detail in
the following section “EMC Transient Protection.”
Some applications require the LED array to
operate at two levels of luminous intensity (i.e.
a rear Stop/ Tail signal). Generally, it is desirable
that the LED emitters should appear matched at
both drive conditions. SuperFlux and SnapLED
70 emitters are categorized for luminous flux at
70 mA (150 mA for the SnapLED 150). As shown
in the section “Electrical, Optical, and Thermal
Characteristics of LED Emitters,” the light output
matching for random combinations of LED
emitters gets progressively worse at lower
12
forward currents. For SuperFlux and SnapLED
emitters, the light output varies by a factor of
2:1 at a forward current of 20 mA (40 mA for
the SnapLED 150). Thus, even if all of the LED
emitters are driven at the same forward current,
there would likely be unacceptable light output
matching if the Tail signal is driven at a low DC
forward current.
reduced luminous intensity. The Stop signal
might operate the LED array at a high DC
forward current. Then for the Tail signal, the
array would be operated at the same peak
forward current with a low duty cycle (ratio of
“on” time to “on” plus “off” time). This
approach provides light output matching under
both levels of luminous intensity. A
recommended PWM circuit is shown in the
section “Special Considerations for Dual
Luminous Intensity Operation.”
For best matching, it is recommended that a
pulse width modulation (PWM) circuit be
designed to operate the signal lamp at
Theory
Overview of Electrical, Optical, and
Thermal Characteristics of an LED Emitter
In order to properly design an LED signal light,
it is important to have a basic understanding
of the electrical, optical, and thermal
the incremental forward voltage. Although this
graph has been used traditionally to describe the
forward characteristics of a diode, in reality LED
emitters are best thought of as current controlled
devices, not voltage controlled devices. For an
LED emitter, the optical properties are best
described as a function of current, not a function
of voltage. In addition, operation of the LED
emitter at a constant current gives the best
control of light output. In contrast, operation of
the LED emitter at a constant voltage allows a
larger variation in forward current and light output
from device to device.
characteristics of an LED emitter.
The typical forward current (IF) versus forward
voltage (VF) characteristic for an AlInGaP LED
emitter under positive (forward) bias is shown in
Figure 3.7. On a linear scale of forward current
versus forward voltage, negligible current flows
until a threshold voltage, also known as the
turn-on voltage (VO), is exceeded. Above this
voltage, the current increases proportionally to
Figure 3.7 Typical Forward Current versus
Forward Voltage for HPWA-xHOO LET Emitter
(Linear Scale).
Figure 3.8 Typical Forward Current versus Forward
Voltage for HPWA-xHOO LED Emitter (Semi-Long
Scale.)
13
The low-current forward characteristics of the
same AlInGaP LED emitter are shown in Figure
3.8. This graph shows the forward voltage
versus the log of forward current. Note that a
small current flows through the emitter even at
low forward voltages below the turn-on voltage
shown in Figure 3.7. Due to the high optical
efficiency of AlInGaP material, a perceptible
amount of light is generated from the LED
emitters at forward currents as low as 10 mA.
Thus the inadvertent operation at low forward
currents can cause “ghosting” within an “off”
LED signal light.
HPWT-xx00 emitters. Operation of the LED
emitter in the reverse current region is not
recommended. Reverse currents in excess of 50
mA can cause permanent damage to the LED
junction, as discussed later in the section titled
“Electrical Transients.” The reverse breakdown
voltage is essentially constant over the –40ºC to
100ºC temperature range.
The change in luminous flux (FV) as a function of
forward current (IF) of an AlInGaP LED emitter is
shown in Figure 3.10. Note that the change in
luminous flux is roughly proportional to the
change in forward current. At forward currents
over 20 mA, the luminous flux increases at a
lower rate due to internal heating within the LED
emitter. The change in luminous flux due to a
change in forward current ( DFV / DIF) varies
somewhat from unit to unit. Figure 3.11 shows
the expected range in light output for HPWT-
xH00 emitters that were matched at 70 mA.
Note that the light output varies by a factor of 2:1
at a 20 mA forward current. Since the SnapLED
150 emitter is matched at 150 mA, then the light
output can be expected to vary by a factor of 2:1
at a forward current of 40 mA.
The forward voltage of an AlInGaP LED emitter
changes by about –2 mV per °C over
temperature. Thus, the forward voltage at a
given current is slightly lower at elevated
temperatures and slightly higher at colder
temperatures.
The reverse characteristics of an AlInGaP LED
emitter are shown in Figure 3.9. Note that a
negligible amount of reverse current (< 1 mA)
flows through the LED until the reverse
breakdown voltage is reached. The reverse
current increases quickly at voltages higher than
the reverse breakdown voltage (defined as the
voltage across the LED at which the reverse
current reaches 100 mA). The reverse
The luminous flux of an AlInGaP LED emitter
varies inversely with temperature as shown in
Figure 3.12.
breakdown voltage for AlInGaP LED emitters is
typically in the range of 20 V. However, it can
be as low as 10 V for the HPWA-xx00 and
14
Figure 3.9 Typical Reverse Current versus
Reverse Voltage for HPWA-xHOO LED Emitter
(Linear Scale).
Figure 3.10 Typical Luminous Flux versus
Forward Current for HPWA-xHOO LED Emitter
(Logarithmic Scale).
At 85°C, the light output will be approximately
50% of the light output at 25°C. At –40°C, the
light output will be approximately twice the light
output at 25°C. This change is fully reversible.
and dominant wavelength over temperature are
fully reversible when the ambient temperature
returns to 25ºC.
As might be expected, the junction temperature
varies directly as a function of ambient
The peak and dominant wavelength of an
AlInGaP LED emitter changes by about 0.1 nm
per ºC. Thus, the color of the LED shifts slightly
toward the red at elevated temperatures.
temperature. In addition, the junction
temperature of the LED emitter is hotter than the
surrounding ambient temperature due to the
internal power dissipation (IFVF) within the LED
emitter. Figure 3.13 shows the internal
By now, it should be apparent that a number of
the electrical and optical characteristics of an
LED emitter vary as a function of ambient and
junction temperature. All of these changes in
forward voltage, luminous intensity, and peak
temperature rise, TJ – TA, for an LED signal lamp
over a range of thermal resistance, as a function
of the forward current through the LED emitter.
Figure 3.11 Expected Variations in Luminous Flux
versus Forward Current for HPWT-xHOO LED
Emitters (Logarithmic Scale).
Figure 3.12 Typical Luminous Flux versus
Temperature for HPWT-xHOO LED Emitter
Driven at 60 mA (Linear Scale).
15
Figure 3.13 Expected Internal Temperature Rise
(TJ -TA) for HPWA-xHOO LED Emitter versus
Forward Current (Linear Scale).
Figure 3.14 Straight-Line Forward Voltage Model
for LED Emitter (Linear Scale).
Besides affecting a number of the electrical and
optical parameters, the junction temperature
and maximum operating current also affect the
reliability of the LED emitter. For AlInGaP
SuperFlux LED emitters, operation of the emitter
near the maximum operating temperature limit
and maximum operating current limit can result
in a small amount of light degradation over time.
In addition, due to the different rates of thermal
expansion of the epoxy material used for the
emitter package and the metal pins and gold
bond-wire within the LED emitter, there are
upper and lower limits to the operating and
storage temperature ranges for each LED
package. Exceeding these limits, especially for
hundred’s of temperature cycles, can result in
premature catastrophic LED emitter failures.
These effects are covered in detail in AB20-6,
titled “Reliability Considerations for SuperFlux
LEDs.”
For these reasons, it is important to understand
the thermal properties of the individual LED
emitter as well as the thermal properties of all the
elements of the LED signal lamp (printed circuit
board, case, etc). AB20-4, titled “Thermal
Management Considerations for SuperFlux
LEDs” discusses the proper thermal design of an
LED signal lamp. In this application note, thermal
modeling will be covered only in sufficient detail
so as to allow proper circuit modeling to maintain
the LED junction temperature within the
recommended operating temperature limits. This
application note will also use thermal modeling to
estimate the change in electrical and optical
parameters of the LED emitters over temperature
and how these effect the operation of the LED
signal light. For additional detail on thermal
modeling please refer to AB20-4.
LED Emitter Modeling
The purpose of modeling is to represent the
electrical, optical, and thermal characteristics of
a component with equations that allow their
interactions with other electronic components to
be expressed mathematically. The process of
modeling also requires that mathematical
16
expressions be selected that best approximate
the actual measured data.
Thus, the equations for VO and RS can be written
as:
For operation over a restricted range of current,
say from 30 mA to 70 mA, the forward current
can be modeled with a linear model. As shown
in Figure 3.14, the linear model draws a straight
line between two points (IF1, VF1) and (IF2, VF2) at
two forward currents, IF1 < IF2, to linearize the
electrical forward characteristics between these
forward currents. The linear model is shown
graphically in Figure 3.15 for the forward voltage
versus forward current curve shown in Figure
3.7. The equation for the forward current
becomes:
For most applications this linear model can be
used to model the forward characteristics of an
LED emitter. For best accuracy, the use of the
linear model should be restricted to a range of
forward currents, IF2 / IF1, less than 4:1. For
operation at a lower range of currents, different
points (IF3, VF3) and (IF4, VF4) can be selected to
bracket the approximate range of operating
current. However, it’s always important to
recognize that the linear model only works for
a specified range of forward currents (IF1 £?IF
£?IF2) as the accuracy of the linear model
degrades quickly outside of this range. It
should go without saying that the linear model
cannot be used at all for values of VF < VO.
Where:
VO = turn-on voltage, the y-intercept of the
straight line (IF = 0)
RS = series resistance, the slope of the straight
line
Figure 3.15 Linear Forward Voltage Model for
HPWA-xHOO LED Emitter Shown in Figure 7.
Figure 3.16 Worst-Case Linear Forward Voltage
Models for LED Emitters.
17
Using the nominal forward voltage at the two
test currents in Equations #3.4 and #3.5 would
generate the typical linear forward voltage
model as shown below. The nominal linear
forward voltage model (VO nom and RS nom) is
based on the average forward voltages at two
test currents, IF1 and IF2, for a large number of
SuperFlux LED emitters from the same forward
voltage category.
estimated with two permutations of the linear
model as shown in Figure 3.16:
VF min = VO LL + RS LL IF @ VO min + RS min IF
VF max = VO HH + RS HH IF @ VO max + RS max IF
In order to model the variation in electrical
forward characteristics over temperature,
another term can be added to the linear model
as shown in Equation #3.6. Note that the data
shown in AB20-3B represents the forward
voltage at 25°C with the units measured cold (i.e.
TJ = 25°C). Thus, the thermally stabilized forward
voltage at 25°C will be slightly lower than the
values shown in AB20-3B.
(IF1, VF1 nom), (IF2, VF2 nom) Þ ( VO nom, RS nom
)
Then:
VF nom = VO nom + RS nom IF
The values of VF(IF1) and VF(IF2) vary for different
SuperFlux LED emitters from the same forward
voltage category. Statistical forward voltage
data for SuperFlux LED emitters is given in
AB20-3B. Then, the values of VO and RS can be
calculated using the desired limits (i.e. VF max, VF
min, or VF average ± n s ). Worst-case circuit analysis
is concerned primarily with the highest and
lowest forward voltages over the range of IF1 £ IF
£ IF2. In most cases, the worst-case range of
forward current and forward voltage can be
Where:
TJ
= junction temperature, °C
D VF /D = change in VF due to temperature,
@ –2mV°C
VO, RS = measured at a junction temperature
of 25°C
Figure 3.17 Linear Model (m = 1) for
Luminous Flux versus Forward Current for
HPWA-xHOO LED Emitter Shown in Figure
3.10.
Figure 3.18 Exponential Model (k = -0.0110)
and Exponential Curve Fit (k = -0.0096) for
Luminous Flux versus Temperature for
HPWA-xHOO LED Emitter Shown in
Figure 3.12.
18
In general, the luminous flux output of LED
emitters varies as a function of the forward
current. Ignoring the effect of heating, the
relationship between luminous flux and forward
current can be modeled with the following
equation:
FV (TJ ) = luminous flux at forward current IF at
junction temperature, TJ
FV (TJ = 25°C) = luminous flux at 25°C, without
heating
k
= thermal coefficient, k @ –0.01
(3.7)
Over the automotive operating temperature
range of –40°C to 85°C, this model matches the
actual data within ± 10%. Figure 3.18 shows
how the modeled data for FV as a function of
temperature compares to the actual data shown
in Figure 3.12. Note that the value selected for k
was chosen to improve the curve fit at elevated
temperatures than at temperatures below 25°C.
Typical values of k for AlInGaP and TS AlGaAs
SuperFlux LED emitters are shown in Table 3.1.
m
FV(IF,TJ = 25°C) @ F V(IF TEST,TJ = 25°C)[IF/IF TEST
]
Where:
FV(IF,TJ = 25°C) = Luminous flux at forward
current, IF, ignoring heating
F (IF TEST,TJ = 25°C) = Luminous flux at test
V
current, IF TEST, ignoring heating
= forward current
IF
I
F TEST = forward current at data sheet test
conditions
m
= linearity factor, 1 £ m £ 2
Thermal resistance is a measurement of the
temperature rise within the LED signal lamp
caused by internal power dissipation as well as
other sources of heat in close proximity to the
LED (i.e. bulbs, resistors, drive transistors, etc).
For a detailed discussion of thermal resistance,
please refer to AB20-4. The units of thermal
resistance are ºC/W. For the same power
dissipation, the LED signal lamp with a higher
thermal resistance would have a larger internal
temperature rise. The basic thermal modeling
equation is shown below:
At forward currents less than 10 mA, m » 1.3 for
AlInGaP LED emitters. At forward currents over
30 mA, the linearity factor, m » 1.0 for AlInGaP
LED emitters. Figure 3.17 shows how the
modeled data for FV versus IF compares to the
actual data shown in Figure 3.10.
For operation at forward currents over 30 mA,
Equation #3.7 can be simplified into a simple
linear equation:
FV(IF, TJ = 25°C) @ FV (IF TEST , TJ = 25°C)[ IF / IF
TJ @ TA + RqJAPD
(3.9)
]
TEST
Where:
The luminous flux varies exponentially with
TJ = internal junction temperature within the LED
emitter, °C
temperature. The simplest model is shown
below:
TA = ambient temperature surrounding the LED
signal lamp, °C
(3.8)
FV(TJ ) @ F V(TJ = 25°C) exp [k(TJ -25°C)]
Where:
RqJA = thermal resistance, junction to ambient,
°C/W
19
PD = internal power dissipation within the LED
LED signal lamps typically use several LED
emitters. Each LED has a slightly different
thermal resistance, based on the proximity of
other heat sources (e.g. adjacent LED emitters,
resistors, power transistors, bulbs, etc) and
printed circuit board layout. Generally, the
thermal resistance value used for thermal
modeling is the highest thermal resistance,
RqJA, of any of the LED emitters within the LED
lamp assembly. Experience has shown that the
LED emitter with the highest thermal resistance
is usually either one of the emitters in the center
of the LED lamp assembly for an x-y
emitter (IF VF),W
Where:
Rq JP = thermal resistance, junction to pin (LED
emitter package), °C/W
Rq PA
= thermal resistance pin to air (printed
circuit and case), °C/W
TP = LED cathode pin temperature on
underside of printed circuit board, °C
These equations are especially useful since the
thermal resistance junction to pin, RqJP, is
specified on the product data sheet and the LED
pin temperature can be measured directly by
attaching a thermocouple on the cathode lead of
the LED emitter on the underside of the printed
circuit board. Thus the junction temperature can
be estimated based on a measurement of the pin
temperature of the LED emitter (please refer to
AB20-4).
arrangement of emitters, the middle emitter in a
single row of emitters, or one of the emitters
adjacent to other heat sources (e.g. resistors,
power transistors, bulbs, etc).
The thermal modeling equation can be further
broken down by separately considering the
thermal resistance of each of the elements of
the LED signal lamp as shown below:
Usually thermal resistance measurements are
done at thermal equilibrium. For an LED signal
lamp, thermal equilibrium usually occurs after
30 minutes of continuous operation. In some
cases, it is important to calculate the junction
temperature under a transient condition
(e.g. 2 minutes at 24 V).
TJ @ TA + (Rq JP + RqPA) PD
TP @ TA + (Rq PA) PD
(3.10)
Table 3.1
Values of k for AlInGaP SuperFlux LED Emitters
Coefficient of
Dominant
Family
LED Material
Wavelength
F V, ( T ), k
HPWA-xHOO
HPWA-xLOO
HPWT-xDOO
HPWT-xHOO
HPWT-xLOO
AS AlInGaP
AS AlInGaP
TS AlInGaP
TS AlInGaP
TS AlInGaP
618 nm
592 nm
630 nm
620 nm
594 nm
-0.0106
-0.0175
-0.0106
-0.0106
-0.0175
20
This can be done by further subdividing the
thermal modeling equation as shown below:
die will be the first element of the model to heat-
up, followed by the LED emitter package, and
then the rest of the LED signal light.
TJ @ TA + (RqJ LF + RqLF P + RqP A) PD (3.11)
This section discussed the key concepts of
modeling the electrical, optical, and thermal
performance of LED signal lights. Equations #3.3
and #3.7 can be used to model the operation of
an LED emitter at room temperature, ignoring
the effects of self-heating. Equations #3.6, #3.7,
#3.8, and #3.9 can be used together to model
the effects of self-heating of an LED emitter at
room temperature as well as to model the
operation of an LED emitter over temperature.
Equations #3.10 and #3.11 show the various
components of the overall thermal resistance,
RqJA , which can be useful in the thermal
modeling of an LED signal lamp assembly and
the thermal modeling of transient power
conditions.
Where:
Rq J LF = thermal resistance, junction to lead
frame (LED die), °C/W
Rq LF P = thermal resistance, lead frame to pin
(LED package excluding die), °C/W
Please note that each thermal resistance (Rq J LF
Rq LF P, and Rq P A) has a different heating time
constant. The time constant associated with
heating of the LED die is in the order of one
millisecond. The time constant associated with
the heating of the LED emitter package is in the
order of one minute. The time constant
,
associated with the heating of the complete LED
signal lamp is in the order of 10 to 30 minutes.
Thus, for a transient heating condition, the LED
Applications
Resistive Current Limiting
As discussed previously in the section “Key
Concepts for Electrical Design of LED Signal
Lamps,” the choice of the number of LED
emitters per series-string has a large effect on
the forward current regulation and the overall
electrical power consumption of the LED signal
lamp. Most 12V designs commonly use either
three or four emitters per series-string, which is
a good balance of current regulation and
electrical power consumption. Then, the choice
of circuit topology (Figure 3.1 circuits) and the
design current determine the variation in
if the LED signal light will be subjected to
automotive EMC transients.
For a resistive current-limited circuit the electrical
design process consists mainly of picking the
proper value(s) for the current limiting resistor(s).
The key principles of worst-case design are
shown in Figure 3.19. The figure shows the
forward current through one LED string of four
emitters as a function of input voltage. The
equation for this graph (Equation #3.12) is equal
to Equation #3.2 solved for IF:
forward currents for the LED emitters in the
array. Finally, protection circuitry can be added,
Equation #3.2, from “Key Concepts for Electrical
Design of LED Signal Lamps.”
21
#3.12, for the same value of external current
limiting resistor, R.
The maximum forward current through the LED
string is determined by the effects of thermal
resistance of the LED signal lamp, RqJA, and
maximum ambient temperature, TA MAX, as shown
in Figure 4 of the SuperFlux LED Data Sheet.
Where:
R = external current limiting resistor
VIN = input voltage applied to the circuit
VD = voltage drop across optional reverse
transient EMC protection diode
IF = design forward current through the circuit
VO = turn-on voltage of the linear forward
voltage model
So, the worst-case design procedure is to
determine the maximum forward current, IF MAX
,
based on parameters RqJA and TA MAX from Figure
4 of the SuperFlux LED Data Sheet. Then the
value of the external resistor, R, is determined
RS = series resistance of the linear forward
voltage model
y = number of series connected LED emitters
x = number of paralleled strings used with
external current limiting resistor
with Equation #3.2, using values of IF MAX, VIN MAX
and LED linear model parameters (VO LL, RS LL).
,
The nominal design current, IF DES, which occurs
at the design voltage, VIN DES, can be calculated
with Equation #3.12 using values of VIN DES, R,
and LED emitters with a typical forward voltage
[i.e. with linear model parameters (VO NOM, RS NOM).
In practice, the LED signal lamp needs to be
designed to accommodate a range of forward
voltage categories and luminous flux categories.
In most cases, the overall goal is to design an
LED signal lamp with a fixed light output. For
LED emitters from the same luminous flux
category, this can be accomplished by
Figure 3.19 Worst-Case Variations in Forward
Current Through Several LED Strings as a
Function of the Applied Voltage.
calculating different values of external resistor, R,
using Equation #3.2, with the same design
current and voltage, IF DES and VIN DES, and using
the nominal forward voltage models (VO NOM, RS
NOM) for each forward voltage category.
Note, for the example shown in this section:
x = 1 and y = 4.
Figure 3.19 shows how the variation in forward
voltage of the LED emitters affects the forward
current through the string. These curves are
generated by substituting the worst-case linear
forward voltage model parameters [(VO NOM, RS
NOM), (VO LL, RS LL), or (VO HH, RS HH)] into Equation
For LED emitters with higher luminous flux
categories, the design current would be reduced
to keep the light output constant. First, the
minimum luminous flux would be calculated for
the lowest expected luminous flux category at
22
the nominal design current. Then Figure 3 from
the SuperFlux LED Data Sheet could be used to
calculate the other design currents for higher
luminous flux categories. Then values of
design. Lumileds Lighting recommends that the
designer use realistic assumptions for these
parameters. It is very easy to overly guard-band
these assumptions, which results in an excessive
estimate of the number of LED emitters needed.
external resistor, R, can be calculated with
Equation #3.2 at the reduced design current
using the appropriate nominal forward voltage
models for each forward voltage category.
The luminous efficiency of AlInGaP technology
has significantly improved over the past few
years. Please consult with your Lumileds Lighting
or Agilent Technologies Field Sales Engineer for
the recommended minimum luminous flux
categories of SuperFlux LED emitters for given
future production dates.
After all of these “ideal” values of R are
computed, the designer would need to choose
the closest standard resistor values. In many
cases, the designer can use the same resistor
value for multiple LED emitter categories
provided that the maximum forward current is
not exceeded under worst-case conditions.
Many LED signal lamp requirements also include
operation at higher voltages for a limited duration
(i.e. 24 volts for two minutes). In analyzing the
performance of an LED signal lamp under these
conditions, it is important to analyze the transient
heating effects. Under these conditions the LED
emitters don’t reach thermal equilibrium so the
junction temperatures are lower than indicated
by Equation #3.9. Equation #3.11 can be used
to estimate the maximum junction temperature
Experience has shown that the worst-case
design occurs with the lowest expected
luminous flux category and the highest forward
voltage category. Thus, the lowest value of
external resistor, R, and the highest design
current, IF DES, would be determined for this
particular category combination. For LED
emitters with the lowest expected luminous flux
category and lower forward voltage categories,
Equation #3.2 will generate higher values of R.
For LED emitters with higher luminous flux
categories, the values of R will be even larger
since the design current is reduced.
using the appropriate time constants for RqJ LF
RqLF P, and RqP A. In addition, many test
specifications allow a different operating
temperature for these tests.
,
The assumptions used for maximum ambient
temperature, RqJA, maximum steady-state input
voltage, and the worst-case SuperFlux LED
categories (minimum expected luminous flux
and maximum expected forward voltage) have a
large effect on the nominal design current and
thus the luminous flux output. Thus these
parameters have a large effect on the number of
LED emitters needed for a given signal lamp
23
CHMSL Design Example
This worst-case design procedure will be
illustrated with an example. Let suppose that an
LED array is being designed using 4-LED
strings of HPWT-MH00 from luminous flux
categories F through L and forward voltage
categories 2 through 6. For this example RqJA =
350° C/W, TA MAX = 70° C, VIN MAX = 15.0 V, and
VIN DES = 12.8 V. In addition, a silicon diode with
a forward voltage of 0.8 V is connected in series
with the circuit in order to provide protection
against negative EMC transients. Then, the
design steps are shown below:
For HPWT-MH00, forward voltage category 6:
VO LL = 1.85 V, RS LL = 14.4 ohm
Then:
3. Determine nominal design current, IF DES
:
The nominal forward current through the LED
emitters at the design voltage is determined with
Equation #3.12. The equation should use the
value of R from the Step 2 at the design voltage
and the nominal forward voltage of the SuperFlux
LED emitters using the same forward voltage
category used in Step 2.
1. Determine IF MAX
:
The maximum allowable DC forward current
through the SuperFlux LED emitters is
determined from the maximum ambient
temperature, TA MAX, estimated overall thermal
resistance, RqJA, of the LED signal lamp, and
Figure 4 of the Data Sheet.
For HPWT-MH00, forward voltage category 6:
VO NOM = 2.03 V, RS NOM = 12.4 ohm
For TA MAX = 70° C, and RqJA = 350° C/W:
Then: IF MAX = 55 mA, from HPWT-MH00
DataSheet, Figure 4
2. Determine minimum value of current limiting
resistor, R:
The minimum value of R is determined with
Equation #3.2 at the maximum input voltage
and maximum forward current from Step 1 for
the maximum forward voltage category Super
Flux LED to be used in the assembly.
24
4. Determine value of external current limiting
The linear forward voltage models for the other
HPWT-MH00 forward voltage categories are
shown below:
resistor, R, for each forward voltage category:
For SuperFlux LED emitters from lower forward
voltage categories, the value of the external
resistor, R, will need to be increased (using
Equation #3.2) in order to maintain the same
nominal forward current.
HPWT-
MHOO
Voltage
Category 2
Voltage
Category 3
Voltage
Category 4
Voltage
Category 5
Voltage
Category 6
VO
RS
=
=
1.87 V
8.2 ohm
1.91 V
9.2 ohm
1.94 V
10.5 ohm
1.96 V
11.6 ohm
2.03 V
12.4 ohm
NOM
NOM
For VIN DES = 12.8 V, VD = 0.8 V, IF DES = 33.6 mA, x = 1, y = 4:
HPWT-
MHOO
Voltage
Category 2
Voltage
Category 3
Voltage
Category 4
Voltage
Category 5
Voltage
Category 6
R =
102 ohm
93 ohm
84 ohm
77 ohm
66 ohm
5. Determine minimum thermally stabilized
luminous flux:
Design currents for SuperFlux LED emitters at
higher luminous flux categories can be
determined using Figure 3 from the SuperFlux
LED Data Sheet. This can be done by computing
a new “relative luminous flux” equal to the
desired luminous flux divided by the minimum
luminous flux category bin limit and then reading
a new value of forward current from Figure 3.
The thermally stabilized luminous flux of the
SuperFlux LED emitters from the lowest
expected luminous flux category can be
determined using Figure 3 from the SuperFlux
LED Data Sheet.
For HPWT-MH00, luminous flux category F (3.0
lm minimum) and IF DES = 33.6 mA:
The same minimum luminous flux obtained from
a HPWT-MH00 luminous flux category F (3.0 lm)
driven at 33.6 mA can be obtained from a
HPWT-MH00 from the following luminous flux
categories when driven at the specified forward
current:
Then: F V MIN = (3.0)(0.54) = 1.62 lm, (i.e. “relative
luminous flux” = 0.54) from HPWT-MH00 Data
Sheet, Figure 3
6. Determine design currents for brighter
SuperFlux LED emitters:
25
From Figure 3, HPWT-MH00 Data Sheet:
Luminous Flux Category
F
G
H
J
L
Minimum Luminous Flux
Desired “relative luminous flux”
Design Current, from Figure 3
3.0 lm
0.54
33.6 mA
3.5 lm
0.46
29 mA
4.0 lm
0.41
25 mA
5.0 lm
0.32
19 mA
6.0 lm
0.27
15 mA
Note: Due to the variations in forward voltage at
low currents, there is a practical limit to the use
of higher and higher luminous flux categories at
correspondingly lower dc drive currents. For the
series string circuit shown in Figure 3.1a, at
drive currents less than 20 mA, the “worst-
case” ratio of forward currents between two
strings of LED emitters can vary by over 2:1. As
shown by this example, in order to achieve the
same light output for all CHMSL arrays, designs
using HPWT-MH00 emitters from luminous flux
categories J and L would require drive currents
less than 20 mA. Thus, the designer needs to
establish whether it is better to limit the forward
current to 20 mA and allow the light output to
increase for these brighter luminous flux
categories, or to accept possible visible light
output mismatch within the array.
7. Determine values of R for expected luminous
flux and forward voltage categories:
Values of R can be determined (using Equation
#3.2) for each SuperFlux LED emitter forward
voltage category and luminous flux category at
the appropriate design current as calculated in
Step 6.
Note: Since the design current of the HPWT-
MH00 LED array is less than 32 mA for designs
using luminous flux bins G through K, a “low
current” linear forward voltage model (8 mA £ IF
£?32 mA) was used. This model is shown below:
HPWT-
MHOO
Voltage
Category 2
Voltage
Category 3
Voltage
Category 4
Voltage
Category 5
Voltage
Category 6
VO
RS
=
=
1.80 V
10.4 ohm
1.83 V
11.7 ohm
1.85 V
13.2 ohm
1.88 V
14.3 ohm
1.94 V
15.1 ohm
NOM
NOM
For VIN DES = 12.8 V, VD = 0.8 V, IF DES from Step 6, VO NOM, RS NOM, x = 1, y = 4:
HPWT-
MHOO
Design
Current
Voltage
Category 2
Voltage
Category 3
Voltage
Voltage
Voltage
Category 4 Category 5 Category 6
Flux, F
Flux, G
Flux, H
Flux, J
Flux, K
33.6 mA
29 mA
102 ohm
124 ohm
151 ohm
212 ohm
279 ohm
93 ohm
115 ohm
140 ohm
199 ohm
265 ohm
84 ohm
106 ohm
131 ohm
189 ohm
253 ohm
77 ohm
97 ohm
122 ohm
179 ohm
242 ohm
66 ohm
86 ohm
109 ohm
162 ohm
222 ohm
25 mA
19 mA[1]
15 mA[1]
Note 1: Operation at dc drive currents below 20 mA can cause noticeable light output differences within
the LED array.
26
8. Select “standard” resistor values:
Standard 5% Tolerance Resistors
HPWT-
MHOO
Design
Current
Voltage
Category 2
Voltage
Category 3
Voltage
Voltage
Voltage
Category 4 Category 5 Category 6
Flux, F
Flux, G
Flux, H
Flux, J
Flux, K
33.6 mA
29 mA
100 ohm
120 ohm
150 ohm
220 ohm
270 ohm
91 ohm
110 ohm
150 ohm
200 ohm
270 ohm
82 ohm
110 ohm
130 ohm
180 ohm
240 ohm
75 ohm
100 ohm
120 ohm
180 ohm
240 ohm
68 ohm
91 ohm
110 ohm
160 ohm
220 ohm
25 mA
19 mA[1]
15 mA[1]
Note 1: Operation at dc drive currents below 20 mA can cause noticeable light output differences within
the LED array.
9. Group “standard” adjacent cells in resistor matrix in Step 8 as desired:
Standard 5% Tolerance Resistors
HPWT-
MHOO
Design
Current
Voltage
Category 2
Voltage
Category 3
Voltage
Voltage
Voltage
Category 4 Category 5 Category 6
Flux, F
Flux, G
Flux, H
Flux, J
Flux, K
33.6 mA
29 mA
100 ohm
82 ohm
110 ohm
130 ohm
180 ohm
240 ohm
120 ohm
150 ohm
220 ohm
270 ohm
25 mA
19 mA[1]
15 mA[1]
Note 1: Operation at dc drive currents below 20 mA can cause noticeable light output differences within
the LED array.
10. Perform “worst-case” analysis to ensure
that maximum forward current is not exceeded
over temperature.
varies slightly over temperature as shown in
Equation #3.6. This thermal effect can be
included in Equation #3.12 as shown below:
Calculate maximum forward current (using
Equation #3.12) at “worst-case” conditions—
i.e. maximum input voltage, minimum resistor
values, and minimum forward voltages for each
SuperFlux LED emitter forward voltage
category. The forward voltage of LED emitters
EMC Transient Protection
Circuits designed for the automotive electrical
environment must be able to operate over a
wide range of input voltages and be able to
tolerate a number of different types of electrical
transients. These worst-case voltage ranges and
electrical transients have been characterized and
27
are defined in different automotive specifications
such as:
are turned off within the vehicle, switching
transients of electronic circuitry, alternator field
decay, or a fully discharged battery being
disconnected while the alternator is operating at
rated load. These transients consist of both
positive and negative pulses with different
amplitudes and decay times.
DIN 40839 Part 1
“Electromagnetic Compatibility (EMC) in Motor
Vehicles; interferences conducted along supply
lines in 12 V onboard system”
DIN 40839 Part 2
Limited reliability testing has been done with
AlInGaP LED emitters connected in typical LED
signal lamp configurations.
“Electromagnetic Compatibility (EMC) in Motor
Vehicles; interferences conducted along supply
lines in 24 V onboard system”
High-voltage negative transients in excess of the
reverse breakdown voltage can permanently
damage AlInGaP LED emitters. Sufficient energy
can be dissipated within the AlInGaP LED die to
cause localized damage to the p-n diode
structure. This damage can result in reduced
breakdown voltages, and degraded low-current
performance. Under extreme conditions, high
voltage negative transients can even destroy the
p-n junction, resulting in a short between anode
and cathode.
ISO 7647-1
“Road Vehicles—Electrical Disturbance Caused
by Conduction and Coupling; passenger cars
and light commercial vehicles with nominal 12 V
supply voltage”
ISO 7647-2
“Road Vehicles—Electrical Disturbance Caused
by Conduction and Coupling; commercial
vehicles with nominal 24 V supply voltage”
SAE J1113
Adding a high-voltage silicon diode in series with
the LED signal light array, such as previously
shown in Figure 3.6, can prevent potential
damage to high voltage negative transients. The
silicon diode should have a higher reverse
breakdown voltage than the amplitude of the
worst-case negative transient, which can be as
large as –300 V (–600 V for heavy trucks). Table
3.2 shows several recommended silicon diodes
for different LED signal lamp applications.
“Electromagnetic Susceptibility Measurement
Procedures for Vehicle Components (except
Aircraft)”
SAE J1211
“Recommended Environmental Practices for
Electronic Equipment Design”
SAE J1812
“Function Performance Status for EMC
Susceptibility Testing of Automotive Electronic
and Electrical Devices”
In addition, high-voltage positive transients can
permanently damage AlInGaP LED emitters.
Sufficient energy can be dissipated within the
AlInGaP LED die to cause permanent damage to
the p-n diode structure and cause epoxy
These specifications define several electrical
transient pulses that occur when inductive loads
28
delamination between the LED and surrounding
epoxy. Under extreme conditions, the epoxy
surrounding the LED die can be charred and
the gold bond wire and LED die can be
destroyed, resulting in an open circuit. The
AlInGaP LED die can tolerate non-recurring
peak current transients of several hundred
milliamperes for short time periods (t << 1 ms)
with minimal permanent effects. However,
longer transients can cause sufficient localized
heating to cause the various effects listed
earlier. The “Load Dump” transient pulse can be
especially damaging since the pulse duration
can be up to 400 ms.
limiting properties of the LED drive circuit,
determine the maximum peak current through
the LED array. For best results, the breakdown
voltage of the transient suppressor should fall
within the following range:
24 V < VBR < 45 V
Note that the 24 V restriction is determined by
the “Jump Start” voltage condition. The 45 V
restriction is determined by the ability of the LED
array to withstand the peak current imposed by
the transient voltage. Since the 45 V limit
depends on the circuit topography of the LED
array and the maximum “Load Dump” transient
pulse duration, this voltage limit should be
established by reliability testing.
The effects of “Load Dump” transients can be
minimized by putting a surge-suppressor or
silicon transient suppressor in parallel with the
LED array as previously shown in Figure 3.6.
Note that the breakdown voltage of the
transient suppressor, as well as the current-
Table 3.2
Silicon Diodes for EMC Negative Transient Protection
Diode Part
Number
Maximum Continuous
Reverse Breakdown
Forward Current, IO
Voltage, VRRM
Applications
1N4005
1N5396
1N5406
1.0 A
1.5 A
3.0 A
600 V
600 V
600 V
CHMSL
Rear Combination Lamp
Rear Combination lamp,
& Front Turn Signal
Special Considerations for Dual Luminous Intensity Operation
Some applications, such as a Stop/Tail signal
lamp require two discrete levels of light output.
These applications require some additional
design considerations. In most cases, the ratios
in light output at the two signal conditions are
determined by the various signal lamp
ratios for Stop/Tail signals are 7:1 to 15:1.
Generally, the LED emitters should appear
matched in luminous flux at both drive
conditions. This implies that the forward currents
for the LED emitters in the array should be
matched at both drive currents. SuperFlux and
SnapLED 70 emitters are categorized for
specifications or regulations. Typical dimming
29
luminous flux and forward voltage at 70 mA
(150 mA for the SnapLED 150). Thus, their
matching is best when driven at high forward
currents. As discussed in the section “Electrical,
Optical, and Thermal Properties of an LED
Emitter,” Figure 3.11 shows the expected range
in light output for HPWT-xH00 emitters that are
matched at 70 mA. Note that the light output
varies by approximately 2:1 at a 20 mA forward
current. Note that since the SnapLED 150 is
matched at 150 mA, then the light output would
vary by about 2:1 at 40 mA. Thus, even if a
well-controlled constant current circuit drives
the LED emitters, the light output matching
might be unacceptable for the Tail function if
driven by a low DC forward current.
Figure 3.20 shows a PWM Tail circuit. When the
input voltage is applied to the Stop pin, the
cross-connected paralleled string circuit is
operated at a dc forward current determined
external resistor, RSTOP. The value for RSTOP can be
determined using Equation #3.2. When the input
voltage is applied to the Tail pin, the NE555
oscillator is energized. Resistors, R1 and R2, and
capacitor, C1, determine the frequency and duty
cycle of the oscillator. The values shown
generate a 2K Hz frequency and a 10% duty
cycle (output low). When the output of the
NE555 (pin 3) is low, a high-current switching
transistor is turned-on, which supplies current to
the LED array. External resistor, R TAIL, determines
the peak current of the Tail circuit. The value for
R TAIL can be determined using a similar equation
as used previously for RSTOP and including the
extra voltage drop across the high-current
switching transistor. Thus for the same value of
peak forward current, R TAIL < RSTOP. Diodes D1
and D2 protect the circuit from negative EMC
transients. Zener diode D 3 protects the NE555
from positive EMC transients.
A PWM circuit is recommended for best
luminous intensity matching for the Tail function.
This circuit could drive the LED array at a high
forward current for the Stop function and drive
the LED array at the same peak forward current
but at a low duty cycle for the Tail function. With
this approach, the matching of the LED array
will be the same regardless of whether the
signal is operating in Stop or Tail mode.
Figure 3.20 Stop/Tail LED
Signal Lamp Circuit that Uses
a PWM Scheme to Generate
the Reduced Light Output of
the Tail Signal.
30
Current and Voltage Regulator Circuits
This section will discuss active circuits that are
designed to drive the LED emitter array at a
constant voltage or constant current despite
input voltage or load variations. These circuits
are called voltage or current regulator circuits
because they are designed to regulate the input
voltage to generate either a fixed output voltage
or current.
and compare the load voltage with a reference
voltage. Current regulator circuits usually
measure the current through the load by
measuring the voltage drop across a “sense”
resistor in series with the load. Then the voltage
across the sense resistor is compared with a
reference voltage.
Since most LED signal lamp designs consist of
several LED emitters, they are normally arranged
in one or more series-connected strings, such as
shown previously in Figure 3.1. While it is
possible to use one voltage or current regulator
per string, due to cost considerations, most
practical designs use a single voltage or current
regulator for the entire LED array. Note that when
only a single regulator is used for the entire array
it is possible to encounter the same type of
forward current variations as described earlier in
the section “Key Concepts for the Electrical
Design of LED Signal Lamps.” Since LED
emitters are current-controlled devices,
voltage regulator circuits should use current-
limiting resistors in series with each string of
LED emitters (Figure 3.1a circuit), paralleled
string of LED emitters (Figure 3.1b circuit), or
cross-connected paralleled string of LED
emitters (Figure 3.1c circuit). For voltage
regulator circuits, Equation #3.2 can be used to
calculate the value of the external current-limiting
resistor(s) if the regulated output voltage, VOUT, is
substituted into the equation for VIN. For current
regulator circuits, external current limiting
resistors are not required but their use can
reduce forward current variations within the LED
array.
The use of voltage or current regulation
improves the operation of the LED signal lamp.
Since the drive current of the LED array remains
constant despite variations in the supply
voltage, the light output is not affected by input
voltage variations. Since the drive current
doesn’t increase due to over voltage conditions,
the LED emitters can be driven at a higher
forward current at the design voltage without
exceeding the maximum allowable forward
current at the maximum input voltage. In
addition, if the circuit is located outside of the
LED signal lamp case, the voltage or current
regulator circuit can improve the thermal
properties of the signal lamp by reducing the
power consumption within the LED signal lamp.
Block diagrams of typical voltage and current
regulator circuits are shown in Figure 3.21. The
basic elements of all of these circuits consist of
a high gain amplifier and feedback circuit, which
vary the dynamic load of a power circuit that is
either in series or parallel with the LED emitter
array. The regulator circuit modulates the
dynamic load so as to provide either a constant
voltage or current to the LED emitter array
independent of input voltage or load variations
(over some specified range). Voltage regulator
circuits measure the voltage across the load
31
As shown in Figure 3.21, there are three basic
types of regulator circuits. The circuits shown in
Figures 3.21a and 3.21d are called “shunt”
regulators. They use a dynamic load in parallel
with the load being regulated that shunts some
of the supply current around the load. Shunt
regulators also have a power resistor in series
with both loads. The value of the power resistor
has been selected such that at the minimum
input voltage and maximum load condition, the
current through the dynamic load goes to zero.
At higher input voltages or smaller loads, the
current through the dynamic load is increased,
which increases the voltage drop across the
power resistor to keep the load current or
voltage constant. In this way, the shunt
due to the large variations in input voltage and
will not be covered further in this section.
The circuits shown in Figures 3.21b and 3.21e
are called “series-pass” regulators. They use a
dynamic load in series with the load being
regulated. At minimum input voltages the voltage
drop across the dynamic load goes to a
minimum value. This minimum voltage drop is
called the “drop-out” voltage. At higher input
voltages, the voltage drop across the dynamic
load increases so as to maintain either a fixed
current or voltage across the load. At voltages
below the drop-out voltage, the dynamic load
can no longer regulate the output voltage or
current. Thus, for proper voltage or current
regulation, the input voltage needs to be higher
than the sum of the drop-out voltage, the voltage
across the load, and the voltage drop across the
sense resistor (if applicable).
regulator maintains either a fixed current or
voltage across the load. Shunt regulators are
not very practical for automotive signal lamps
Figure 3.21 Block Diagrams of Several Active Drive Circuits for LED Signal Lamps.
32
The circuits shown in Figures 3.21c and 3.21f
are called “switching” regulators. They use a
dynamic load that is switched ON and OFF at
very high frequencies at a varying duty cycle.
The dynamic load supplies electrical power to
an energy storage element such as a capacitor
or an inductor or a combination of both. This
energy storage element then supplies power to
the load. The percentage of time the dynamic
load is ON is varied depending on the input
voltage and load requirements. The “switching”
regulator provides the highest power efficiency
of the three circuits. However, it is the most
complex of the three regulator circuits and has
the highest potential for creating unwanted EMI
(due to the high-frequency switching).
circuit shown in Figure 3.1b or “rung” for the
circuit shown in Figure 3.1c.
With a voltage regulator, the forward voltage
applied to the LED array voltage will be
independent of supply voltage variations as long
as the voltage regulator remains in its active
region. However, ambient temperature variations
and the use of different forward voltage
categories can affect the forward current through
the LED array unless provisions are made in the
design. As mentioned earlier, current limiting
resistors, R, are needed for each string of LED
emitters. With R > y DRS, the forward current
through each string will primarily be determined
by the value of R. If the designer uses a voltage
regulator with a fixed output voltage, then the
values of these current-limiting resistors will need
to be varied for each of the different forward
voltage categories in order to compensate for the
different forward voltages at the design current.
Alternatively, the designer could use the same
value of current-limiting resistors for all forward
voltage categories. However, in this case, the
regulator output voltage would need to be varied
slightly for each different forward voltage
The performance of these different types of
regulators is compared with an example shown
in the sidebar “Comparison of Three Constant-
Current Circuits.”
The LED emitter array can be driven from either
a voltage regulator or a current regulator circuit.
With a current regulator, the total array current
will be independent of supply voltage,
temperature and forward voltage category
variations as long as the current regulator
remains in its active region. If the current
regulator is used with parallel-connected LED
emitters, such as shown in Figure 3.1b or 3.1c,
there can still be similar forward current
category to compensate for the different forward
voltages at the design current. Despite these
precautions, there will still be small variations in
the total current through the LED array due to
slightly different forward voltages of the individual
emitters. With only a small voltage drop across
the current limiting resistor, small variations in
the regulated voltage can cause large changes
in forward current through the LED emitters. In
addition, since the forward voltage of the LED
emitter varies with temperature, the forward
current through the LED array will increase at
elevated temperatures. However, it is possible
variations within the LED array as was
discussed in the section “Key Concepts for the
Electrical Design of LED Signal Lamps.” Note
that the forward current matching can be
improved with the addition of a small resistor
(ROPT > RS) in series with each string for the
33
to maintain fixed current through the LED array
if the output voltage of the regulator tracks
the DVF /DT of the LED array (approximately
–2 mV/°C times the number of emitters in each
series string). Finally, if the voltage regulator is
used with parallel-connected LED emitters,
such as shown in Figure 3.1b or 3.1c, there can
still be similar forward current variations within
the LED array as was discussed in the section
“Key Concepts for Electrical Design of LED
Signal Lamps.” Note that the forward current
matching can be improved with the addition of a
small resistor (ROPT > RS) in series with each string
for the circuit shown in Figure 3.1b or “rung” for
the circuit shown in Figure 3.1c.
Comparison of Three Constant-Current Circuits
SETUP:
Suppose an LED signal lamp is being designed
using 30 HPWT-DH00 SuperFlux LED emitters
from forward voltage category 3. The circuit will
be designed to operate at 50 mA per emitter at
a design voltage of 12.8 V.
SOLUTION:
For the first two designs, the value of the external
current limiting resistor, R, can be determined
using Equation #3.2. Note, for forward voltage
category 3, the nominal linear forward voltage
model is VO NOM = 1.91 V, and RS NOM = 9.2 ohm.
Thus, for the three-LED string circuit, R = 114
ohm. For the four-LED string circuit, R = 66 ohm.
The detailed designs are shown in Figure 3.22.
Then over an input voltage range of 7 to 18 volts,
the forward current through each LED string
would vary as shown in Figure 3.23.
PROBLEM STATEMENT:
How does the overall power consumption
compare for the following 4 possible circuit
designs over an input voltage range of 9 V
to 18 V?
1. Resistive current limiting (Figure 3.1a circuit)
with ten strings of three emitters per string.
2. Resistive current limiting (Figure 3.1a circuit)
with eight strings of four emitters per string.
3. Series-pass constant-current regulator
driving ten strings of three emitters per string.
4. Switching constant-current regulator driving
ten strings of three emitters per string.
Figure 3.22 Two LED Signal Lamp Designs Using
Resistive Current Limiting.
34
Figure 3.23 Forward Current Through LED
Emitters as a Function of Applied Voltage
for Resistive Limited Circuits Shown in
Figure 3.22.
Figure 3.24 Block Diagram of LED Signal Lamp Design
Using Series-Pass Constant-Current Regulator.
The key elements of the series pass constant-
current regulator are shown in Figure 3.24. For
series strings of three forward voltage category
3 HPWT-DH00 emitters, the forward voltage of
the string is about 7.10 V at 50 mA. Assuming
a voltage drop across the sense resistor of 0.25
V, then at an input voltage of 9 V, the drop-out
voltage of the regulator would be (9 V – 7.1 V –
0.25 V), or 1.65 V. Since there are 10 strings of
LED emitters, the total LED array current would
be 50 mA times 10, or 500 mA. Thus, the sense
resistor would be (0.25 V / 0.500 A), or 0.5
ohms. Then over an input voltage range of 7
to 18 volts, the total load current of the circuit
would vary as shown in Figure 3.25. As
Figure 3.25 Forward Current Through LED Emitters
as a Function of Applied Voltage for Series-Pass
Constant-Current Regulator Circuit Shown in Figure
3.24.
The key elements of the switching constant-
current regulator are shown in Figure 3.26. There
are a number of different types of switching
regulators. Buck or Down Converters are
designed, this circuit maintains a constant
current through the LED array at input voltages
greater than 9 V. Suppose that the minimum
compliance voltage of the circuit is designed to
be 10 V, then an additional volt can be dropped
across the load or series pass regulator.
designed to generate a regulated output voltage
that is always less than the input voltage. Boost
or Up Converters are capable of generating a
regulated output voltage that is always higher
than the input voltage. Buck/Boost or Up/Down
Converters can generate a regulated output
voltage using any input voltage. By comparison,
35
current-limiting resistors and series-pass
input voltages, the efficiency of the switching
regulator is better than the series-pass regulator
and the resistor-limited circuits. Assuming a
0.25 V drop across the sense resistor, then for
the ten-string circuit, RSENSE would be equal to
(0.25 V / 0.500 A), or 0.5 ohms. Assuming a
power conversion efficiency of 80% and an input
voltage range of 7 to 18 volts, then the input
current and total load current of the circuit would
vary as shown in Figure 3.27.
regulators can only reduce the output voltage to
a lower value than the input voltage. Thus for
some types of switching regulator circuits the
number of LED emitters per string can be larger
than the number of LED emitters per string for a
resistor-limited or series-pass regulator circuit.
In general, the switching regulator converts the
average input power (VIN times IIN) to the desired
output power (VLOAD times ILOAD) with a relatively
fixed power conversion efficiency. At higher
Figure 3.26 Block Diagram
of LED Signal Lamp
Design Using Switching
Constant-Current
Regulator.
Figure 3.27 Forward Current Through LED
Emitters as a Function of Applied Voltage for
Switching Constant-Current Regulator Circuit
Shown in Figure 3.26.
Figure 3.28 Comparison of Total Supply
Current versus Applied Voltage for Circuit
Designs Shown in Figures 3.22, 3.24 and 3.26.
The total power consumption for the four
different LED signal lamp designs is shown in
Figure 3.28. The series pass and switching
regulator designs provide substantial power
savings compared to the resistor-controlled
circuits during over-voltage conditions. Note
that at an input voltage of 18 V, both resistor
limited circuits have an overall power consumption
of 15 W. The series pass current regulator circuit
has an overall power consumption of 9 W. The
switching current regulator has an overall power
consumption of 5 W.
36
Company Information
Lumileds is a world-class supplier of Light Emitting Diodes (LEDs) producing
billions of LEDs annually. Lumileds is a fully integrated supplier, producing
core LED material in all three base colors (Red, Green, Blue)
and White. Lumileds has R&D development centers in San Jose,
California and Best, The Netherlands. Production capabilities in
San Jose, California and Malaysia.
Lumileds is pioneering the high-flux LED technology and bridging the gap
between solid state LED technology and the lighting world. Lumileds is
absolutely dedicated to bringing the best and brightest LED technology to
enable new applications and markets in the Lighting world.
LUMILEDS
www.luxeon.com
www.lumileds.com
For technical assistance or the
location of your nearest Lumileds
sales office, call:
Worldwide:
+1 408-435-6044
US Toll free: 877-298-9455
Europe: +31 499 339 439
Fax: 408-435-6855
Email us at info@lumileds.com
ã 2002 Lumileds Lighting. All rights reserved. Lumileds Lighting is a joint venture between Agilent Technologies and Philips
Lumileds Lighting, LLC
370 West Trimble Road
San Jose, CA 95131
Lighting. Luxeon is a trademark of Lumileds Lighting, Inc. Product specifications are subject to change without notice.
Publication No. AB20-3 (Sept2002)
37
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