ISL97516IUZ-T [INTERSIL]
600kHz/1.2MHz PWM Step-Up Regulator; 600kHz的/ 1.2MHz的PWM升压调节器
| 型号： | ISL97516IUZ-T |
| 厂家： | 
Intersil |
| 描述： | 600kHz/1.2MHz PWM Step-Up Regulator |
| 文件： | 总9页 (文件大小：327K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
ISL97516
®
Data Sheet
December 22, 2006
FN9261.1
600kHz/1.2MHz PWM Step-Up Regulator
Features
The ISL97516 is a high frequency, high efficiency step-up
voltage regulator operated at constant frequency PWM
mode. With an internal 2.0A, 200mΩ MOSFET, it can deliver
up to 1A output current at over 90% efficiency. The
selectable 600kHz and 1.2MHz allows smaller inductors and
faster transient response. An external compensation pin
gives the user greater flexibility in setting frequency
compensation allowing the use of low ESR Ceramic output
capacitors.
• >90% Efficiency
• 2.0A, 200mΩ Power MOSFET
• 2.3V to 5.5V Input
• Up to 25V Output
• 600kHz/1.2MHz Switching Frequency Selection
• Adjustable Soft-Start
• Internal Thermal Protection
When shut down, it draws <1µA of current and can operate
down to 2.3V input supply. These features along with
1.2MHz switching frequency makes it an ideal device for
portable equipment and TFT-LCD displays.
• 1.1mm Max Height 8 Ld MSOP Package
• Pb-free Plus Anneal Available (RoHS compliant)
Applications
• TFT-LCD displays
• DSL modems
The ISL97516 is available in an 8 Ld MSOP package with a
maximum height of 1.1mm. The device is specified for
operation over the full -40°C to +85°C temperature range.
• PCMCIA cards
Pinout
• Digital cameras
• GSM/CDMA phones
• Portable equipment
• Handheld devices
ISL97516
(8 LD MSOP)
TOP VIEW
COMP
FB
SS
1
2
3
4
8
7
6
5
FSEL
VDD
LX
Ordering Information
EN
PART NUMBER
(Note)
PART
MARKING
PACKAGE
(Pb-Free)
PKG.
DWG. #
GND
ISL97516IUZ-T
ISL97516IUZ-TK
7516Z
7516Z
8 Ld MSOP
8 Ld MSOP
MDP0043
MDP0043
NOTE: Intersil Pb-free plus anneal products employ special Pb-free
material sets; molding compounds/die attach materials and 100%
matte tin plate termination finish, which are RoHS compliant and
compatible with both SnPb and Pb-free soldering operations. Intersil
Pb-free products are MSL classified at Pb-free peak reflow
temperatures that meet or exceed the Pb-free requirements of
IPC/JEDEC J STD-020.
CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures.
1-888-INTERSIL or 1-888-468-3774 | Intersil (and design) is a registered trademark of Intersil Americas Inc.
Copyright Intersil Americas Inc. 2006. All Rights Reserved
1
All other trademarks mentioned are the property of their respective owners.
ISL97516
Absolute Maximum Ratings (T = +25°C)
A
LX to GND . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .27V
to GND. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .6V
Storage Temperature . . . . . . . . . . . . . . . . . . . . . . . .-65°C to +150°C
Operating Ambient Temperature . . . . . . . . . . . . . . . .-40°C to +85°C
Operating Junction Temperature . . . . . . . . . . . . . . . . . . . . . . +135°C
Power Dissipation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . See Curves
V
DD
COMP, FB, EN, SS, FSEL to GND . . . . . . . . . -0.3V to (V
+0.3V)
DD
CAUTION: Stresses above those listed in “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress only rating and operation of the
device at these or any other conditions above those indicated in the operational sections of this specification is not implied.
IMPORTANT NOTE: All parameters having Min/Max specifications are guaranteed. Typical values are for information purposes only. Unless otherwise noted, all tests
are at the specified temperature and are pulsed tests, therefore: T = T = T
J
C
A
Electrical Specifications
V
= 3.3V, V
= 12V, I
= 0mA, FSEL = GND, T = -40°C to +85°C unless otherwise specified.
A
IN
OUT
OUT
PARAMETER
DESCRIPTION
CONDITIONS
MIN
TYP
1
MAX
UNIT
µA
mA
mA
V
IQ1
IQ2
IQ3
Quiescent Current - Shutdown
EN = 0V
EN= V , FB = 1.3V
5
Quiescent Current - Not Switching
Quiescent Current - Switching
Feedback Voltage
0.7
DD
EN = V , FB = 1.0V
DD
3
4
V
1.272
1.294
0.01
1.309
0.5
FB
I
Feedback Input Bias Current
Input Voltage Range
µA
V
B-FB
V
2.3
85
5.5
DD
D
D
-600kHz Maximum Duty Cycle
FSEL = 0V
92
90
%
MAX
-1.2MHz Maximum Duty Cycle
FSEL = V
85
%
MAX
DD
I
Current Limit - Max Peak Input Current
1.5
2.0
A
LIM
I
Shutdown Input Bias Current
Switch ON Resistance
EN = 0V
0.01
0.2
0.5
3
µA
Ω
EN
r
V
= 2.7V, I = 1A
LX
DS(ON)
DD
VSW = 27V
3V < V < 5.5V, V
I
Switch Leakage Current
Line Regulation
0.01
0.2
µA
%
LX-LEAK
ΔV /ΔV
= 12V
OUT
/ΔI
IN
IN
= 3.3V, V
OUT
ΔV
Load Regulation
V
= 12V, I = 30mA to 200mA
0.3
%
OUT OUT
IN
OUT
O
F
F
Switching Frequency Accuracy
Switching Frequency Accuracy
EN, FSEL Input Low Level
EN, FSEL Input High Level
Error Amp Tranconductance
FSEL = 0V
500
620
1250
740
1500
0.5
kHz
kHz
V
OSC1
OSC2
FSEL = V
1000
DD
V
IL
V
1.5
70
V
IH
G
ΔI = 5µA
130
2.2
100
6
150
2.3
1µ/Ω
V
M
V
V
V
UVLO On Threshold
UVLO hyeteresis
2.1
DD-ON
HYS
DD
DD
mV
µA
°C
I
Soft-Start Charge Current
4
8
SS
OTP
Over Temperature Protection
150
FN9261.1
December 22, 2006
2
ISL97516
Block Diagram
FSEL
EN
SS
SHUTDOWN &
START-UP
CONTROL
REFERENCE
GENERATOR
VDD
OSCILLATOR
LX
PWM LOGIC
CONTROLLER
FET
DRIVER
COMPARATOR
CURRENT
SENSE
GND
FB
GM
AMPLIFIER
COMP
Pin Descriptions
PIN NUMBER
PIN NAME
DESCRIPTION
1
2
COMP
FB
Compensation pin. Output of the internal error amplifier. Capacitor and resistor from COMP pin to ground.
Voltage feedback pin. Internal reference is 1.294V nominal. Connect a resistor divider from V
.
OUT
V
= 1.294V (1 + R /R ). See Typical Application Circuit.
1 2
OUT
3
4
5
6
7
EN
GND
LX
Shutdown control pin. Pull EN low to turn off the device.
Analog and power ground.
Power switch pin. Connected to the drain of the internal power MOSFET.
Analog power supply input pin.
VDD
FSEL
Frequency select pin. When FSEL is set low, switching frequency is set to 620kHz. When connected to
high or V , switching frequency is set to 1.25MHz.
DD
8
SS
Soft-start control pin. Connect a capacitor to control the converter start-up.
Typical Application Circuit
1
2
3
4
COMP
FB
SS
FSEL
VDD
LX
8
7
6
5
R
3
3.9kΩ
C
3
R
85.2kΩ
1
27nF
C
R
2
10kΩ
5
4.7nF
EN
2.3V TO 5.5V
C
+
C
1
4
22µF
10µH
0.1µF
GND
12V
C
+
S1
2
D
1
22µF
FN9261.1
December 22, 2006
3
ISL97516
Typical Performance Curves
95
92
90
88
86
84
82
80
78
76
74
V
f
= 3.3V, V = 9V,
O
IN
= 620kHz
90
85
s
V
= 5V, V = 12V, f = 1.25 MHz
O s
IN
80
75
70
65
60
V
= 5V, V = 12V, f = 620 kHz
IN
O
s
V
= 3.3V, V = 12V,
O
IN
= 620kHz
f
s
V
= 5V, V = 9V, f = 620 kHz
V
= 3.3V, V = 12V,
O
IN
O
s
IN
= 1.25MHz
f
s
V
= 5V, V = 9V, f = 1.25MHz
V
= 3.3V, V = 9V,
IN
O
s
IN
O
f
= 1.25MHz
s
0
200
400
600
800
1000
0
100
200
I
300
(mA)
400
500
I
(mA)
OUT
OUT
FIGURE 1. BOOST EFFICIENCY vs I
FIGURE 2. BOOST EFFICIENCY vs I
OUT
OUT
0.7
0.9
0.8
0.7
0.6
0.5
0.4
0.3
0.2
0.1
0
V
f
= 3.3V, V = 12V,
V
f
= 3.3V, V = 9V,
O
IN
O
IN
= 1.25MHz
V
f
= 5V, V = 9V,
O
V
f
= 5V, V = 12V,
O
IN
IN
= 1.25MHz
0.6
0.5
0.4
0.3
0.2
0.1
0
= 1.25MHz
s
s
= 1.25MHz
s
s
V
= 3.3, V = 9V,
O
IN
= 1.25kHz
V
f
= 5V, V = 9V,
O
IN
f
s
= 620kHz
s
V
f
= 5V, V = 12V,
O
V
f
= 3.3, V = 12V,
O
IN
IN
= 620kHz
= 620kHz
s
s
0
100
200
I
300
400
500
0
200
400
600
(mA)
800
1000
I
(mA)
OUT
OUT
FIGURE 3. LOAD REGULATION vs I
FIGURE 4. LOAD REGULATION vs I
OUT
OUT
0.9
0.6
V
f
= 5V, V = 12V,
V
f
= 5V, V = 9V,
O
IN
O
IN
0.8
0.7
0.6
0.5
0.4
0.3
0.2
0.1
= 1.25MHz
= 1.25MHz
V
= 9V, I = 80mA
O
s
s
O
0.5
0.4
0.3
0.2
0.1
0
f
= 1.25MHz
s
V
= 9V, I = 100mA
O
O
V
= 5V, V = 9V,
O
IN
f
= 620kHz
s
f
= 620kHz
s
V
f
= 9V, I = 100mA
O
O
= 1.25MHz
s
V
= 5V, V = 12V,
O
IN
= 620kHz
V
= 9V, I = 80mA
O
O
f
s
f
= 620kHz
s
0
-0.1
0
200
400
600
(mA)
800
1000
2
3
4
5
6
I
V
(V)
IN
OUT
FIGURE 5. LOAD REGULATION vs I
FIGURE 6. LINE REGULATION vs V
IN
OUT
FN9261.1
December 22, 2006
4
ISL97516
Typical Performance Curves (Continued)
I
= 50mA to 300mA
I = 50mA to 300mA
O
O
V
= 12V
O
V
= 12V
O
V
= 3.3V
V
= 3.3V
f
= 600kHz
f = 1.2MHz
s
IN
IN
s
FIGURE 7. TRANSIENT RESPONSE
FIGURE 8. TRANSIENT RESPONSE
JEDEC JESD51-7 HIGH EFFECTIVE THERMAL
CONDUCTIVITY TEST BOARD
JEDEC JESD51-3 LOW EFFECTIVE THERMAL
CONDUCTIVITY TEST BOARD
1
0.6
0.5
0.4
0.3
0.2
0.1
0
0.9
0.8
0.7
0.6
0.5
0.4
0.3
0.2
0.1
0
870mW
486mW
0
25
50
75 85 100
125
0
25
50
75 85 100
125
AMBIENT TEMPERATURE (°C)
AMBIENT TEMPERATURE (°C)
FIGURE 9. PACKAGE POWER DISSIPATION vs AMBIENT
TEMPERATURE
FIGURE 10. PACKAGE POWER DISSIPATION vs AMBIENT
TEMPERATURE
on and the Schottky diode is reverse biased and cuts off the
current flow to the output. The output current is supplied
from the output capacitor. The voltage across the inductor is
Applications Information
The ISL97516 is a high frequency, high efficiency boost
regulator operated at constant frequency PWM mode. The
boost converter stores energy from an input voltage source
and deliver it to a higher output voltage. The input voltage
range is 2.3V to 5.5V and output voltage range is 5V to 25V.
The switching frequency is selectable between 600kHz and
1.2MHz allowing smaller inductors and faster transient
response. An external compensation pin gives the user
greater flexibility in setting output transient response and
tighter load regulation. The converter soft-start characteristic
V
and the inductor current ramps up in a rate of V /L, L is
IN
IN
the inductance. The inductance is magnetized and energy is
stored in the inductor. The change in inductor current is:
V
IN
---------
ΔI
= ΔT1 ×
L1
L
D
------------
ΔT1 =
F
SW
D = Duty Cycle
can also be controlled by external C capacitor. The EN pin
SS
allows the user to completely shutdown the device.
I
OUT
---------------
ΔV
=
× ΔT
(EQ. 1)
O
1
C
OUT
Boost Converter Operations
Figure 11 shows a boost converter with all the key
components. In steady state operating and continuous
conduction mode where the inductor current is continuous,
the boost converter operates in two cycles. During the first
cycle, as shown in Figure 12, the internal power FET turns
FN9261.1
December 22, 2006
5
ISL97516
During the second cycle, the power FET turns off and the
Schottky diode is forward biased, (Figure 13). The energy
stored in the inductor is pumped to the output supplying
output current and charging the output capacitor. The
Schottky diode side of the inductor is clamp to a Schottky
diode above the output voltage. So the voltage drop across
L
D
V
V
OUT
IN
C
C
OUT
IN
ISL97516
the inductor is V - V
. The change in inductor current
IN
OUT
I
during the second cycle is:
L
ΔI
L2
ΔT
2
V
– V
OUT
L
IN
-------------------------------
ΔI = ΔT2 ×
ΔV
O
L
1 – D
-------------
ΔT2 =
FIGURE 13. BOOST CONVERTER - CYCLE 2, POWER
SWITCH OPEN
(EQ. 2)
F
SW
Output Voltage
For stable operation, the same amount of energy stored in
the inductor must be taken out. The change in inductor
current during the two cycles must be the same.
An external feedback resistor divider is required to divide the
output voltage down to the nominal 1.294V reference
voltage. The current drawn by the resistor network should be
limited to maintain the overall converter efficiency. The
maximum value of the resistor network is limited by the
feedback input bias current and the potential for noise being
coupled into the feedback pin. A resistor network less than
100k is recommended. The boost converter output voltage is
determined by the relationship:
ΔI1 + ΔI2 = 0
V
V
– V
IN OUT
D
1 – D
IN
------------ --------- ------------- -------------------------------
×
+
×
= 0
F
L
F
L
SW
SW
V
1
OUT
(EQ. 3)
---------------
-------------
=
V
1 – D
IN
R
⎛
⎞
⎟
⎠
1
(EQ. 4)
------
V
= V × 1 +
⎜
OUT
FB
R
2
⎝
L
D
The nominal VFB voltage is 1.294V.
V
V
OUT
IN
C
C
OUT
IN
Inductor Selection
The inductor selection determines the output ripple voltage,
transient response, output current capability, and efficiency.
Its selection depends on the input voltage, output voltage,
switching frequency, and maximum output current. For most
applications, the inductance should be in the range of 2µH to
33µH. The inductor maximum DC current specification must
be greater than the peak inductor current required by the
regulator. The peak inductor current can be calculated:
:
ISL97516
FIGURE 11. BOOST CONVERTER
L
V
V
OUT
IN
C
C
OUT
IN
I
× V
V
× (V
– V
)
IN
OUT
OUT
IN
OUT
-----------------------------------
----------------------------------------------------
I
=
+ 1 ⁄ 2 ×
L(PEAK)
V
L × V
× FREQ
OUT
ISL97516
IN
(EQ. 5)
Output Capacitor
Low ESR capacitors should be used to minimized the output
voltage ripple. Multilayer ceramic capacitors (X5R and X7R)
are preferred for the output capacitors because of their lower
ESR and small packages. Tantalum capacitors with higher
ESR can also be used. The output ripple can be calculated
as:
I
L
ΔI
L1
ΔT
1
ΔV
O
FIGURE 12. BOOST CONVERTER - CYCLE 1, POWER
SWITCH CLOSED
I
× D
OUT
(EQ. 6)
---------------------------
ΔV
=
+ I
× ESR
OUT
O
F
× C
O
SW
For noise sensitive application, a 0.1µF placed in parallel
with the larger output capacitor is recommended to reduce
the switching noise coupled from the LX switching node.
FN9261.1
December 22, 2006
6
ISL97516
Schottky Diode
Maximum Output Current
The MOSFET current limit is nominally 2.0A and guaranteed
In selecting the Schottky diode, the reverse break down
voltage, forward current and forward voltage drop must be
considered for optimum converter performance. The diode
must be rated to handle 2.0A, the current limit of the
ISL97516. The breakdown voltage must exceed the
maximum output voltage. Low forward voltage drop, low
leakage current, and fast reverse recovery will help the
converter to achieve the maximum efficiency.
1.7A. This restricts the maximum output current, I
based on the following formula:
,
OMAX
(EQ. 7)
I
= I
+ (1 ⁄ 2 × ΔI )
L-AVG L
L
where:
I = MOSFET current limit
L
Input Capacitor
I
= average inductor current
L-AVG
The value of the input capacitor depends the input and
output voltages, the maximum output current, the inductor
value and the noise allowed to put back on the input line. For
most applications, a minimum 10µF is required. For
applications that run close to the maximum output current
limit, input capacitor in the range of 22µF to 47µF is
recommended.
ΔI = inductor ripple current
L
V
× [(V + V
) – V
]
IN
IN
O
DIODE
(EQ. 8)
------------------------------------------------------------------------------
=
ΔI
L
L × (V + V
) × F
S
O
DIODE
V
= Schottky diode forward voltage, typically, 0.6V
DIODE
F
I
= switching frequency, 600kHz or 1.2MHz
S
The ISL97516 is powered from the VIN. A High frequency
0.1µF bypass cap is recommended to be close to the VIN
pin to reduce supply line noise and ensure stable operation.
I
OUT
-------------
=
L-AVG
1 – D
Loop Compensation
D = MOSFET turn-on ratio:
The ISL97516 incorporates a transconductance amplifier in
its feedback path to allow the user some adjustment on the
transient response and better regulation. The ISL97516
uses current mode control architecture which has a fast
current sense loop and a slow voltage feedback loop. The
fast current feedback loop does not require any
V
IN
(EQ. 9)
--------------------------------------------
OUT
D = 1 –
V
+ V
DIODE
Table 1 gives typical maximum I
OUT
switching frequency and 10µH inductor.
values for 1.2MHz
compensation. The slow voltage loop must be compensated
for stable operation. The compensation network is a series
RC network from COMP pin to ground. The resistor sets the
high frequency integrator gain for fast transient response
and the capacitor sets the integrator zero to ensure loop
stability. For most applications, the compensation resistor in
the range of 2k to 7.5k and the compensation capacitor in
the range of 3nF to 10nF.
TABLE 1.
V
(V)
V
(V)
I
(mA)
IN
OUT
OMAX
2.5
5
870
2.5
2.5
3.3
3.3
3.3
5
9
12
5
500
380
1150
655
500
990
750
9
Soft-Start
12
9
The soft-start is provided by an internal 6µA current source
charges the external C , the peak MOSFET current is
SS
limited by the voltage on the capacitor. This in turn controls
the rising rate of the output voltage. The regulator goes
through the start-up sequence as well after the EN pin is
pulled to HI.
5
12
Cascaded MOSFET Application
An 25V N-channel MOSFET is integrated in the boost
regulator. For the applications where the output voltage is
greater than 25V, an external cascaded MOSFET is needed
as shown in Figure 12. The voltage rating of the external
Frequency Selection
The ISL97516 switching frequency can be user selected to
operate at either constant 620kHz or 1.25MHz. Connecting
F
pin to ground sets the PWM switching frequency to
SEL
620kHz. When connecting F
MOSFET should be greater than A .
VDD
high or V , the switching
DD
SEL
frequency is set to 1.25MHz.
Shutdown Control
When the EN pin is pulled down, the ISL97516 is shutdown
reducing the supply current to <1µA.
FN9261.1
December 22, 2006
7
ISL97516
DC PATH BLOCK APPLICATION
Note that there is a DC path in the boost converter from the
input to the output through the inductor and diode, hence the
input voltage will be seen at output with a forward voltage
drop of diode before the part is enabled. If this voltage is not
desired, the following circuit can be inserted between input
and inductor to disconnect the DC path when the part is
disabled.
A
V
VDD
IN
LX
FB
Intersil
ISL97516
INPUT
TO INDUCTOR
EN
FIGURE 15. CIRCUIT TO DISCONNECT THE DC PATH OF
BOOST CONVERTER
FIGURE 14. CASCADED MOSFET TOPOLOGY FOR HIGH
OUTPUT VOLTAGE APPLICATIONS
FN9261.1
December 22, 2006
8
ISL97516
Mini SO Package Family (MSOP)
MDP0043
0.25 M C A B
A
MINI SO PACKAGE FAMILY
D
(N/2)+1
SYMBOL
MSOP8
1.10
0.10
0.86
0.33
0.18
3.00
4.90
3.00
0.65
0.55
0.95
8
MSOP10
1.10
0.10
0.86
0.23
0.18
3.00
4.90
3.00
0.50
0.55
0.95
10
TOLERANCE
Max.
NOTES
N
A
A1
A2
b
-
±0.05
-
±0.09
-
E
E1
PIN #1
I.D.
+0.07/-0.08
±0.05
-
c
-
D
±0.10
1, 3
E
±0.15
-
1
B
(N/2)
E1
e
±0.10
2, 3
Basic
-
L
±0.15
-
e
H
C
L1
N
Basic
-
SEATING
PLANE
Reference
-
Rev. C 6/99
M
C A B
b
0.08
0.10 C
NOTES:
N LEADS
1. Plastic or metal protrusions of 0.15mm maximum per side are not
included.
2. Plastic interlead protrusions of 0.25mm maximum per side are
not included.
L1
3. Dimensions “D” and “E1” are measured at Datum Plane “H”.
4. Dimensioning and tolerancing per ASME Y14.5M-1994.
A
c
SEE DETAIL "X"
A2
GAUGE
PLANE
0.25
L
DETAIL X
A1
3° ±3°
All Intersil U.S. products are manufactured, assembled and tested utilizing ISO9000 quality systems.
Intersil Corporation’s quality certifications can be viewed at www.intersil.com/design/quality
Intersil products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design, software and/or specifications at any time without
notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be accurate and
reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result
from its use. No license is granted by implication or otherwise under any patent or patent rights of Intersil or its subsidiaries.
For information regarding Intersil Corporation and its products, see www.intersil.com
FN9261.1
December 22, 2006
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