5962-9560302QCA [TI]

四路微功耗轨到轨输入和输出 CMOS 运算放大器 | J | 14 | -55 to 125;


型号：	5962-9560302QCA
厂家：	TEXAS INSTRUMENTS
描述：	四路微功耗轨到轨输入和输出 CMOS 运算放大器 \| J \| 14 \| -55 to 125 放大器运算放大器放大器电路
文件：	总22页 (文件大小：1160K)
中文：	中文翻译
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LMC6464QML

LMC6464QML Quad Micropower, Rail-to-Rail Input and Output CMOS Operational

Amplifier

Literature Number: SNOSAR8

December 8, 2010

LMC6464QML Quad

Micropower, Rail-to-Rail Input and Output CMOS

Operational Amplifier

General Description

Features

The LMC6464 is a micropower version of the popular

LMC6484, combining Rail-to-Rail Input and Output Range

with very low power consumption.

(Typical unless otherwise noted)

Low offset voltage. 500µV

■

Ultra Low Supply Currentꢀ 23 μA/Amplifier

Operates from 3V to 15V single supply

■

The LMC6464 provides an input common-mode voltage

range that exceeds both rails. The rail-to-rail output swing of

the amplifier, guaranteed for loads down to 25 KΩ, assures

maximum dynamic signal range. This rail-to-rail performance

of the amplifier, combined with its high voltage gain makes it

unique among rail-to-rail amplifiers. The LMC6464 is an ex-

cellent upgrade for circuits using limited common-mode range

amplifiers.

Rail-to-Rail Output Swing

(within 10 mV of rail, V_S= 5V and R_L= 25 KΩ)

Low Input Bias Current 150 fA

■

Applications

Battery Operated Circuits

■

The LMC6464, with guaranteed specifications at 3V and 5V,

is especially well-suited for low voltage applications. A quies-

cent power consumption of 60 μW per amplifier (at V_S= 3V)

can extend the useful life of battery operated systems. The

amplifier's 150 fA input current, low offset voltage of 0.25 mV,

and 85 dB CMRR maintain accuracy in battery-powered sys-

tems.

Transducer Interface Circuits

Portable Communication Devices

Medical Applications

Battery Monitoring

■

Ordering Information

NS Part Number

SMD Part Number

NS Package Number

Package Description

14LD Ceramic DIP

LMC6464AMJ-QML

5962–9560302QCA

J14A

201606

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14-Pin Ceramic DIP

20160602

Top View

Low-Power Two-Op-Amp Instrumentation Amplifier

20160621

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Absolute Maximum Ratings (Note 1)

Supply Voltage (V⁺− V⁻)

Differential Input Voltage

Voltage at Input/Output Pin

Current at Input Pin (Note 8)

Current at Output Pin (Note 4), (Note 6)

Current at Power Supply Pin

Junction Temperature (Note 4), (Note 2)

Power Dissipation (Note 2)

LMC6464

16V

± Supply Voltage

(V⁺) + 0.3V, (V⁻) − 0.3V

±5 mA

±30 mA

40 mA

150°C

6mW

Thermal Resistance (Note 10)

ꢀθ_JA

14LD Ceramic DIP (Still Air)

14LD Ceramic DIP (500LF/Min Air flow)

ꢀθ_JC

74°C/W

37°C/W

14LD Ceramic DIP

8°C/W

Storage Temperature Range

−65°C ≤ T_A≤ +150°C

260°C

Lead Temp. (Soldering, 10 sec.)

ESD Tolerance (Note 3)

2.0 KV

Recommended Operating Range

(Note 1)

3.0V ≤ V⁺≤ 15.5V

−55°C ≤ T_A≤ +125°C

Supply Voltage

Operating Temperature Range

Quality Conformance Inspection

Mil-Std-883, Method 5005 - Group A

Subgroup

Description

Static tests at

Temp (°C)

+25

+125

-55

Static tests at

Dynamic tests at

Functional tests at

Switching tests at

Settling time at

+25

+125

-55

+25

+125

-55

+25

+125

-55

+25

+125

-55

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LMC6464 Electrical Characteristics

DC Parameters: 3 Volt

The following conditions apply, unless otherwise specified. V⁺= 3V, V⁻= 0V, V_CM= V_O= V⁺/2 and R_L> 1M.

Sub-

groups

Symbol

V_IO

Parameter

Conditions

Notes

Min Max

Units

Input Offset Voltage

0.8

1.7

I_IB

Input Bias Current

(Note 9)

100

I_IO

Input Offset Current

100

2, 3

CMRR

V_CM

V_Op

I_CC

Common Mode Rejection Ratio

0V ≤ V_CM≤ 3.0V

2, 3

Input Common Mode Voltage

Range

3.0

2.9

2.8

0.0

0.1

For CMRR ≥ 50 dB

R_L= 25KΩ to V⁺/2

V_O= V⁺/2

2, 3

Output Swing

0.10

0.15

110

140

2, 3

Supply Current

µA

2, 3

I_SC

Output Short Circuit Current

Sourcing

V_O= 0V

8.0

6.0

2, 3

Sinking

V_O= 3V

2, 3

DC Parameters: 5 Volt

The following conditions apply, unless otherwise specified. V⁺= 5V, V⁻= 0V, V_CM= V_O= V⁺/2 and R_L> 1M.

Sub-

groups

Symbol

V_IO

Parameter

Conditions

Notes

Min Max

Units

Input Offset Voltage

0.5

2, 3

1.4

I_IB

Input Bias Current

(Note 9)

100

2, 3

I_IO

Input Offset Current

100

2, 3

CMRR

V_CM

V_Op

Common Mode Rejection Ratio

0V ≤ V_CM≤ 5.0V

2, 3

Input Common-Mode Voltage

Range

5.25 -0.10

5.00 0.00

4.990 0.010

4.980 0.020

4.975 0.020

4.965 0.035

110

For CMRR ≥ 50 dB

R_L= 100KΩ to V⁺/2

R_L= 25KΩ to V⁺/2

V_O= V⁺/2

2, 3

Output Swing

2, 3

I_CC

I_SC

Supply Current

µA

140

2, 3

Output Short Circuit Current

Sourcing

V_O= 0V

2, 3

Sinking

V_O= 5V

2, 3

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DC Parameters: 15 Volt

The following conditions apply, unless otherwise specified. V⁺= 15V, V⁻= 0V, V_CM= V_O= V⁺/2 and R_L> 1M.

Sub-

groups

Symbol

V_IO

Parameter

Conditions

Notes

Min

Max

Units

Input Offset Voltage

1.8

2.3

2, 3

I_IB

Input Bias Current

(Note 9)

100

2, 3

I_IO

Input Offset Current

100

2, 3

CMRR

V_CM

Common Mode Rejection Ratio

0V ≤ V_CM≤ 15.0V

2, 3

Input Common Mode Voltage

Range

15.25 -0.15

For CMRR ≥ 50dB

15.00 0.00

2, 3

5V ≤ V⁺≤ 15V

+PSRR

Positive Power Supply Rejection

Ratio

V^-= 0V, V_O= 2.5V

2, 3

-15V ≤ V^-≤ -5V

-PSRR

V_Op

Negative Power Supply

Rejection Ratio

V⁺= 0V, V_O= -2.5V

2, 3

R_L= 100KΩ to V⁺/2

R_L= 25KΩ to V⁺/2

V_O= V⁺/2

Output Swing

14.975 0.025

2, 3

14.965 0.035

14.900 0.050

14.850 0.150

2, 3

I_CC

I_SC

Supply Current

120

µA

140

2, 3

Output Short Circuit Current

Sourcing

V_O= 0V

2, 3

Sinking

V_O= 12V

(Note 6)

(Note 5)

2, 3

A_V

Large Signal Voltage Gain

Sourcing

110

R_L= 100KΩ

2, 3

Sinking

100

R_L= 100KΩ

2, 3

Sourcing

110

R_L= 25KΩ

2, 3

Sinking

R_L= 25KΩ

2, 3

AC Parameters: 15 Volt

The following conditions apply, unless otherwise specified.

DC:

V⁺= 15V, V⁻= 0V, V_CM= V_O= V⁺/2 and R_L> 1M.

Sub-

groups

Symbol

Parameter Conditions

Notes

Min

Max

Units

GBW

Slew Rate

Gain-Bandwidth

(Note 7)

7.0

V/mS

KHz

5, 6

KHz

5, 6

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Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is

functional, but do not guarantee specific performance limits. For guaranteed specifications and test conditions, see the Electrical Characteristics. The guaranteed

specifications apply only for the test conditions listed. Some performance characteristics may degrade when the device is not operated under the listed test

conditions.

Note 2: The maximum power dissipation must be derated at elevated temperatures and is dictated by T_Jmax(maximum junction temperature), θ_JA(package

junction to ambient thermal resistance), and T_A(ambient temperature). The maximum allowable power dissipation at any temperature is P_Dmax= (T_Jmax- T_A)/

_JAor the number given in the Absolute Maximum Ratings, whichever is lower.

Note 3: Human body model, 1.5 kΩ in series with 100 pF.

Note 4: Applies to both single supply and split-supply operation. Continuous short circuit operation at elevated ambient temperature can result in exceeding the

maximum allowed junction temperature of 150°C. Output currents in excess of ±30 mA over long term may adversely affect reliability.

Note 5: V_CM= 7.5V and R_Lconnected to 7.5V. For Sourcing tests, 7.5V ≤ V_O≤ 11.5V. For Sinking tests, 3.5V ≤ V_O≤ 7.5V.

Note 6: Do not short circuit output to V⁺, when V⁺is greater than 13V or reliability will be adversely affected.

Note 7: Device configured as a Voltage Follower with a 10V input step. For positive slew, V_Iswing is 2.5V to 12.5V, V_Ois measured between 6.0V and 9.0V. For

negative slew, V_Iswing is 12.5V to 2.5V, V_Ois measured between 9.0V and 6.0V.

Note 8: Limiting input pin current is only necessary for input voltages that exceed absolute maximum input voltage ratings.

Note 9: Limits are dictated by testing limitations and not device performance.

Note 10: All numbers apply for packages soldered directly into a PC board.

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Typical Performance Characteristics V_S= +5V, Single Supply, T_A= 25°C unless otherwise specified

Supply Current vs. Supply Voltage

Sourcing Current vs. Output Voltage

20160630

20160631

Sourcing Current vs. Output Voltage

20160632

20160633

Sinking Current vs. Output Voltage

20160634

20160635

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Sinking Current vs. Output Voltage

Input Voltage Noise vs Frequency

20160637

20160636

Input Voltage Noise vs. Input Voltage

20160638

20160639

Input Voltage Noise vs. Input Voltage

ΔV_OSvs CMR

20160640

20160641

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Input Voltage vs. Output Voltage

Open Loop Frequency Response

20160643

20160642

Open Loop Frequency Response vs. Temperature

Gain and Phase vs. Capacitive Load

20160644

20160645

Slew Rate vs. Supply Voltage

Non-Inverting Large Signal Pulse Response

20160647

20160646

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Non-Inverting Large Signal Pulse Response

20160648

20160649

Non-Inverting Small Signal Pulse Response

20160650

20160651

Non-Inverting Small Signal Pulse Response

Inverting Large Signal Pulse Response

20160652

20160653

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Inverting Large Signal Pulse Response

20160654

20160655

Inverting Small Signal Pulse Response

20160656

20160657

Inverting Small Signal Pulse Response

20160658

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2.0 RAIL-TO-RAIL OUTPUT

Application Information

The approximated output resistance of the LMC6464 is

180Ω sourcing, and 130Ω sinking at V_S= 3V, and 110Ω

sourcing and 83Ω sinking at V_S= 5V. The maximum output

swing can be estimated as a function of load using the cal-

culated output resistance.

1.0 INPUT COMMON-MODE VOLTAGE RANGE

The LMC6464 has a rail-to-rail input common-mode voltage

range. Figure 1 shows an input voltage exceeding both sup-

plies with no resulting phase inversion on the output.

3.0 CAPACITIVE LOAD TOLERANCE

The LMC6464 can typically drive a 200 pF load with V_S= 5V

at unity gain without oscillating. The unity gain follower is the

most sensitive configuration to capacitive load. Direct capac-

itive loading reduces the phase margin of op-amps. The

combination of the op-amp's output impedance and the ca-

pacitive load induces phase lag. This results in either an

underdamped pulse response or oscillation.

Capacitive load compensation can be accomplished using

resistive isolation as shown in Figure 4. If there is a resistive

component of the load in parallel to the capacitive component,

the isolation resistor and the resistive load create a voltage

divider at the output. This introduces a DC error at the output.

20160605

FIGURE 1. An Input Voltage Signal Exceeds

the LMC6464 Power Supply Voltage

with No Output Phase Inversion

The absolute maximum input voltage at V⁺= 3V is 300 mV

beyond either supply rail at room temperature. Voltages

greatly exceeding this absolute maximum rating, as in Figure

2, can cause excessive current to flow in or out of the input

pins, possibly affecting reliability. The input current can be

externally limited to ±5 mA, with an input resistor, as shown

in Figure 3.

20160608

FIGURE 4. Resistive Isolation of

a 300 pF Capacitive Load

20160609

20160606

FIGURE 5. Pulse Response of the LMC6464

Circuit Shown in Figure 4

FIGURE 2. A ±7.5V Input Signal Greatly Exceeds

the 3V Supply in Figure 3 Causing

No Phase Inversion Due to R_I

Figure 5 displays the pulse response of the LMC6464 circuit

in Figure 4.

Another circuit, shown in Figure 6, is also used to indirectly

drive capacitive loads. This circuit is an improvement to the

circuit shown in Figure 4 because it provides DC accuracy as

well as AC stability. R1 and C1 serve to counteract the loss

of phase margin by feeding the high frequency component of

the output signal back to the amplifiers inverting input, thereby

preserving phase margin in the overall feedback loop. The

values of R1 and C1 should be experimentally determined by

the system designer for the desired pulse response. In-

creased capacitive drive is possible by increasing the value

of the capacitor in the feedback loop.

20160607

FIGURE 3. Input Current Protection for Voltages

Exceeding the Supply Voltage

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R₁C_I≤ R₂C_F

which typically provides significant overcompensation.

Printed circuit board stray capacitance may be larger or small-

er than that of a breadboard, so the actual optimum value for

C_Fmay be different. The values of C_Fshould be checked on

the actual circuit. (Refer to the LMC660 quad CMOS amplifier

data sheet for a more detailed discussion.)

20160610

5.0 OFFSET VOLTAGE ADJUSTMENT

FIGURE 6. LMC6464 Non-Inverting Amplifier,

Offset voltage adjustment circuits are illustrated in Figure 9

and Figure 10. Large value resistances and potentiometers

are used to reduce power consumption while providing typi-

cally ±2.5 mV of adjustment range, referred to the input, for

both configurations with V_S= ±5V.

Compensated to Handle a 300 pF Capacitive

and 100 KΩ Resistive Load

20160611

20160613

FIGURE 7. Pulse Response of

LMC6464 Circuit in Figure 6

FIGURE 9. Inverting Configuration

Offset Voltage Adjustment

The pulse response of the circuit shown in Figure 6 is shown

in Figure 7.

4.0 COMPENSATING FOR INPUT CAPACITANCE

It is quite common to use large values of feedback resistance

with amplifiers that have ultra-low input current, like the

LMC6464. Large feedback resistors can react with small val-

ues of input capacitance due to transducers, photodiodes,

and circuits board parasitics to reduce phase margins.

20160614

FIGURE 10. Non-Inverting Configuration

Offset Voltage Adjustment

6.0 SPICE MACROMODEL

A Spice macromodel is available for the LMC6464. This mod-

el includes a simulation of:

•

Input common-mode voltage range

Frequency and transient response

GBW dependence on loading conditions

Quiescent and dynamic supply current

Output swing dependence on loading conditions

20160612

FIGURE 8. Canceling the Effect of Input Capacitance

and many more characteristics as listed on the macromodel

disk.

The effect of input capacitance can be compensated for by

adding a feedback capacitor. The feedback capacitor (as in

Figure 8 ), C_F, is first estimated by:

Contact the National Semiconductor Customer Response

Center to obtain an operational amplifier Spice model library

disk.

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7.0 PRINTED-CIRCUIT-BOARD LAYOUT FOR HIGH-

IMPEDANCE WORK

It is generally recognized that any circuit which must operate

with less than 1000 pA of leakage current requires special

layout of the PC board. When one wishes to take advantage

of the ultra-low input current of the LMC6464, typically 150 fA,

it is essential to have an excellent layout. Fortunately, the

techniques of obtaining low leakages are quite simple. First,

the user must not ignore the surface leakage of the PC board,

even though it may sometimes appear acceptably low, be-

cause under conditions of high humidity or dust or contami-

nation, the surface leakage will be appreciable.

20160616

To minimize the effect of any surface leakage, lay out a ring

of foil completely surrounding the LMC6464's inputs and the

terminals of capacitors, diodes, conductors, resistors, relay

terminals, etc. connected to the op-amp's inputs, as in Figure

11. To have a significant effect, guard rings should be placed

in both the top and bottom of the PC board. This PC foil must

then be connected to a voltage which is at the same voltage

as the amplifier inputs, since no leakage current can flow be-

tween two points at the same potential. For example, a PC

board trace-to-pad resistance of 10¹²Ω, which is normally

considered a very large resistance, could leak 5 pA if the trace

were a 5V bus adjacent to the pad of the input. This would

cause a 30 times degradation from the LMC6464's actual

performance. However, if a guard ring is held within 5 mV of

the inputs, then even a resistance of 10¹¹Ω would cause only

0.05 pA of leakage current. See Figure 12 for typical connec-

tions of guard rings for standard op-amp configurations.

Inverting Amplifier

20160617

Non-Inverting Amplifier

20160618

Follower

FIGURE 12. Typical Connections of Guard Rings

The designer should be aware that when it is inappropriate to

lay out a PC board for the sake of just a few circuits, there is

another technique which is even better than a guard ring on

a PC board: Don't insert the amplifier's input pin into the board

at all, but bend it up in the air and use only air as an insulator.

Air is an excellent insulator. In this case you may have to

forego some of the advantages of PC board construction, but

the advantages are sometimes well worth the effort of using

point-to-point up-in-the-air wiring. See Figure 13.

20160615

FIGURE 11. Example of Guard Ring in P.C. Board Layout

20160619

(Input pins are lifted out of PC board and soldered directly to components.

All other pins connected to PC board.)

FIGURE 13. Air Wiring

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8.0 INSTRUMENTATION CIRCUITS

these features include analytic medical instruments, magnetic

field detectors, gas detectors, and silicon-based transducers.

The LMC6464 has the high input impedance, large common-

mode range and high CMRR needed for designing instru-

mentation circuits. Instrumentation circuits designed with the

LMC6464 can reject a larger range of common-mode signals

than most in-amps. This makes instrumentation circuits de-

signed with the LMC6464 an excellent choice for noisy or

industrial environments. Other applications that benefit from

A small valued potentiometer is used in series with R_Gto set

the differential gain of the three op-amp instrumentation cir-

cuit in Figure 14. This combination is used instead of one large

valued potentiometer to increase gain trim accuracy and re-

duce error due to vibration.

20160620

FIGURE 14. Low Power Three Op-Amp Instrumentation Amplifier

A two op-amp instrumentation amplifier designed for a gain

of 100 is shown in Figure 15. Low sensitivity trimming is made

for offset voltage, CMRR and gain. Low cost and low power

consumption are the main advantages of this two op-amp cir-

cuit.

Higher frequency and larger common-mode range applica-

tions are best facilitated by a three op-amp instrumentation

amplifier.

20160621

FIGURE 15. Low-Power Two-Op-Amp Instrumentation Amplifier

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Typical Single-Supply Applications

TRANSDUCER INTERFACE CIRCUITS

20160625

20160622

FIGURE 19. Full-Wave Rectifier

with Input Current Protection (R_I)

FIGURE 16. Photo Detector Circuit

In Figure 18 Figure 19, R_Ilimits current into the amplifier since

excess current can be caused by the input voltage exceeding

the supply voltage.

Photocells can be used in portable light measuring instru-

ments. The LMC6464, which can be operated off a battery, is

an excellent choice for this circuit because of its very low input

current and offset voltage.

PRECISION CURRENT SOURCE

LMC6464 AS A COMPARATOR

20160623

FIGURE 17. Comparator with Hysteresis

20160626

Figure 17 shows the application of the LMC6464 as a com-

parator. The hysteresis is determined by the ratio of the two

resistors. The LMC6464 can thus be used as a micropower

comparator, in applications where the quiescent current is an

important parameter.

FIGURE 20. Precision Current Source

The output current I_OUTis given by:

HALF-WAVE AND FULL-WAVE RECTIFIERS

OSCILLATORS

20160624

FIGURE 18. Half-Wave Rectifier with

Input Current Protection (R_I)

20160627

FIGURE 21. 1 Hz Square-Wave Oscillator

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For single supply 5V operation, the output of the circuit will

swing from 0V to 5V. The voltage divider set up R₂, R₃and

R₄will cause the non-inverting input of the LMC6464 to move

from 1.67V (⅓ of 5V) to 3.33V (⅓ of 5V). This voltage behaves

as the threshold voltage.

LOW FREQUENCY NULL

R₁and C₁determine the time constant of the circuit. The fre-

quency of oscillation, f_Oscis

where Δt is the time the amplifier input takes to move from

1.67V to 3.33V. The calculations are shown below.

where τ = RC = 0.68 seconds

→t₁= 0.27 seconds.

and

20160628

→t₂= 0.75 seconds

Then,

FIGURE 22. High Gain Amplifier

with Low Frequency Null

Output offset voltage is the error introduced in the output volt-

age due to the inherent input offset voltage V_OS, of an ampli-

fier.

Output Offset Voltage = (Input Offset Voltage) (Gain)

In the above configuration, the resistors R₅and R₆determine

the nominal voltage around which the input signal, V_Ishould

be symmetrical. The high frequency component of the input

signal V_Iwill be unaffected while the low frequency compo-

nent will be nulled since the DC level of the output will be the

input offset voltage of the LMC6464 plus the bias voltage. This

implies that the output offset voltage due to the top amplifier

will be eliminated.

= 1 Hz

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Revision History

Released

Revision

Section

Changes

12/08/2010

New Release, Corporate format

1 MDS data sheets converted into one Corp. data

sheet format. MNLMC6464AM-X Rev 1A1 will be

archived.

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Physical Dimensions inches (millimeters) unless otherwise noted

14-Pin Ceramic DIP

NS Package Number J14A

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