RHF310K2 [STMICROELECTRONICS]
OP-AMP, 3900uV OFFSET-MAX, CDSO8, ROHS COMPLIANT, CERAMIC, FLAT PACKAGE-8;
| 型号： | RHF310K2 |
| 厂家： | 
ST |
| 描述： | OP-AMP, 3900uV OFFSET-MAX, CDSO8, ROHS COMPLIANT, CERAMIC, FLAT PACKAGE-8 放大器 CD |
| 文件： | 总22页 (文件大小：380K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
RHF310
Rad-hard 400 µA high-speed operational amplifier
Preliminary data
Features
Pin connections
TM
■ OptimWatt device featuring ultra-low 2 mW
consumption and low 400 μA quiescent
(top view)
(a)
current
■ Bandwidth: 120 MHz (gain = 2)
■ Slew rate: 115 V/μs
Ceramic Flat-8
■ Specified on 1 kΩ
1
4
8
5
■ Input noise: 7.5 nV/√Hz
■ Tested with 5 V power supply
NC
IN -
NC
+VCC
IN +
■ 300 krad MIL-STD-883 1019.7 ELDRS free
OUT
NC
-VCC
compliant
■ SEL immune at 125° C, LET up to
2
110 MEV.cm /mg
■ SET characterized, LET up to
2
110 MEV.cm /mg
Applications
■ Low-power, high-speed systems
■ Communication and space equipment
■ Harsh radiation environments
■ ADC drivers
Description
The RHF310 is a very low power, high-speed
operational amplifier. A bandwidth of 120 MHz is
achieved while drawing only 400 µA of quiescent
current. This low-power characteristic is
particularly suitable for high-speed, battery-
powered equipment requiring dynamic
performance. The RHF310 is a single operator
available in Flat-8 package, saving board room as
well as providing excellent thermal performance.
TM
a. OptimWatt is an STMIcroelectronics registered trademark
that applies to products with specific features that optimize
energy efficiency.
May 2009
Doc ID 15577 Rev 1
1/22
This is preliminary information on a new product now in development or undergoing evaluation. Details are subject to
change without notice.
www.st.com
22
Contents
RHF310
Contents
1
2
3
Absolute maximum ratings and operating conditions . . . . . . . . . . . . . 3
Electrical characteristics . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4
Power supply considerations . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 10
3.1
Single power supply . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 10
4
Noise measurements . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 12
4.1
4.2
4.3
Measurement of the input voltage noise eN . . . . . . . . . . . . . . . . . . . . . . . 13
Measurement of the negative input current noise iNn . . . . . . . . . . . . . . . 13
Measurement of the positive input current noise iNp . . . . . . . . . . . . . . . . 13
5
6
7
8
Intermodulation distortion product . . . . . . . . . . . . . . . . . . . . . . . . . . . . 14
Bias of an inverting amplifier . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 16
Active filtering . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 17
Package information . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 18
8.1
Ceramic Flat-8 package information . . . . . . . . . . . . . . . . . . . . . . . . . . . . 19
9
Ordering information . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 20
Revision history . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 21
10
2/22
Doc ID 15577 Rev 1
RHF310
Absolute maximum ratings and operating conditions
1
Absolute maximum ratings and operating conditions
Table 1.
Symbol
Absolute maximum ratings
Parameter
Value
Unit
Supply voltage (1)
(voltage difference between -VCC and +VCC pins)
VCC
6
V
Vid
Vin
Differential input voltage(2)
+/-0.5
+/-2.5
-65 to +150
150
V
V
Input voltage range(3)
Tstg
Tj
Storage temperature
°C
Maximum junction temperature
Thermal resistance junction to ambient area
Thermal resistance junction to case
°C
Rthja
Rthjc
125
°C/W
°C/W
40
Maximum power dissipation(4) (at Tamb = 25° C)
for Tj = 150° C
Pmax
250
mW
kV
HBM: human body model (5)
pins 1, 4, 5, 6, 7 and 8
pins 2 and 3
2
0.5
ESD
MM: machine model (6)
V
pins 1, 4, 5, 6, 7 and 8
pins 2 and 3
200
60
CDM: charged device model (all pins)(7)
1.5
kV
Latch-up immunity
200
mA
1. All voltages values are measured with respect to the ground pin.
2. Differential voltage is the non-inverting input terminal with respect to the inverting input terminal.
3. The magnitude of input and output voltage must never exceed VCC +0.3 V.
4. Short-circuits can cause excessive heating. Destructive dissipation can result from short circuit on
amplifiers.
5. Human body model: a 100 pF capacitor is charged to the specified voltage, then discharged through a
1.5 kΩ resistor between two pins of the device. This is done for all couples of connected pin combinations
while the other pins are floating.
6. This is a minimum value. Machine model: a 200 pF capacitor is charged to the specified voltage, then
discharged directly between two pins of the device with no external series resistor (internal resistor < 5 Ω).
This is done for all couples of connected pin combinations while the other pins are floating.
7. Charged device model: all pins and package are charged together to the specified voltage and then
discharged directly to the ground through only one pin. This is done for all pins.
Table 2.
Symbol
Operating conditions
Parameter
Value
Unit
VCC
Vicm
Tj
Supply voltage
4.5 to 5.5
V
-VCC +1.5 V to
+VCC -1.5 V
Common mode input voltage
Operating junction temperature range
V
-55 to +125
°C
Doc ID 15577 Rev 1
3/22
Electrical characteristics
RHF310
2
Electrical characteristics
Table 3.
Electrical characteristics for V = 2.5 V, T
= 25° C
CC
amb
(unless otherwise specified)
Symbol
Parameter
Test conditions
Min. Typ. Max.
Unit
DC performance
Tamb
1.7
6.5
3.9
Input offset voltage
Offset voltage between both inputs
Vio
ΔVio
Iib+
mV
µV/°C
µA
Tmin < Tamb < Tmax
Tmin < Tamb < Tmax
Tamb
Vio drift vs. temperature
4
3.1
12
6.8
5
Non-inverting input bias current
DC current necessary to bias the + input
Tmin < Tamb < Tmax
Tamb
0.1
61
82
Inverting input bias current
DC current necessary to bias the - input
Iib-
µA
dB
dB
Tmin < Tamb < Tmax
ΔVic = 1 V
1.57
57
58
65
77
Common mode rejection ratio
CMR
20 log (ΔVic/ΔVio)
Tmin < Tamb < Tmax
ΔVCC= 3.5 V to 5 V
Tmin < Tamb < Tmax
Supply voltage rejection ratio
SVR
PSRR
ICC
20 log (ΔVCC/ΔVio)
Power supply rejection ratio
AV = +1, ΔVCC= 100 mV
at 1 kHz
50
dB
µA
20 log (ΔVCC/ΔVout
)
No load
400
530
479
Positive supply current
DC consumption with no input signal
Tmin < Tamb < Tmax
Dynamic performance and output characteristics
Transimpedance
Output voltage/input current gain in open
loop of a CFA.
For a VFA, the analog of this feature is the
RL = 1 kΩ, Vout = 1 V
0.6
1.45
MΩ
MΩ
ROL
Tmin < Tamb < Tmax
0.64
open loop gain (AVD
)
Small signal
RL = 1 kΩ
AV = +1, Rfb = 3 kΩ
AV = +2, Rfb = 3 kΩ
AV = +10, Rfb = 510 Ω
230
120
26
-3 dB bandwidth
80
Frequency where the gain is 3 dB below
the DC gain AV
MHz
(1)
Bw
SR
AV = +2, Rfb = 3 kΩ
TBD
Tmin < Tamb < Tmax
Gain flatness at 0.1 dB
Small signal
Band of frequency where the gain variation Vout = 20 mVp-p
25
does not exceed 0.1 dB
AV = +2, RL = 1kΩ
Vout = 2 Vp-p, AV = +2,
RL = 1 kΩ
Slew rate
75
115
90
Maximum output speed of sweep in large
signal
V/µs
Tmin < Tamb < Tmax
4/22
Doc ID 15577 Rev 1
RHF310
Table 3.
Electrical characteristics
Electrical characteristics for V = 2.5 V, T
= 25° C
CC
amb
(unless otherwise specified) (continued)
Symbol
Parameter
Test conditions
RL = 1 kΩ
Min. Typ. Max.
Unit
1.55
1.65
VOH
High level output voltage
V
Tmin < Tamb < Tmax
RL = 1 kΩ
1.56
-1.66 -1.55
-1.58
VOL
Low level output voltage
V
Tmin < Tamb < Tmax
Output to GND
Isink
70
88
110
Short-circuit output current coming into the
op-amp(2)
Tmin < Tamb < Tmax
Iout
mA
Output to GND
60
75
100
Isource
Output current coming out of the op-amp(3)
Tmin < Tamb < Tmax
Noise and distortion
eN
Equivalent input noise voltage(4)
F = 100 kHz
F = 100 kHz
F = 100 kHz
7.5
13
6
nV/√Hz
pA/√Hz
pA/√Hz
Equivalent input noise current (+)(4)
Equivalent input noise current (-)(4)
iN
Spurious free dynamic range
The highest harmonic of the output
spectrum when injecting a filtered sine
wave
Vout = 2 Vp-p, AV = +2,
RL = 1 kΩ
SFDR
F = 1 MHz
-87
-55
dBc
dBc
F = 10 MHz
1. Gain bandwidth product criterion is not applicable for CFA.
2. See Figure 10.
3. See Figure 11.
4. See Chapter 5 on page 14.
Note:
For Tmin < Tamb < Tmax, minimum and maximum values are the worst case of the parameter
on a standard lot along the entire temperature variation. The evaluation is performed on 50
units in Flat-8 package. The temperature curves on pages 6, 7 and 8 are a representation of
the average of these 50 units.
Table 4.
Closed-loop gain and feedback components
VCC (V)
Gain
Rfb (Ω)
+10
-10
+4
-4
100
180
150
300
1.2k
1k
2.5
+2
-2
+1
-1
3k
3k
Doc ID 15577 Rev 1
5/22
Electrical characteristics
RHF310
Figure 1.
Frequency response, positive gain Figure 2.
Frequency response vs. capa-load
10
8
24
22
20
18
16
14
12
10
8
C-Load=10pF
C-Load=4.7pF
R-iso=33 ohms
R-iso=0
Gain=+10
6
4
Gain=+4
Gain=+2
C-Load=22pF
R-iso=47ohms
2
0
Vin
6
4
+
-
Vout
-2
-4
-6
-8
-10
R-iso
2
Gain=+1
3k
0
-2
-4
1k
3k
C-Load
Small Signal
Vcc=5V
-6
-8
Gain=+2, Vcc=5V,
Small Signal
Load=1k
Ω
-10
1M
10M
100M
1M
10M
100M
Frequency (Hz)
Frequency (Hz)
Figure 3.
Output amplitude vs. load
Figure 4.
Input voltage noise vs. frequency
4.0
Gain=32dB
Rg=12ohms
Rfb=510ohms
non-inverting input in short-circuit
Vcc=5V
3.5
3.0
2.5
2.0
10
100
1k
10k
100k
Load (ohms)
Figure 5.
Distortion at 1 MHz
Figure 6.
Distortion at 10 MHz
-20
0
Vcc=5V
F=1MHz
Load=1k
Vcc=5V
F=10MHz
Load=1k
-30
-40
-50
-60
-70
-80
-90
-100
-10
-20
-30
-40
-50
-60
-70
-80
Ω
Ω
H2
H2
H3
H3
0
1
2
3
4
0
1
2
3
4
Output (Vp-p)
Output (Vp-p)
6/22
Doc ID 15577 Rev 1
RHF310
Electrical characteristics
Figure 7.
Positive slew-rate on 1 kΩ load
Figure 8.
Negative slew-rate on 1 kΩ load
Figure 9.
Quiescent current vs. V
Figure 10. I
CC
sink
150
400
200
0
125
100
75
Icc(+)
Gain=+2
Vcc=5V
Inputs to ground, no load
50
-200
Icc(-)
25
-400
1.25
1.50
1.75
2.00
2.25
2.50
0
-2.0
-1.5
-1.0
-0.5
0.0
+/-Vcc (V)
V (V)
Figure 11. I
Figure 12. Bandwidth vs. temperature
source
0
200
190
180
170
160
150
140
130
120
-25
-50
-75
-100
-125
110
Gain=+2
Vcc=5V
100
Load=1k
-40
Ω
90
-20
0
20
40
60
80
100
120
-150
0.0
0.5
1.0
1.5
2.0
Temperature (°C)
V (V)
Doc ID 15577 Rev 1
7/22
Electrical characteristics
RHF310
Figure 13. CMR vs. temperature
Figure 14. SVR vs. temperature
66
90
88
86
84
82
80
78
76
74
64
62
60
58
Vcc=5V
Load=1k
Vcc=5V
72
Ω
Load=1k
Ω
56
70
-40
-20
0
20
40
60
80
100
100
100
120
120
120
-40
-20
0
20
40
60
80
80
80
100
120
Temperature (°C)
Temperature (°C)
Figure 15. Slew rate vs. temperature
Figure 16. R vs. temperature
OL
140
1.60
1.55
1.50
1.45
1.40
1.35
1.30
neg. SR
130
120
pos. SR
110
100
Gain=+2
Vcc=5V
Load=1k
90
80
1.25
Open Loop
Ω
Vcc=5V
1.20
-40
-20
0
20
40
60
80
-40
-20
0
20
40
60
100
120
Temperature (°C)
Temperature (°C)
Figure 17. I
vs. temperature
Figure 18. V vs. temperature
bias
io
5
3.0
2.8
2.6
2.4
2.2
2.0
1.8
1.6
1.4
4
Ib(+)
3
2
1
0
Ib(−)
-1
-2 Vcc=5V
Open Loop
1.2
Vcc=5V
1.0
-3
-40
-20
0
20
40
60
80
-40
-20
0
20
40
60
100
120
Temperature (°C)
Temperature ( C)
8/22
Doc ID 15577 Rev 1
RHF310
Electrical characteristics
Figure 19. V and V vs. temperature
Figure 20. I
vs. temperature
OH
OL
out
200
150
100
50
2
1
VOH
Isource
Isink
0
0
-50
-1
-2
-3
-4
VOL
-100
-150
-200
Gain=+2
Vcc=+/-2.5V
Load=1k
Output: short-circuit
Vcc=5V
-250
-300
Ω
-40
-20
0
20
40
60
80
-40
-20
0
20
40
60
80
100
120
Temperature (°C)
Temperature (°C)
Figure 21. I vs. temperature
CC
400
Icc(+)
200
0
-200
Icc(-)
-400
-600
Gain=+2
Vcc=5V
no Load
-800
in(+) and in(-) to GND
-1000
-40
-20
0
20
40
60
80
100
120
Temperature ( C)
Doc ID 15577 Rev 1
9/22
Power supply considerations
RHF310
3
Power supply considerations
Correct power supply bypassing is very important to optimize the performance in high-
frequency ranges. The bypass capacitors should be placed as close as possible to the IC
pins to improve high-frequency bypassing. A capacitor greater than 1 µF is necessary to
minimize the distortion. For better quality bypassing, a capacitor of 10 nF can be added. It
should also be placed as close as possible to the IC pins. The bypass capacitors must be
incorporated for both the negative and positive supply.
Figure 22. Circuit for power supply bypassing
+VCC
10 µF
+
10 nF
+
-
10 nF
10 µF
+
-VCC
AM00835
3.1
Single power supply
If you use a single supply system, biasing is necessary to obtain a positive output dynamic
range between 0 V and +V supply rails. Considering the values of V and V , the
CC
OH
OL
amplifier will provide an output swing from +0.9 V to +4.1 V on 1 kΩ loads.
The amplifier must be biased with a mid-supply (nominally +V /2), in order to maintain the
CC
DC component of the signal at this value. Several options are possible to provide this bias
supply, such as a virtual ground using an operational amplifier or a two-resistance divider
(which is the cheapest solution). A high resistance value is required to limit the current
consumption. On the other hand, the current must be high enough to bias the non-inverting
input of the amplifier. If we consider this bias current (55 µA maximum) as 1% of the current
through the resistance divider, to keep a stable mid-supply, two resistances of 470 Ω can be
used.
The input provides a high-pass filter with a break frequency below 10 Hz, which is
necessary to remove the original 0 V DC component of the input signal, and to set it at
+V /2.
CC
Figure 23 on page 11 illustrates a 5 V single power supply configuration.
A capacitor C is added in the gain network to ensure a unity gain in low frequencies to
G
keep the right DC component at the output. C contributes to a high-pass filter with R //R
G
fb
G
and its value is calculated with a consideration of the cut-off frequency of this low-pass filter.
10/22
Doc ID 15577 Rev 1
RHF310
Power supply considerations
Figure 23. Circuit for +5 V single supply
+5 V
10 µF
+
IN
OUT
Rin
1 kΩ
+5 V
_
1 kΩ
R1
470 Ω
Rfb
RG
CG
+ 1 µF 10 nF
R2
470 Ω
+
AM00841
Doc ID 15577 Rev 1
11/22
Noise measurements
RHF310
4
Noise measurements
The noise model is shown in Figure 24.
●
●
●
eN: input voltage noise of the amplifier.
iNn: negative input current noise of the amplifier.
iNp: positive input current noise of the amplifier.
Figure 24. Noise model
+
Output
HP3577
+
-
iN
iN
R3
_
Input noise:
8 nV/√Hz
N3
eN
R2
N2
R1
N1
AM00837
The thermal noise of a resistance R is:
4kTRΔF
where ΔF is the specified bandwidth, and k is the Boltzmann's constant, equal to
1,374.10-23J/°K. T is the temperature (°K).
On a 1 Hz bandwidth the thermal noise is reduced to:
4kTR
The output noise eNo is calculated using the superposition theorem. However, eNo is not
the simple sum of all noise sources, but rather the square root of the sum of the square of
each noise source, as shown in Equation 1.
Equation 1
eNo = V12 + V22 + V32 + V42 + V52 + V62
12/22
Doc ID 15577 Rev 1
RHF310
Noise measurements
Equation 2
2
2
2
2
2
2
2
R22
R1
R22
R1
eNo2 = eN × g + iNn × R2 + iNp × R3 × g +
× 4kTR1 + 4kTR2 + 1 + ------- × 4kTR3
-------
The input noise of the instrumentation must be extracted from the measured noise value.
The real output noise value of the driver is:
Equation 3
eNo = (Measured)2 – (instrumentation)2
The input noise is called equivalent input noise because it is not directly measured but is
evaluated from the measurement of the output divided by the closed loop gain (eNo/g).
After simplification of the fourth and fifth terms of Equation 2, you obtain:
Equation 4
R22
R1
2
2
2
2
2
2
2
eNo2 = eN × g + iNn × R2 + iNp × R3 × g + g × 4kTR2 + 1 + ------- × 4kTR3
4.1
Measurement of the input voltage noise eN
Assuming a short-circuit on the non-inverting input (R3=0), from Equation 4 you can derive:
Equation 5
eNo = eN2 × g2 + iNn2 × R22 + g × 4kTR2
In order to easily extract the value of eN, the resistance R2 must be chosen to be as low as
possible. On the other hand, the gain must be high enough.
R3=0, gain: g=100
4.2
4.3
Measurement of the negative input current noise iNn
To measure the negative input current noise iNn, R3 is set to zero and Equation 5 is used.
This time, the gain must be lower in order to decrease the thermal noise contribution.
R3=0, gain: g=10
Measurement of the positive input current noise iNp
To extract iNp from Equation 3, a resistance R3 is connected to the non-inverting input. The
value of R3 must be chosen in order to keep its thermal noise contribution as low as
possible against the iNp contribution.
R3=100 Ω, gain: g=10
Doc ID 15577 Rev 1
13/22
Intermodulation distortion product
RHF310
5
Intermodulation distortion product
The non-ideal output of the amplifier can be described by the following series of equations.
Vout = C0 + C1Vin + C2V2in + …+ C Vn
in
n
where the input is V = Asinωt, C is the DC component, C (V ) is the fundamental and C
n
in
0
1
in
is the amplitude of the harmonics of the output signal V
.
out
A one-frequency (one-tone) input signal contributes to harmonic distortion. A two-tone input
signal contributes to harmonic distortion and to the intermodulation product.
The study of the intermodulation and distortion for a two-tone input signal is the first step in
characterizing the driving capability of multi-tone input signals.
In this case:
Vin = Asinω t + Asinω t
1
2
therefore:
Vout = C0 + C1(Asinω t + Asinω t) + C2(Asinω t + Asinω t)2…+ Cn(Asinω t + Asinω t)n
1
2
1
2
1
2
From this expression, we can extract the distortion terms, and the intermodulation terms
from a single sine wave.
●
Second-order intermodulation terms IM2 by the frequencies (ω -ω ) and (ω +ω ) with an
1 2 1 2
2
amplitude of C2A .
●
Third-order intermodulation terms IM3 by the frequencies (2ω -ω ), (2ω +ω ), (−ω +2ω )
1
2
1
2
1
2
3
and (ω +2ω ) with an amplitude of (3/4)C3A .
1
2
The intermodulation product of the driver is measured by using the driver as a mixer in a
summing amplifier configuration (Figure 25). In this way, the non-linearity problem of an
external mixing device is avoided.
14/22
Doc ID 15577 Rev 1
RHF310
Intermodulation distortion product
Figure 25. Inverting summing amplifier
Rfb
Vin1
R1
R2
Vin2
_
+
Vout
1 kΩ
R
AM00842
Doc ID 15577 Rev 1
15/22
Bias of an inverting amplifier
RHF310
6
Bias of an inverting amplifier
A resistance is necessary to achieve good input biasing, such as resistance R shown in
Figure 26.
The value of this resistance is calculated from the negative and positive input bias current.
The aim is to compensate for the offset bias current, which can affect the input offset voltage
and the output DC component. Assuming I , I , R , R and a 0 V output, the resistance
ib- ib+
in
fb
R is:
Rin × Rfb
R = ------------------------
R
in + Rfb
Figure 26. Compensation of the input bias current
Rfb
Rin
-
Iib
VCC
+
_
+
Output
Load
-
+
VCC
Iib
R
AM00839
16/22
Doc ID 15577 Rev 1
RHF310
Active filtering
7
Active filtering
Figure 27. Low-pass active filtering, Sallen-Key
C1
R1
R2
+
IN
OUT
C2
_
1 kΩ
Rfb
RG
AM00843
From the resistors R and R , it is possible to directly calculate the gain of the filter in a
fb
G
classic non-inverting amplification configuration.
Rfb
AV = g = 1 + --------
Rg
The response of the system is assumed to be:
Voutjω
g
Tjω = ---------------- = ----------------------------------------
(jω)2
Vinjω
jω
----
1 + 2ζ + -----------
ω 2
ω
c
c
The cut-off frequency is not gain-dependent and so becomes:
1
ω = ------------------------------------
c
R1R2C1C2
The damping factor is calculated using the following expression.
1
--
ζ = ω (C1R1 + C1R2 + C2R1 – C1R1g)
c
2
The higher the gain, the more sensitive the damping factor. When the gain is higher than 1,
it is preferable to use very stable resistor and capacitor values. In the case of R1=R2=R:
Rfb
--------
2C2 – C
1 Rg
ζ = --------------------------------
2 C1C2
Due to a limited selection of capacitor values in comparison with the resistors, you can set
C1=C2=C, so that:
Rfb
--------
2R2 – R
1 Rg
ζ = --------------------------------
2 R1R2
Doc ID 15577 Rev 1
17/22
Package information
RHF310
8
Package information
In order to meet environmental requirements, ST offers these devices in different grades of
®
®
ECOPACK packages, depending on their level of environmental compliance. ECOPACK
specifications, grade definitions and product status are available at: www.st.com.
®
ECOPACK is an ST trademark.
18/22
Doc ID 15577 Rev 1
RHF310
Package information
8.1
Ceramic Flat-8 package information
Figure 28. Ceramic Flat-8 package mechanical drawing
Table 5.
Ref.
Ceramic Flat-8 package mechanical data
Dimensions
Millimeters
Inches
Min.
Typ.
Max.
Min.
Typ.
Max.
A
b
2.24
0.38
0.10
6.35
6.35
4.32
0.88
2.44
0.43
0.13
6.48
6.48
4.45
1.01
1.27
3.00
0.79
1.12
08
2.64
0.48
0.16
6.61
6.61
4.58
1.14
0.088
0.015
0.004
0.250
0.250
0.170
0.035
0.096
0.017
0.005
0.255
0.255
0.175
0.040
0.050
0.118
0.031
0.044
08
0.104
0.019
0.006
0.260
0.260
0.180
0.045
c
D
E
E2
E3
e
L
Q
S1
N
0.66
0.92
0.92
1.32
0.026
0.036
0.092
0.052
Doc ID 15577 Rev 1
19/22
Ordering information
RHF310
9
Ordering information
Table 6.
Order codes
Description
Temperature
range
Order code
Package
Terminal finish
Marking
RHF310K-01V
RHF310K-02V
RHF310K1
Flight parts (QMLV) -55°C to +125°C
Flight parts (QMLV) -55°C to +125°C
Engineering samples -55°C to +125°C
Flat-8
Flat-8
Flat-8
Gold
Solder
Gold
TBD
TBD
RHF310K1
Engineeringsamples
-55°C to +125°C
RHF310K2
Flat-8
Gold
-
RHF310K2
No marking
with 48-hour burn-in
RHF310DIE2V
Flight parts (QMLV) -55°C to +125°C
Bare die
20/22
Doc ID 15577 Rev 1
RHF310
Revision history
10
Revision history
Table 7.
Date
26-May-2009
Document revision history
Revision
Changes
1
Initial release.
Doc ID 15577 Rev 1
21/22
RHF310
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Doc ID 15577 Rev 1
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