RHF330K-02V [STMICROELECTRONICS]
OP-AMP, 1930uV OFFSET-MAX, CDFP8, ROHS COMPLIANT, HERMETIC SEALED, CERAMIC, FLAT-8;
| 型号： | RHF330K-02V |
| 厂家： | 
ST |
| 描述： | OP-AMP, 1930uV OFFSET-MAX, CDFP8, ROHS COMPLIANT, HERMETIC SEALED, CERAMIC, FLAT-8 放大器 CD |
| 文件： | 总24页 (文件大小：748K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
RHF330
Rad-hard 1 GHz low noise operational amplifier
Preliminary data
Features
Pin connections
■ Bandwidth: 1 GHz (gain = +2)
■ Quiescent current: 16.6 mA
■ Slew rate: 1800 V/μs
(top view)
Ceramic Flat-8
■ Input noise: 1.3 nV/√Hz
■ Distortion: SFDR = -78 dBc (10 MHz, 2 V )
pp
■ 100 Ω load optimized output stage
■ 5 V power supply
1
4
8
5
NC
IN -
NC
■ 300 krad MIL-STD-883 1019.7 ELDRS free
+VCC
compliant
IN +
OUT
NC
■ SEL immune at 125° C, LET up to
-VCC
2
110 MEV.cm /mg
■ SET characterized, LET up to
2
110 MEV.cm /mg
Applications
■ Communication satellites
■ Space data acquisition systems
■ Aerospace instrumentation
■ Nuclear and high energy physics
■ Harsh radiation environments
■ ADC drivers
The RHF330 is a single operator available in the
Flat-8 hermetic ceramic package, saving board
space as well as providing excellent thermal and
dynamic performance.
Description
The RHF330 is a current feedback operational
amplifier that uses very high-speed
complementary technology to provide a large
bandwidth of 1 GHz in gains of 2 while drawing
only 16.6 mA of quiescent current. In addition, the
RHF330 offers 0.1 dB gain flatness up to
160 MHz with a gain of 2.
With a slew rate of 1800 V/µs and an output stage
optimized for standard 100 Ω load, this device is
highly suitable for applications where speed and
low-distortion are the main requirements.
May 2009
Doc ID 15576 Rev 1
1/24
This is preliminary information on a new product now in development or undergoing evaluation. Details are subject to
change without notice.
www.st.com
24
Contents
RHF330
Contents
1
2
3
4
Absolute maximum ratings and operating conditions . . . . . . . . . . . . . 3
Electrical characteristics . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4
Demonstration board schematics . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 10
Power supply considerations . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 12
4.1
Single power supply . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 12
5
Noise measurements . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 14
5.1
5.2
5.3
Measurement of the input voltage noise eN . . . . . . . . . . . . . . . . . . . . . . . 15
Measurement of the negative input current noise iNn . . . . . . . . . . . . . . . 15
Measurement of the positive input current noise iNp . . . . . . . . . . . . . . . . 15
6
7
8
9
Intermodulation distortion product . . . . . . . . . . . . . . . . . . . . . . . . . . . . 16
Bias of an inverting amplifier . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 18
Active filtering . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 19
Package information . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 20
9.1
Ceramic Flat-8 package information . . . . . . . . . . . . . . . . . . . . . . . . . . . . 21
10
11
Ordering information . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 22
Revision history . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 23
2/24
Doc ID 15576 Rev 1
RHF330
Absolute maximum ratings and operating conditions
1
Absolute maximum ratings and operating conditions
Table 1.
Symbol
Absolute maximum ratings
Parameter
Value
Unit
VCC
Vid
Supply voltage (1)
6
+/-0.5
+/-2.5
-55 to + 125
-65 to +150
150
V
V
Differential input voltage (2)
Vin
Input voltage range (3)
V
Toper
Tstg
Tj
Operating free air temperature range
Storage temperature
°C
°C
Maximum junction temperature
Flat-8 thermal resistance junction to ambient
Flat-8 thermal resistance junction to case
°C
Rthja
Rthjc
50
°C/W
°C/W
30
Flat-8 maximum power dissipation(4)
(Tamb = 25° C) for Tj = 150° C
Pmax
830
mW
kV
HBM: human body model (5)
pins 1, 4, 5, 6, 7 and 8
pins 2 and 3
2
0.6
MM: machine model (6)
V
ESD
pins 1, 4, 5, 6, 7 and 8
pins 2 and 3
200
80
CDM: charged device model(7)
pins 1, 4, 5, 6, 7 and 8
pins 2 and 3
kV
1.5
1
Latch-up immunity
200
mA
1. All voltage values are measured with respect to the ground pin.
2. Differential voltage is the non-inverting input terminal with respect to the inverting input terminal.
3. The magnitude of input and output voltage must never exceed VCC +0.3 V.
4. Short-circuits can cause excessive heating. Destructive dissipation can result from short-circuits on all
amplifiers.
5. Human body model: a 100 pF capacitor is charged to the specified voltage, then discharged through a
1.5 kΩ resistor between two pins of the device. This is done for all couples of connected pin combinations
while the other pins are floating.
6. This is a minimum value.
Machine model: a 200 pF capacitor is charged to the specified voltage, then discharged directly between
two pins of the device with no external series resistor (internal resistor < 5Ω). This is done for all couples of
connected pin combinations while the other pins are floating.
7. Charged device model: all pins and package are charged together to the specified voltage and then
discharged directly to the ground through only one pin.
Table 2.
Symbol
Operating conditions
Parameter
Value
Unit
VCC
Vicm
Supply voltage
4.5 to 5.5
V
-VCC +1.5 V to
+VCC-1.5V
Common mode input voltage
V
Doc ID 15576 Rev 1
3/24
Electrical characteristics
RHF330
2
Electrical characteristics
Table 3.
Electrical characteristics for V = 2.5 V, T
= +25° C
CC
amb
(unless otherwise specified)
Symbol
Parameter
Test conditions
Min.
Typ.
Max.
Unit
DC performance
Tamb
Tmin < Tamb < Tmax
Tamb
-3.1
0.18
26
7
+3.1
+1.93
55
Input offset voltage
Offset voltage between both inputs
Vio
mV
μA
μA
dB
(1)
-1.47
Non-inverting input bias current
DC current necessary to bias the + input
Iib+
Tmin < Tamb < Tmax
Tamb
5
48
22
Inverting input bias current
DC current necessary to bias the - input
Iib-
Tmin < Tamb < Tmax
ΔVic = 1 V
0
50
17
54
74
Common mode rejection ratio
CMR
20 log (ΔVic/ΔVio)
Tmin < Tamb < Tmax
ΔVCC = 3.5 V to 5 V
Tmin < Tamb < Tmax
50.5
60
Supply voltage rejection ratio
SVR
PSRR
ICC
dB
dB
20 log (ΔVCC/ΔVout
)
64
Power supply rejection ratio
ΔVCC = 200 mVpp at
1 kHz
56
20 log (ΔVCC/ΔVout
)
No load
16.6
20.2
17.5
mA
mA
Supply current
DC consumption with no input signal
Tmin < Tamb < Tmax
Dynamic performance and output characteristics
Transimpedance
Output voltage/input current gain in
open loop of a CFA.
For a VFA, the analog of this feature is
ΔVout= 1 V, RL = 100 Ω
104
123
153
kΩ
kΩ
ROL
Tmin < Tamb < Tmax
the open loop gain (AVD
)
Vout = 20 mVpp,
RL = 100 Ω
AV = +2
-3 dB bandwidth
Frequency where the gain is 3dB below
the DC gain AV
1000
630
AV = -4
550
Bw
AV = -4,
Tmin < Tamb < Tmax
MHz
TBD
TBD
160
Gain flatness at 0.1 dB
Band of frequency where the gain
variation does not exceed 0.1 dB
Small signal
Vout = 20 mVpp
AV = +2, RL = 100 Ω
Slew rate
Maximum output speed of sweep in
large signal
Vout = 2 Vpp, AV = +2,
RL = 100 Ω
SR
1800
1.64
V/μs
RL = 100 Ω
1.5
VOH
High level output voltage
V
Tmin < Tamb < Tmax
1.55
4/24
Doc ID 15576 Rev 1
RHF330
Table 3.
Electrical characteristics
Electrical characteristics for V = 2.5 V, T
= +25° C
CC
amb
(unless otherwise specified) (continued)
Symbol
Parameter
Test conditions
RL = 100 Ω
Min.
Typ.
Max.
Unit
-1.55
-1.5
VOL
Low level output voltage
V
Tmin < Tamb < Tmax
Output to GND
-1.49
Isink
360
390
453
Short-circuit output current coming into
the op-amp (2)
Tmin < Tamb < Tmax
Output to GND
Iout
mA
Isource
-320
-319
-400
Output current coming out from the
op-amp(3)
Tmin < Tamb < Tmax
Noise and distortion
eN
iN
Equivalent input noise voltage (4)
F = 100 kHz
F = 100 kHz
F = 100 kHz
1.3
22
16
nV/√Hz
pA/√Hz
pA/√Hz
Equivalent input noise current (+)(4)
Equivalent input noise current (-) (4)
AV = +2, Vout = 2 Vpp,
RL = 100 Ω
Spurious free dynamic range:
the highest harmonic of the output
F = 10 MHz
-78
-73
-48
-37
SFDR
dBc
spectrum when injecting a filtered sine F = 20 MHz
wave.
F = 100 MHz
F = 150 MHz
1. Worst case of the parameter on a standard sample across the range Tmin < Tamb < Tmax. The evaluation is done on 50
units in the SO-8 plastic package.
2. See Figure 11 for more details.
3. See Figure 10 for more details.
4. See Chapter 5 on page 14.
Table 4.
Closed-loop gain and feedback components
VCC (V)
Gain
Rfb (Ω)
+10
-10
+4
-4
200
200
240
240
300
270
300
270
2.5
+2
-2
+1
-1
Doc ID 15576 Rev 1
5/24
Electrical characteristics
RHF330
Figure 1.
Frequency response, positive gain Figure 2.
Flatness, gain = +2 compensated
6.5
6.1
6.0
5.9
5.8
24
22
20
18
16
14
12
10
8
Gain=10
Vin
Vout
100
+
-
0.5pF
300
300
Gain=4
Gain=2
Gain=1
Gain=+2, Vcc=+5V,
Small Signal
6
4
2
0
-2
-4
Small Signal
Vcc=5V
-6
-8
Load=100
Ω
-10
1M
10M
100M
1G
1M
10M
100M
1G
Frequency (Hz)
Frequency (Hz)
Figure 3.
Flatness, gain = +4 compensated
Figure 4.
Flatness, gain = +10 compensated
12.2
12.1
11.5
11.4
11.3
20.3
20.2
19.6
19.5
19.4
Vin
Vin
Vout
100
+
-
Vout
100
+
-
2.7pF
12pF
240
200
82
22
Gain=+4, Vcc=+5V,
Small Signal
Gain=+10, Vcc=+5V,
Small Signal
11.2
1M
19.3
1M
10M
100M
1G
10M
100M
1G
Frequency (Hz)
Frequency (Hz)
Figure 5.
Quiescent current vs. V
Figure 6.
Positive slew rate
CC
20
15
10
5
2.00
1.75
1.50
1.25
1.00
0.75
0.50
0.25
0.00
Gain=+2
Vcc=+5V
Load=100
Icc(+)
Ω
0
-5
-10
Icc(-)
Gain=+2
Vcc=5V
Input to ground, no load
-15
-20
0.0
0.5
1.0
1.5
2.0
2.5
-2ns
-1ns
0s
1ns
2ns
Vcc (V)
Time (ns)
6/24
Doc ID 15576 Rev 1
RHF330
Electrical characteristics
Figure 7.
Negative slew rate
Figure 8.
Output amplitude vs. load
2.00
1.75
1.50
1.25
1.00
0.75
0.50
0.25
0.00
4.0
Gain=+2
Vcc=+5V
Load=100
Ω
3.5
3.0
2.5
Gain=+2
Vcc=5V
Load=100
Ω
2.0
10
-2ns
-1ns
0s
1ns
2ns
100
1k
10k
100k
Time (ns)
Load (ohms)
Figure 9.
Distortion vs. amplitude
Figure 10. I
source
0
-50
Gain=+2
Vcc=+5V
F=10MHz
Load=100
-100
-150
-200
-250
-300
-350
-400
-450
-500
-550
Ω
HD2
HD3
-600
0.0
0.5
1.0
1.5
2.0
V (V)
Figure 11. I
Figure 12. Noise figure
sink
600
550
500
450
400
350
300
250
200
150
100
50
Vcc=5V
0
-2.0
-1.5
-1.0
-0.5
0.0
V (V)
Doc ID 15576 Rev 1
7/24
Electrical characteristics
RHF330
Figure 13. Input current noise vs. frequency
Figure 14. Input voltage noise vs. frequency
Gain=14.1dB
Rg=180ohms
Rfb=750ohms
Gain=37dB
Rg=10ohms
Rfb=750ohms
non-inverting input in short-circuit
Vcc=5V
non-inverting input in short-circuit
Vcc=5V
Neg. Current
Noise
Pos. Current
Noise
Figure 15. Reverse isolation vs. frequency
Figure 16. I
vs. temperature
out
0
2.0
1.5
Isource
-20
-40
-60
1.0
0.5
0.0
-0.5
-1.0
-1.5
-2.0
Isink
-80
Small Signal
Vcc=5V
Output: short-circuit
Vcc=5V
Load=100
Ω
-100
1M
10M
100M
1G
-40
-20
0
20
40
60
80
100
120
Frequency (Hz)
Temperature (°C)
Figure 17. CMR vs. temperature
Figure 18. SVR vs. temperature
85
80
75
70
65
60
64
62
60
58
56
54
52
50
Gain=+1
55
48
Vcc=5V
Vcc=5V
Load=100
Ω
46
Load=100Ω
50
-40
-20
0
20
40
60
80
100
120
-40
-20
0
20
40
60
80
100
120
Temperature (°C)
Temperature (°C)
8/24
Doc ID 15576 Rev 1
RHF330
Electrical characteristics
Figure 19. R vs. temperature
Figure 20. V and V vs. temperature
OH OL
OL
180
160
140
120
2
1
VOH
0
-1
-2
-3
-4
VOL
100
Gain=+2
Vcc=5V
Open Loop
Vcc=5V
Load=100
Ω
80
-40
-20
0
20
40
60
80
-40
-20
0
20
40
60
80
100
100
100
120
120
120
Temperature (°C)
Temperature (°C)
Figure 21. I
vs. temperature
Figure 22. I vs. temperature
bias
CC
30
28
26
24
22
20
18
16
14
12
10
20
15
Ib(+)
Icc(+)
10
5
0
-5
-10
Icc(-)
-15
Ib(−)
-20
Gain=+2
Vcc=5V
no Load
In+/In- to GND
-25
-30
-35
8
6
Vcc=5V
Load=100
Ω
-40
-20
0
20
40
60
80
-40
-20
0
20
40
60
80
100
120
Temperature (°C)
Temperature ( C)
Figure 23. V vs. temperature
io
1000
Open Loop
Vcc=5V
Load=100
Ω
800
600
400
200
0
-40
-20
0
20
40
60
80
Temperature ( C)
Doc ID 15576 Rev 1
9/24
Demonstration board schematics
RHF330
3
Demonstration board schematics
Figure 24. Electrical schematics (inverting and non-inverting gain configuration)
Figure 25. RHF3xx demonstration board
10/24
Doc ID 15576 Rev 1
RHF330
Demonstration board schematics
Figure 26. Top view layout
Figure 27. Bottom view layout
Doc ID 15576 Rev 1
11/24
Power supply considerations
RHF330
4
Power supply considerations
Correct power supply bypassing is very important for optimizing performance in high-
frequency ranges. The bypass capacitors should be placed as close as possible to the IC
pins to improve high-frequency bypassing. A capacitor greater than 1 μF is necessary to
minimize the distortion. For better quality bypassing, a 10 nF capacitor can be added. It
should also be placed as close as possible to the IC pins. The bypass capacitors must be
incorporated for both the negative and the positive supply.
For example, on the RHF3xx single op-amp demonstration board, these capacitors are C6,
C7, C8, C9.
Figure 28. Circuit for power supply bypassing
+VCC
10 µF
+
10 nF
+
-
10 nF
10 µF
+
-VCC
AM00835
4.1
Single power supply
In the event that a single supply system is used, biasing is necessary to obtain a positive
output dynamic range between 0 V and +V supply rails. Considering the values of V
CC
OH
and V , the amplifier will provide an output swing from +0.9 V to +4.1 V on a 100 Ω load.
OL
The amplifier must be biased with a mid-supply (nominally +V /2), in order to maintain the
CC
DC component of the signal at this value. Several options are possible to provide this bias
supply, such as a virtual ground using an operational amplifier or a two-resistance divider
(which is the cheapest solution). A high resistance value is required to limit the current
consumption. On the other hand, the current must be high enough to bias the non-inverting
input of the amplifier. If we consider this bias current (55 μA maximum) as 1% of the current
through the resistance divider, to keep a stable mid-supply, two resistances of 470 Ω can be
used.
The input provides a high-pass filter with a break frequency below 10 Hz which is necessary
to remove the original 0 V DC component of the input signal, and to set it at +V /2.
CC
Figure 29 on page 13 illustrates a 5 V single power supply configuration for the RHF3xx
single op-amp demonstration board.
12/24
Doc ID 15576 Rev 1
RHF330
Power supply considerations
A capacitor C is added in the gain network to ensure a unity gain in low frequencies to
G
keep the right DC component at the output. C contributes to a high-pass filter with R //R
G
fb
G
and its value is calculated with regard to the cut-off frequency of this low-pass filter.
Figure 29. Circuit for +5 V single supply
+5 V
10 µF
+
IN
+5 V
100 µ F
OUT
Rin
1 kΩ
_
100 Ω
R1
470 Ω
Rfb
RG
CG
+ 1 µF 10 nF
R2
470 Ω
+
AM00836
Doc ID 15576 Rev 1
13/24
Noise measurements
RHF330
5
Noise measurements
The noise model is shown in Figure 30.
●
●
●
eN: input voltage noise of the amplifier
iNn: negative input current noise of the amplifier
iNp: positive input current noise of the amplifier
Figure 30. Noise model
+
Output
HP3577
+
-
iN
iN
R3
_
Input noise:
8 nV/√Hz
N3
eN
R2
N2
R1
N1
AM00837
The thermal noise of a resistance R is:
4kTRΔF
where ΔF is the specified bandwidth.
On a 1 Hz bandwidth the thermal noise is reduced to:
4kTR
where k is the Boltzmann's constant, equal to 1,374.E(-23)J/°K. T is the temperature (°K).
The output noise eNo is calculated using the superposition theorem. However, eNo is not
the simple sum of all noise sources, but rather the square root of the sum of the square of
each noise source, as shown in Equation 1.
Equation 1
eNo = V12 + V22 + V32 + V42 + V52 + V62
14/24
Doc ID 15576 Rev 1
RHF330
Noise measurements
Equation 2
2
2
2
2
2
2
2
R22
R1
R22
R1
eNo2 = eN × g + iNn × R2 + iNp × R3 × g +
× 4kTR1 + 4kTR2 + 1 + ------- × 4kTR3
-------
The input noise of the instrumentation must be extracted from the measured noise value.
The real output noise value of the driver is:
Equation 3
eNo = (Measured)2 – (instrumentation)2
The input noise is called equivalent input noise because it is not directly measured but is
evaluated from the measurement of the output divided by the closed loop gain (eNo/g).
After simplification of the fourth and the fifth term of Equation 2 we obtain:
Equation 4
R22
R1
2
2
2
2
2
2
2
eNo2 = eN × g + iNn × R2 + iNp × R3 × g + g × 4kTR2 + 1 + ------- × 4kTR3
5.1
Measurement of the input voltage noise eN
If we assume a short-circuit on the non-inverting input (R3=0), from Equation 4 we can
derive:
Equation 5
eNo = eN2 × g2 + iNn2 × R22 + g × 4kTR2
In order to easily extract the value of eN, the resistance R2 will be chosen to be as low as
possible. On the other hand, the gain must be large enough.
R3=0, gain: g=100
5.2
5.3
Measurement of the negative input current noise iNn
To measure the negative input current noise iNn, we set R3=0 and use Equation 5. This
time, the gain must be lower in order to decrease the thermal noise contribution.
R3=0, gain: g=10
Measurement of the positive input current noise iNp
To extract iNp from Equation 3, a resistance R3 is connected to the non-inverting input. The
value of R3 must be chosen in order to keep its thermal noise contribution as low as
possible against the iNp contribution.
R3=100 W, gain: g=10
Doc ID 15576 Rev 1
15/24
Intermodulation distortion product
RHF330
6
Intermodulation distortion product
The non-ideal output of the amplifier can be described by the following series of equations.
Vout = C0 + C1Vin + C2V2in + …+ C Vn
in
n
where the input is V =Asinωt, C is the DC component, C (V ) is the fundamental and C is
in
0
1
in
n
the amplitude of the harmonics of the output signal V
.
out
A one-frequency (one-tone) input signal contributes to harmonic distortion. A two-tone input
signal contributes to harmonic distortion and to the intermodulation product.
The study of the intermodulation and distortion for a two-tone input signal is the first step in
characterizing the driving capability of multi-tone input signals.
In this case:
Vin = Asinω t + Asinω t
1
2
then:
Vout = C0 + C1(Asinω t + Asinω t) + C2(Asinω t + Asinω t)2…+ Cn(Asinω t + Asinω t)n
1
2
1
2
1
2
From this expression, we can extract the distortion terms and the intermodulation terms
from a single sine wave.
●
Second order intermodulation terms IM2 by the frequencies (ω -ω ) and (ω +ω ) with an
1 2 1 2
2
amplitude of C2A .
●
Third order intermodulation terms IM3 by the frequencies (2ω -ω ), (2ω +ω ), (−ω +2ω )
1
2
1
2
1
2
3
and (ω +2ω ) with an amplitude of (3/4)C3A .
1
2
The intermodulation product of the driver is measured by using the driver as a mixer in a
summing amplifier configuration (Figure 31 on page 17). In this way, the non-linearity
problem of an external mixing device is avoided.
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Doc ID 15576 Rev 1
RHF330
Intermodulation distortion product
Figure 31. Inverting summing amplifier
Rfb
Vin1
Vin2
R1
R2
_
+
Vout
100 Ω
R
AM00838
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Bias of an inverting amplifier
RHF330
7
Bias of an inverting amplifier
A resistance is necessary to achieve good input biasing, such as resistance R shown in
Figure 32.
The value of this resistance is calculated from the negative and positive input bias current.
The aim is to compensate for the offset bias current, which can affect the input offset voltage
and the output DC component. Assuming I , I , R , R and a zero volt output, the
ib- ib+
in
fb
resistance R is:
Rin × Rfb
R = ------------------------
R
in + Rfb
Figure 32. Compensation of the input bias current
Rfb
Rin
-
Iib
VCC
+
_
+
Output
Load
-
+
VCC
Iib
R
AM00839
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RHF330
Active filtering
8
Active filtering
Figure 33. Low-pass active filtering, Sallen-Key
C1
R1
R2
+
IN
OUT
C2
_
100 Ω
Rfb
RG
AM00840
From the resistors R and R we can directly calculate the gain of the filter in a classic non-
fb
G
inverting amplification configuration.
Rfb
AV = g = 1 + --------
Rg
We assume the following expression is the response of the system.
Voutjω
g
Tjω = ---------------- = ----------------------------------------
(jω)2
Vinjω
jω
----
1 + 2ζ + -----------
ω 2
ω
c
c
The cut-off frequency is not gain-dependent and so becomes:
1
ω = ------------------------------------
c
R1R2C1C2
The damping factor is calculated by the following expression.
1
--
ζ = ω (C1R1 + C1R2 + C2R1 – C1R1g)
c
2
The higher the gain, the more sensitive the damping factor is. When the gain is higher than
1, it is preferable to use very stable resistor and capacitor values. In the case of R1=R2=R:
Rfb
--------
2C2 – C
1 Rg
ζ = --------------------------------
2 C1C2
Due to a limited selection of capacitor values in comparison with resistors, we can set
C1=C2=C, so that:
Rfb
--------
2R2 – R
1 Rg
ζ = --------------------------------
2 R1R2
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Package information
RHF330
9
Package information
In order to meet environmental requirements, ST offers these devices in different grades of
®
®
ECOPACK packages, depending on their level of environmental compliance. ECOPACK
specifications, grade definitions and product status are available at: www.st.com.
®
ECOPACK is an ST trademark.
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RHF330
Package information
9.1
Ceramic Flat-8 package information
Figure 34. Ceramic Flat-8 package mechanical drawing
Table 5.
Ref.
Ceramic Flat-8 package mechanical data
Dimensions
Millimeters
Inches
Min.
Typ.
Max.
Min.
Typ.
Max.
A
b
2.24
0.38
0.10
6.35
6.35
4.32
0.88
2.44
0.43
0.13
6.48
6.48
4.45
1.01
1.27
3.00
0.79
1.12
08
2.64
0.48
0.16
6.61
6.61
4.58
1.14
0.088
0.015
0.004
0.250
0.250
0.170
0.035
0.096
0.017
0.005
0.255
0.255
0.175
0.040
0.050
0.118
0.031
0.044
08
0.104
0.019
0.006
0.260
0.260
0.180
0.045
c
D
E
E2
E3
e
L
Q
S1
N
0.66
0.92
0.92
1.32
0.026
0.036
0.092
0.052
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Ordering information
RHF330
10
Ordering information
Table 6.
Order codes
Description
Temperature
range
Order code
Package
Terminal finish
Marking
RHF330K-01V
RHF330K-02V
RHF330K1
Flight parts (QMLV) -55°C to +125°C
Flight parts (QMLV) -55°C to +125°C
Engineering samples -55°C to +125°C
Flat-8
Flat-8
Flat-8
Gold
Solder
Gold
TBD
TBD
RHF330K1
Engineeringsamples
-55°C to +125°C
RHF330K2
Flat-8
Gold
-
RHF330K2
No marking
with 48-hrs burn-in
RHF330DIE2V
Flight parts (QMLV) -55°C to +125°C
Bare die
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RHF330
Revision history
11
Revision history
Table 7.
Date
20-May-2009
Document revision history
Revision
Changes
1
Initial release.
Doc ID 15576 Rev 1
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RHF330
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Doc ID 15576 Rev 1
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