LM7341MFX [NSC]
±15V, 4.6 MHz GBW, Operational Amplifier in SOT-23 Package; ± 15V ， 4.6 MHz的增益带宽积，采用SOT- 23封装运算放大器
| 型号： | LM7341MFX |
| 厂家： | 
National Semiconductor |
| 描述： | ±15V, 4.6 MHz GBW, Operational Amplifier in SOT-23 Package |
| 文件： | 总20页 (文件大小：567K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
October 13, 2008
LM7341 Rail-to-Rail Input/Output
±15V, 4.6 MHz GBW, Operational Amplifier in SOT-23
Package
General Description
Features
The LM7341 is a rail-to-rail input and output amplifier in a
small SOT-23 package with a wide supply voltage and tem-
perature range. The LM7341 has a 4.6 MHz gain bandwidth
and a 1.9 volt per microsecond slew rate, and draws 0.75 mA
of supply current at no load.
(VS = ±15V, TA = 25°C, typical values.)
Tiny 5-pin SOT-23 package saves space
Greater than rail-to-rail input CMVR
Rail-to-rail output swing
Supply current
■
−15.3V to 15.3V
−14.84V to 14.86V
0.7 mA
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The LM7341 is tested at −40°C, 125°C and 25°C with modern
automatic test equipment. Detailed performance specifica-
tions at 2.7V, ±5V, and ±15V and over a wide temperature
range make the LM7341 a good choice for automotive, in-
dustrial, and other demanding applications.
Gain bandwidth
4.6 MHz
1.9 V/µs
2.7V to 32V
106 dB
Slew Rate
Wide supply range
High power supply rejection ratio
High common mode rejection ratio
Excellent gain
115 dB
106 dB
−40°C to 125°C
Greater than rail-to-rail input common mode range with a
minimum 76 dB of common mode rejection at ±15V makes
the LM7341 a good choice for both high and low side sensing
applications.
Temperature range
Tested at −40°C, 125°C and 25°C at 2.7V, ±5V and ±15V
LM7341 performance is consistent over a wide voltage range,
making the part useful for applications where the supply volt-
age can change, such as automotive electrical systems and
battery powered electronics.
Applications
Automotive
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Industrial robotics
The LM7341 uses a small SOT23-5 package, which takes up
little board space, and can be placed near signal sources to
reduce noise pickup.
Sensor output buffers
Multiple voltage power supplies
Reverse biasing of photodiodes
Low current optocouplers
High side sensing
Comparator
Battery chargers
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Test point output buffers
Below ground current sensing
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Typical Performance Characteristics
Open Loop Frequency Response
Open Loop Frequency Response
20206046
20206047
© 2008 National Semiconductor Corporation
202060
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Power Supply Current
Soldering Information
Infrared or Convection (20 sec)
Wave Soldering Lead Temp.
(10 sec.)
25 mA
235°C
Absolute Maximum Ratings (Note 1)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales Office/
Distributors for availability and specifications.
260°C
−65°C to 150°C
150°C
ESD Tolerance (Note 2)
Storage Temperature Range
Junction Temperature (Note 4)
Human Body Model
Machine Model
Charge-Device Model
VIN Differential
2000V
200V
1000V
Operating Ratings (Note 1)
±15V
Supply Voltage (VS = V+ − V−)
Temperature Range (Note 4)
2.5V to 32V
−40°C to 125°C
Voltage at Input/Output Pin
Supply Voltage (VS = V+ − V−)
Input Current
(V+) + 0.3V, (V−) −0.3V
35V
±10 mA
±20 mA
Package Thermal Resistance (θJA
5-Pin SOT-23
)
325°C/W
Output Current(Note 3)
2.7V Electrical Characteristics
Unless otherwise specified, all limits guaranteed for TA = 25°C, V+ = 2.7V, V− = 0V, VCM = 0.5V, VOUT = 1.35V and RL > 1 MΩ to
1.35V. Boldface limits apply at the temperature extremes
Symbol
Parameter
Conditions
Min
Typ
Max
Units
(Note 6)
(Note 5)
(Note 6)
VOS
Input Offset Voltage
VCM = 0.5V and VCM = 2.2V
−4
−5
±0.2
+4
+5
mV
TCVOS
IB
Input Offset Voltage Temperature Drift
Input Bias Current
±2
μV/°C
VCM = 0.5V
−180
−90
−200
nA
nA
VCM = 2.2V
30
1
60
70
IOS
Input Offset Current
VCM = 0.5V and VCM = 2.2V
40
50
CMRR
Common Mode Rejection Ratio
82
80
106
80
0V ≤ VCM ≤ 1.0V
0V ≤ VCM ≤ 2.7V
dB
dB
62
60
PSRR
Power Supply Rejection Ratio
86
84
106
2.7V ≤ VS ≤ 30V
VCM = 0.5V
CMVR
AVOL
Common Mode Voltage Range
Open Loop Voltage Gain
CMRR > 60 dB
−0.3
3.0
65
0.0
V
2.7
12
8
0.5V ≤ VO ≤ 2.2V
RL = 10 kΩ to 1.35V
V/mV
VOUT
Output Voltage Swing
High
50
95
120
150
RL = 10 kΩ to 1.35V
VID = 100 mV
150
200
RL = 2 kΩ to 1.35V
VID = 100 mV
mV from
either rail
Output Voltage Swing
Low
55
120
150
RL = 10 kΩ to 1.35V
VID = −100 mV
100
12
150
200
RL = 2 kΩ to 1.35V
VID = −100 mV
IOUT
Output Current
Sourcing, VOUT = 0V
VID = 200 mV
6
4
mA
Sinking, VOUT = 0V
VID = −200 mV
5
3
10
IS
Supply Current
Slew Rate
VCM = 0.5V and VCM = 2.2V
0.6
1.5
0.9
1.0
mA
SR
±1V Step
V/μs
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2
Symbol
Parameter
Gain Bandwidth
Conditions
Min
(Note 6)
Typ
(Note 5)
Max
(Note 6)
Units
GBW
en
3.6
35
MHz
f = 100 kHz, RL = 100 kΩ
Input Referred Voltage Noise Density
Input Referred Voltage Noise Density
f = 1 kHz
nV/
pA/
dB
in
f = 1 kHz
0.28
THD+N
tPD
Total Harmonic Distortion + Noise
Propagation Delay
f = 10 kHz
−66
4
Overdrive = 50 mV (Note 7)
Overdrive = 1V (Note 7)
20% to 80% (Note 7)
80% to 20% (Note 7)
µs
3
tr
tf
Rise Time
Fall Time
1
µs
µs
1
±5V Electrical Characteristics
Unless otherwise specified, all limits guaranteed for TA = 25°C, V+ = +5V, V− = −5V, VCM = VOUT = 0V and RL > 1 MΩ to 0V.
Boldface limits apply at the temperature extremes.
Symbol
Parameter
Conditions
Min
Typ
Max
Units
(Note 6)
(Note 5) (Note 6)
VOS
Input Offset Voltage
VCM = −4.5V and VCM = 4.5V
−4
−5
±0.2
+4
+5
mV
TCVOS
IB
Input Offset Voltage Temperature Drift
Input Bias Current
±2
μV/°C
VCM = −4.5V
−200
−95
−250
nA
nA
dB
VCM = 4.5V
35
1
70
80
IOS
Input Offset Current
VCM = −4.5V and VCM = 4.5V
40
50
CMRR
Common Mode Rejection Ratio
84
82
112
92
−5V ≤ VCM ≤ 3V
72
−5V ≤ VCM ≤ 5V
70
PSRR
CMVR
Power Supply Rejection Ratio
Common Mode Voltage Range
86
84
106
2.7V ≤ VS ≤ 30V, VCM = −4.5V
CMRR ≥ 65 dB
dB
V
−5.3
5.3
−5.0
5.0
AVOL
Open Loop Voltage Gain
20
12
110
−4V ≤ VO ≤ 4V
RL = 10 kΩ to 0V
V/mV
VOUT
Output Voltage Swing
High
80
170
90
150
200
RL = 10 kΩ to 0V,
VID = 100 mV
300
400
RL = 2 kΩ to 0V,
VID = 100 mV
mV from
either rail
Output Voltage Swing
Low
150
200
RL = 10 kΩ to 0V
VID = −100 mV
210
11
300
400
RL = 2 kΩ to 0V
VID = −100 mV
IOUT
Output Current
Supply Current
Sourcing, VOUT = −5V
VID = 200 mV
6
4
mA
mA
Sinking, VOUT = 5V
VID = −200 mV
6
4
12
IS
VCM = −4.5V and VCM = 4.5V
0.65
1.0
1.1
SR
Slew Rate
±4V Step
1.7
4.0
V/μs
MHz
GBW
Gain Bandwidth
f = 100 kHz, RL = 100 kΩ
3
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Symbol
en
Parameter
Conditions
Min
(Note 6)
Typ
Max
Units
(Note 5) (Note 6)
Input Referred Voltage Noise Density
Input Referred Voltage Noise Density
f = 1 kHz
f = 1 kHz
33
nV/
pA/
dB
in
0.26
THD+N
tPD
Total Harmonic Distortion + Noise
Propagation Delay
f = 10 kHz
−66
8
Overdrive = 50 mV (Note 7)
Overdrive = 1V (Note 7)
20% to 80% (Note 7)
80% to 20% (Note 7)
µs
6
tr
tf
Rise Time
Fall Time
5
µs
µs
5
±15V Electrical Characteristics
Unless otherwise specified, all limits guaranteed for TA = 25°C, V+ = 15V, V− = −15V, VCM = VOUT = 0V and RL > 1 MΩ to 0V.
Boldface limits apply at the temperature extremes
Symbol
Parameter
Conditions
Min
Typ
Max
Units
(Note 6)
(Note 5)
(Note 6)
VOS
Input Offset Voltage
VCM = −14.5V and VCM = 14.5V
−4
−5
±0.2
+4
+5
mV
TCVOS
IB
Input Offset Voltage Temperature Drift
Input Bias Current
±2
μV/°C
VCM = −14.5V
−250
−110
−300
nA
nA
dB
VCM = 14.5V
40
1
80
90
IOS
Input Offset Current
VCM = −14.5V and VCM = 14.5V
40
50
CMRR
Common Mode Rejection Ratio
84
82
115
100
106
−15V ≤ VCM ≤12V
−15V ≤ VCM ≤ 15V
78
76
PSRR
CMVR
Power Supply Rejection Ratio
Common Mode Voltage Range
86
84
2.7V ≤ VS ≤ 30V, VCM = −14.5V
dB
V
CMRR > 80 dB
−15.3
15.3
200
−15.0
15.0
AVOL
Open Loop Voltage Gain
25
15
−13V ≤ VO ≤ 13V
RL = 10 kΩ to 0V
V/mV
VOUT
Output Voltage Swing
High
135
160
10
300
400
RL = 10 kΩ to 0V
VID = 100 mV
mV from
either rail
Output Voltage Swing
Low
300
400
RL = 10 kΩ to 0V
VID = −100 mV
IOUT
Output Current
(Note 4)
Sourcing, VOUT = −15V
VID = 200 mV
5
3
mA
mA
Sinking, VOUT = 15V
VID = −200 mV
8
5
13
IS
Supply Current
VCM = −14.5V and VCM = 14.5V
0.7
1.2
1.3
SR
Slew Rate
±12V Step
1.9
4.6
31
V/μs
MHz
GBW
en
Gain Bandwidth
f = 100 kHz, RL = 100 kΩ
f = 1 kHz
Input Referred Voltage Noise Density
nV/
in
Input Referred Voltage Noise Density
f = 1 kHz
0.27
pA/
dB
THD+N
tPD
Total Harmonic Distortion + Noise
Propagation Delay
f = 10 kHz
−65
17
Overdrive = 50 mV (Note 7)
Overdrive = 1V (Note 7)
µs
12
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4
Symbol
Parameter
Conditions
Min
Typ
Max
Units
(Note 6)
(Note 5)
(Note 6)
tr
tf
Rise Time
Fall Time
20% to 80% (Note 7)
80% to 20% (Note 7)
13
13
µs
µs
Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is
intended to be functional, but specific performance is not guaranteed. For guaranteed specifications and the test conditions, see the Electrical Characteristics.
Note 2: Human Body Model, applicable std. MIL-STD-883, Method 3015.7. Machine Model, applicable std. JESD22-A115-A (ESD MM std. of JEDEC)
Field-Induced Charge-Device Model, applicable std. JESD22-C101-C (ESD FICDM std. of JEDEC).
Note 3: Applies to both single-supply and split-supply operation. Continuous short circuit operation at elevated ambient temperature can result in exceeding the
maximum allowed junction temperature of 150°C.
Note 4: The maximum power dissipation is a function of TJ(MAX), θJA. The maximum allowable power dissipation at any ambient temperature is
PD = (TJ(MAX) − TA)/θJA. All numbers apply for packages soldered directly unto a PC board.
Note 5: Typical values represent the most likely parametric norm as determined at the time of characterization. Actual typical values may vary over time and will
also depend on the application and configuration. The typical values are not tested and are not guaranteed on shipped production material.
Note 6: All limits are guaranteed by testing or statistical analysis.
Note 7: The maximum differential voltage between the input pins is VIN Differential = ±15V.
Connection Diagram
5-Pin SOT-23
20206002
Top View
Ordering Information
Package
Part Number
LM7341MF
Package Marking
Transport Media
1k Units Tape and Reel
250 Units Tape and Reel
3k Units Tape and Reel
NSC Drawing
5-Pin SOT-23
LM7341MFE
LM7341MFX
AV4A
MF05A
5
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Typical Performance Characteristics
Output Swing vs. Sourcing Current
Output Swing vs. Sinking Current
Output Swing vs. Sinking Current
Output Swing vs. Sinking Current
20206030
20206033
20206034
20206035
Output Swing vs. Sourcing Current
20206031
Output Swing vs. Sourcing Current
20206032
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VOS Distribution
VOS vs. VCM (Unit 1)
20206040
20206003
VOS vs. VCM (Unit 2)
VOS vs. VCM (Unit 3)
20206004
20206008
VOS vs. VCM (Unit 1)
VOS vs. VCM (Unit 2)
20206006
20206007
7
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VOS vs. VCM (Unit 3)
VOS vs. VCM (Unit 1)
20206011
20206010
VOS vs. VCM (Unit 2)
VOS vs. VCM (Unit 3)
20206005
20206009
VOS vs. VS (Unit 1)
VOS vs. VS (Unit 2)
20206012
20206013
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VOS vs. VS (Unit 3)
VOS vs. VS (Unit 2)
IBIAS vs. VCM
VOS vs. VS (Unit 1)
VOS vs. VS (Unit 3)
IBIAS vs. VCM
20206014
20206015
20206017
20206019
20206016
20206018
9
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IBIAS vs. VCM
IBIAS vs. VS
IS vs. VCM
IBIAS vs. VS
IS vs. VCM
IS vs. VCM
20206020
20206021
20206024
20206025
20206026
20206027
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IS vs. VCM
IS vs. VCM
20206029
20206028
Positive Output Swing vs. Supply Voltage
Positive Output Swing vs. Supply Voltage
20206036
20206037
Negative Output Swing vs. Supply Voltage
Negative Output Swing vs. Supply Voltage
20206039
20206038
11
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Open Loop Frequency with Various Capacitive Load
Open Loop Frequency with Various Resistive Load
20206044
20206045
Open Loop Frequency with Various Supply Voltage
Open Loop Frequency Response with Various Temperatures
20206046
20206047
CMRR vs. Frequency
+PSRR vs. Frequency
20206043
20206041
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-PSRR vs. Frequency
Small Signal Step Response
20206051
20206042
Large Signal Step Response
Input Referred Noise Density vs. Frequency
20206052
20206048
Input Referred Noise Density vs. Frequency
Input Referred Noise Density vs. Frequency
20206049
20206050
13
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THD+N vs. Frequency
20206053
SPECIFIC ADVANTAGES OF 5-Pin SOT-23 (TinyPak)
Application Information
The obvious advantage of the 5-pin SOT-23, TinyPak, is that
it can save board space, a critical aspect of any portable or
miniaturized system design. The need to decrease overall
system size is inherent in any handheld, portable, or
lightweight system application.
GENERAL INFORMATION
Low supply current and wide bandwidth, greater than rail-to-
rail input range, full rail-to-rail output, good capacitive load
driving ability, wide supply voltage and low distortion all make
the LM7341 ideal for many diverse applications.
Furthermore, the low profile can help in height limited designs,
such as consumer hand-held remote controls, sub-notebook
computers, and PCMCIA cards.
The high common-mode rejection ratio and full rail-to-rail in-
put range provides precision performance when operated in
non-inverting applications where the common-mode error is
added directly to the other system errors.
An additional advantage of the tiny package is that it allows
better system performance due to ease of package place-
ment. Because the tiny package is so small, it can fit on the
board right where the op amp needs to be placed for optimal
performance, unconstrained by the usual space limitations.
This optimal placement of the tiny package allows for many
system enhancements, not easily achieved with the con-
straints of a larger package. For example, problems such as
system noise due to undesired pickup of digital signals can
be easily reduced or mitigated. This pick-up problem is often
caused by long wires in the board layout going to or from an
op amp. By placing the tiny package closer to the signal
source and allowing the LM7341 output to drive the long wire,
the signal becomes less sensitive to such pick-up. An overall
reduction of system noise results.
CAPACITIVE LOAD DRIVING
The LM7341 has the ability to drive large capacitive loads. For
example, 1000 pF only reduces the phase margin to about 30
degrees.
POWER DISSIPATION
Although the LM7341 has internal output current limiting,
shorting the output to ground when operating on a +30V pow-
er supply will cause the op amp to dissipate about 350 mW.
This is a worst-case example. In the 5-pin SOT-23 package,
the higher thermal resistance will cause a calculated rise of
113°C. This can raise the junction temperature to above the
absolute maximum temperature of 150°C.
Often times system designers try to save space by using dual
or quad op amps in their board layouts. This causes a com-
plicated board layout due to the requirement of routing several
signals to and from the same place on the board. Using the
tiny op amp eliminates this problem.
Operating from split supplies greatly reduces the power dis-
sipated when the output is shorted. Operating on ±15V sup-
plies can only cause a temperature rise of 57°C in the 5-pin
SOT-23 package, assuming the short is to ground.
Additional space savings parts are available in tiny packages
from National Semiconductor, including low power amplifiers,
precision voltage references, and voltage regulators.
WIDE SUPPLY RANGE
The high power-supply rejection ratio (PSRR) and common
mode rejection ratio (CMRR) provide precision performance
when operated on battery or other unregulated supplies. This
advantage is further enhanced by the very wide supply range
(2.5V–32V) offered by the LM7341. In situations where highly
variable or unregulated supplies are present, the excellent
PSRR and wide supply range of the LM7341 benefit the sys-
tem designer with continued precision performance, even in
such adverse supply conditions.
LOW DISTORTION, HIGH OUTPUT DRIVE CAPABILITY
The LM7341 offers superior low-distortion performance, with
a total-harmonic-distortion-plus-noise of −66 dB at f = 10 kHz.
The advantage offered by the LM7341 is its low distortion
levels, even at high output current and low load resistance.
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14
Typical Applications
HANDHELD REMOTE CONTROLS
The LM7341 offers outstanding specifications for applications
requiring good speed/power trade-off. In applications such as
remote control operation, where high bandwidth and low pow-
er consumption are needed. The LM7341 performance can
easily meet these requirements.
OPTICAL LINE ISOLATION FOR MODEMS
The combination of the low distortion and good load driving
capabilities of the LM7341 make it an excellent choice for
driving opto-coupler circuits to achieve line isolation for
modems. This technique prevents telephone line noise from
coupling onto the modem signal. Superior isolation is
achieved by coupling the signal optically from the computer
modem to the telephone lines; however, this also requires a
low distortion at relatively high currents. Due to its low distor-
tion at high output drive currents, the LM7341 fulfills this need,
in this and in other telecom applications.
20206054
FIGURE 1. Inverting Comparator
Similarly a non-inverting comparator at VS = 30V and 1V of
overdrive there is typically 12 µs of propagation delay. At
VS = 30V and 50 mV of overdrive there is typically 17 μs of
propagation delay.
REMOTE MICROPHONE IN PERSONAL COMPUTERS
Remote microphones in Personal Computers often utilize a
microphone at the top of the monitor which must drive a long
cable in a high noise environment. One method often used to
reduce the nose is to lower the signal impedance, which re-
duces the noise pickup. In this configuration, the amplifier
usually requires 30 dB–40 dB of gain, at bandwidths higher
than most low-power CMOS parts can achieve. The LM7341
offers the tiny package, higher bandwidths, and greater out-
put drive capability than other rail-to-rail input/output parts can
provide for this application.
20206055
LM7341 AS A COMPARATOR
FIGURE 2. Non-Inverting Comparator
The LM7341 can also be used as a comparator and provides
quite reasonable performance. Note however that unlike a
typical comparator an op amp has a maximum allowed dif-
ferential voltage between the input pins. For the LM7341, as
stated in the Absolute Maximum Ratings section, this maxi-
mum voltage is VIN Differential = ±15V. Beyond this limit, even
for a short time, damage to the device may occur.
COMPARATOR WITH HYSTERESIS
The basic comparator configuration may oscillate or produce
a noisy output if the applied differential input voltage is near
the comparator's offset voltage. This usually happens when
the input signal is moving very slowly across the comparator's
switching threshold. This problem can be prevented by the
addition of hysteresis or positive feedback.
As an inverting comparator at VS = 30V and 1V of overdrive
there is typically 12 μs of propagation delay. At VS = 30V and
50 mV of overdrive there is typically 17 µs of propagation de-
lay.
15
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INVERTING COMPARATOR WITH HYSTERESIS
sistors can be presented as R2||R3 in series with R1. The
upper trip voltage VA2 is defined as
The inverting comparator with hysteresis requires a three re-
sistor network that is referenced to the supply voltage VCC of
the comparator, as shown in Figure 3. When VIN at the in-
verting input is less than VA, the voltage at the non-inverting
node of the comparator (VIN < VA), the output voltage is high
(for simplicity assume VOUT switches as high as VCC). The
three network resistors can be represented as R1||R3 in series
with R2. The lower input trip voltage VA1 is defined as
VA2 = VCC (R2||R3) / ((R1+ (R2||R3)
The total hysteresis provided by the network is defined as
Delta VA = VA1- VA2
For example to achieve 50 mV of hysteresis when VCC = 30V
set R1 = 4.02 kΩ, R2 = 4.02 kΩ, and R3 = 1.21 MΩ. With these
resistors selected the error due to input bias current is ap-
proximately 1 mV. To minimize this error it is best to use low
resistor values on the inputs.
VA1 = VCCR2 / ((R1||R3) + R2)
When VIN is greater than VA (VIN > VA), the output voltage is
low, very close to ground. In this case the three network re-
20206056
FIGURE 3. Inverting Comparator with Hysteresis
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16
NON-INVERTING COMPARATOR WITH HYSTERESIS
VIN2 = (VREF (R1+ R2) - VCCR1)/R2
A non-inverting comparator with hysteresis requires a two re-
sistor network, and a voltage reference (VREF) at the inverting
input. When VIN is low, the output is also low. For the output
to switch from low to high, VIN must rise up to VIN1 where
VIN1 is calculated by
The hysteresis of this circuit is the difference between VIN1
and VIN2
.
Delta VIN = VCCR1/R2
For example to achieve 50 mV of hysteresis when VCC = 30V
set R1 = 20Ω and R2 = 12.1 kΩ.
VIN1 = R1*(VREF/R2) + VREF
When VIN is high, the output is also high, to make the com-
parator switch back to it's low state, VIN must equal VREF
before VA will again equal VREF . VIN can be calculated by
20206057
20206058
FIGURE 4. Non-Inverting Comparator with Hysteresis
OTHER SOT-23 AMPLIFIERS
SMALLER SC70 AMPLIFIERS
The LM7321 is a rail-to-rail input and output amplifier that can
tolerate unlimited capacitive load. It works from 2.7V to ±15V
and across the −40°C to 125°C temperature range. It has 20
MHz gain-bandwidth, and is available in both 5-Pin SOT-23
and 8-Pin SOIC packages.
The LMV641 is a 10 MHz amplifier which uses only 140 micro
amps of supply current. The input voltage offset is less than
0.5 mV.
The LMV851 is an 8 MHz amplifier which uses only 0.4 mA
supply current, and is available in the smaller SC70 package.
The LMV851 also resists Electro Magnetic Interference (EMI)
from mobile phones and similar high frequency sources. It
works on 2.7V to 5.5 V supplies.
The LM6211 is a 20 MHz part with CMOS input, which runs
on 5V to 24V single supplies. It has rail-to-rail output and low
noise.
The LMP7701 is a rail-to-rail input and output precision part
with an input voltage offset under 220 microvolts and low
noise. It has 2.5 MHz bandwidth and works on 2.7V to 12V
supplies.
Detailed information on these and a wide range of other parts
can be found at www.national.com.
17
www.national.com
Physical Dimensions inches (millimeters) unless otherwise noted
5-Pin SOT-23
NS Package Number MF05A
www.national.com
18
Notes
19
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Notes
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相关型号：
LM7341MFX/NOPB
Rail-to-Rail Input/Output ±15V, 4.6 MHz GBW, Operational Amplifier in SOT-23 Package
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