MP28315CN [MPS]
3A, 16V, 340KHz Synchronous Rectified Step-Down Converter;
| 型号： | MP28315CN |
| 厂家： | 
MONOLITHIC POWER SYSTEMS |
| 描述： | 3A, 16V, 340KHz Synchronous Rectified Step-Down Converter 开关 光电二极管 |
| 文件： | 总11页 (文件大小：363K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
TM
MP28315
3A, 16V, 340KHz Synchronous Rectified
Step-Down Converter
TM
The Future of Analog IC Technology
DESCRIPTION
FEATURES
The MP28315 is a monolithic synchronous buck
regulator. The device integrates 100mΩ
MOSFETS that provide 3A continuous load
current over a wide operating input voltage of
5V to 16V. Current mode control provides fast
transient response and cycle-by-cycle current
limit.
•
•
•
•
•
•
•
•
•
•
•
3A Output Current
Wide 5V to 16V Operating Input Range
Integrated 100mΩ Power MOSFET Switches
Output Adjustable from 0.925V to 13V
Up to 95% Efficiency
Programmable Soft-Start
Stable with Low ESR Ceramic Output Capacitors
Fixed 340KHz Frequency
Cycle-by-Cycle Over Current Protection
Input Under-Voltage Lockout
Thermally Enhanced 8-Pin SOIC Package
An adjustable soft-start prevents inrush current
at turn-on. In shutdown mode, the supply
current drops below 1µA.
This device, available in an 8-pin SOIC
package, provides a very compact system
solution with minimal reliance on external
components.
APPLICATIONS
•
•
•
•
•
Distributed Power Systems
Networking Systems
FPGA, DSP, ASIC Power Supplies
Green Electronics/Appliances
Notebook Computers
“MPS” and “The Future of Analog IC Technology” are Trademarks of Monolithic
Power Systems, Inc.
TYPICAL APPLICATION
C5
10nF
Efficiency vs
INPUT
5V to 16V
Load Current
100
V
= 5V
IN
95
90
85
80
75
70
65
60
55
50
V
= 12V
IN
2
1
IN
BS
OUTPUT
3.3V
3A
7
8
3
5
EN
SS
SW
MP28315
FB
GND
COMP
4
6
D1
B130
(optional)
C3
3.9nF
C6
(optional)
0.1
1.0
LOAD CURRENT (A)
10
MP28315_EC01
MP28315_TAC_S01
MP28315 Rev. 1.2
12/12/2007
www.MonolithicPower.com
MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.
© 2007 MPS. All Rights Reserved.
1
TM
MP28315 – 3A, 16V, 340KHz SYNCHRONOUS RECTIFIED STEP-DOWN CONVERTER
PACKAGE REFERENCE
ABSOLUTE MAXIMUM RATINGS (1)
Supply Voltage VIN.......................–0.3V to +22V
Switch Voltage VSW................. –1V to VIN + 0.3V
Boost Voltage VBS..........VSW – 0.3V to VSW + 6V
All Other Pins.................................–0.3V to +6V
Junction Temperature...............................150°C
Lead Temperature....................................260°C
Storage Temperature .............–65°C to +150°C
Recommended Operating Conditions (2)
Input Voltage VIN................................. 5V to 16V
Output Voltage VOUT .................... 0.925V to 13V
Ambient Operating Temp ...................0°C to +70°C
TOP VIEW
BS
IN
1
2
3
4
8
7
6
5
SS
EN
SW
GND
COMP
FB
MP28315_PD01_SOIC8N
EXPOSED PAD
ON BACKSIDE
Thermal Resistance (3)
θJA
θJC
SOIC8N (Exposed Pad) .........50...... 10... °C/W
Part Number*
MP28315CN
Package
SOIC8N
Temperature
Notes:
1) Exceeding these ratings may damage the device.
2) The device is not guaranteed to function outside of its
operating conditions.
0° to +70°C
For Tape & Reel, add suffix –Z (eg. MP28315CN–Z)
For Lead Free, add suffix –LF (eg. MP28315CN–LF–Z)
*
3) Measured on approximately 1” square of 1 oz copper.
ELECTRICAL CHARACTERISTICS
VIN = 12V, TA = +25°C, unless otherwise noted.
Parameter
Symbol Condition
Min
Typ
0.3
Max
10
Units
μA
mA
V
Shutdown Supply Current
Supply Current
VEN = 0V
VEN = 2.0V, VFB = 1.0V
1.3
1.5
Feedback Voltage
VFB
0.900
0.925
1.1
0.951
Feedback Overvoltage Threshold
Error Amplifier Voltage Gain (4)
Error Amplifier Transconductance
High-Side Switch On-Resistance (4)
Low-Side Switch On-Resistance (4)
High-Side Switch Leakage Current
Upper Switch Current Limit
Oscillation Frequency
V
AEA
400
820
100
100
0
V/V
μA/V
mΩ
mΩ
μA
A
GEA
ΔIC = ±10μA
RDS(ON)1
RDS(ON)2
VEN = 0V, VSW = 0V
Minimum Duty Cycle
10
4.0
5.8
Fosc1
Fosc2
300
340
110
90
380
KHz
KHz
%
Short Circuit Oscillation Frequency
Maximum Duty Cycle
Minimum On Time (4)
VFB = 0V
DMAX VFB = 1.0V
TON
220
1.5
ns
EN Shutdown Threshold Voltage
VEN Rising
1.1
2.2
2.0
2.7
V
EN Shutdown Threshold Voltage
Hysterisis
220
mV
EN Lockout Threshold Voltage
EN Lockout Hysteresis
2.5
V
210
mV
MP28315 Rev. 1.2
12/12/2007
www.MonolithicPower.com
MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.
© 2007 MPS. All Rights Reserved.
2
TM
MP28315 – 3A, 16V, 340KHz SYNCHRONOUS RECTIFIED STEP-DOWN CONVERTER
ELECTRICAL CHARACTERISTICS (continued)
VIN = 12V, TA = +25°C, unless otherwise noted.
Parameter
Symbol Condition
Min
Typ
Max
Units
Input Under Voltage Lockout
Threshold
VIN Rising
3.80
4.05
4.40
V
Input Under Voltage Lockout
Threshold Hysteresis
210
mV
Soft-Start Current
Soft-Start Period
Thermal Shutdown (4)
VSS = 0V
6
μA
ms
°C
CSS = 0.1μF
15
130
160
Note:
4) Guaranteed by design, not tested.
PIN FUNCTIONS
Pin # Name Description
High-Side Gate Drive Boost Input. BS supplies the drive for the high-side N-Channel MOSFET
switch. Connect a 0.01μF or greater capacitor from SW to BS to power the high side switch.
1
2
BS
IN
Power Input. IN supplies the power to the IC, as well as the step-down converter switches.
Drive IN with a 5V to 16V power source. Bypass IN to GND with a suitably large capacitor to
eliminate noise on the input to the IC. See Input Capacitor.
Power Switching Output. SW is the switching node that supplies power to the output. Connect
the output LC filter from SW to the output load. Note that a capacitor is required from SW to
BS to power the high-side switch.
3
4
5
SW
GND Ground (Connect Exposed Pad to Pin 4).
Feedback Input. FB senses the output voltage to regulate that voltage. Drive FB with a
resistive voltage divider from the output voltage. The feedback threshold is 0.925V. See
FB
Setting the Output Voltage.
Compensation Node. COMP is used to compensate the regulation control loop. Connect a
series RC network from COMP to GND to compensate the regulation control loop. In some
cases, an additional capacitor from COMP to GND is required. See Compensation
Components.
6
COMP
Enable Input. EN is a digital input that turns the regulator on or off. Drive EN high to turn on
the regulator, drive it low to turn it off. Pull up with 100kΩ resistor for automatic startup.
7
8
EN
SS
Soft-Start Control Input. SS controls the soft-start period. Connect a capacitor from SS to GND
to set the soft-start period. A 0.1μF capacitor sets the soft-start period to 15ms. To disable the
soft-start feature, leave SS unconnected.
MP28315 Rev. 1.2
12/12/2007
www.MonolithicPower.com
MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.
© 2007 MPS. All Rights Reserved.
3
TM
MP28315 – 3A, 16V, 340KHz SYNCHRONOUS RECTIFIED STEP-DOWN CONVERTER
TYPICAL PERFORMANCE CHARACTERISTICS
C1 = 2 x 10µF, C2 = 2 x 22µF, L= 10µH, CSS= 0.1µF, unless otherwise noted.
Steady State Test
Waveforms
Steady State Test
Waveforms
Startup through
Enable Waveforms
V
= 12V, V
= 3.3V, I
OUT
= 0A
V
= 12V, V
= 3.3V, I
OUT
= 3A
V
= 12V, V
= 3.3V, No Load
IN
OUT
IN
OUT
IN
OUT
V
V
V
IN
EN
IN
20mV/div.
5V/div.
200mV/div.
V
V
OUT
OUT
20mV/div.
20MV/div.
V
OUT
2V/div.
V
V
V/div.
SW
SW
10V/div.
I
L
I
L
I
1A/div.
L
1A/div.
2A/div.
V
SW
10V/div.
2ms/div.
MP28315-TPC01
MP28315-TPC02
MP28315-TPC03
Startup Through
Shutdown Through
Enable Waveforms
Shutdown Through
Enable Waveforms
Enable Waveforms
V
I
= 12V, V
= 3.3V,
= 3A (Resistance Load)
V
I
= 12V, V = 3.3V,
OUT
IN
OUT
IN
V
= 12V, V = 3.3V, No Load
OUT
= 3A (Resistance Load)
IN
OUT
OUT
V
EN
5V/div.
V
V
EN
EN
5V/div.
5V/div.
V
OUT
2V/div.
V
V
OUT
OUT
2V/div.
2V/div.
I
L
I
L
2A/div.
1A/div.
I
L
2A/div.
V
V
SW
SW
10V/div.
10V/div.
V
SW
10V/div.
2ms/div.
2ms/div.
MP28315-TP04
MP28315-TPC05
MP28315-TPC06
Load Transient Test
Waveforms
Short Circuit Test
Waveforms
Short Circuit Recovery
Waveforms
V
I
= 12V, V = 3.3V,
OUT
IN
V
= 12V, V
= 3.3V
V
IN
= 12V, V = 3.3V
OUT
= 1A to 2A step
IN
OUT
OUT
V
OUT
200mV/div.
V
OUT
2V/div.
V
OUT
2V/div.
I
L
1A/div.
I
LOAD
I
L
1A/div.
I
2A/div.
L
2A/div.
MP28315-TPC07
MP28315-TPC08
MP28315-TPC09
MP28315 Rev. 1.2
12/12/2007
www.MonolithicPower.com
MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.
© 2007 MPS. All Rights Reserved.
4
TM
MP28315 – 3A, 16V, 340KHz SYNCHRONOUS RECTIFIED STEP-DOWN CONVERTER
OPERATION
The converter uses internal N-Channel
MOSFET switches to step-down the input
voltage to the regulated output voltage. Since
the high-side MOSFET requires a gate voltage
greater than the input voltage, a boost capacitor
connected between SW and BS is needed to
drive the high side gate. The boost capacitor is
charged from the internal 5V rail when SW is low.
FUNCTIONAL DESCRIPTION
The MP28315 is a synchronous rectified,
current-mode, step-down regulator. It regulates
input voltages from 5V to 16V down to an
output voltage as low as 0.925V, and supplies
up to 3A of load current.
The MP28315 uses current-mode control to
regulate the output voltage. The output voltage
is measured at FB through a resistive voltage
divider and amplified through the internal
transconductance error amplifier. The voltage at
the COMP pin is compared to the switch current
measured internally to control the output
voltage.
When the MP28315 FB pin exceeds 20% of the
nominal regulation voltage of 0.925V, the over
voltage comparator is tripped and the COMP
pin and the SS pin are discharged to GND,
forcing the high-side switch off.
+
CURRENT
2
IN
OVP
SENSE
AMPLIFIER
+
--
--
+
1.1V
0.3V
5V
RAMP
CLK
OSCILLATOR
110/340KHz
5
8
FB
SS
1
3
BS
--
S
Q
Q
--
+
--
+
+
SW
R
CURRENT
COMPARATOR
ERROR
AMPLIFIER
0.925V
6
7
COMP
EN
4
GND
--
EN OK
OVP
IN < 4.10V
1.2V
LOCKOUT
COMPARATOR
2.5V
1.5V
+
+
IN
7V
Zener
INTERNAL
REGULATORS
--
SHUTDOWN
COMPARATOR
MP28315_BD01
Figure 1—Functional Block Diagram
MP28315 Rev. 1.2
12/12/2007
www.MonolithicPower.com
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© 2007 MPS. All Rights Reserved.
5
TM
MP28315 – 3A, 16V, 340KHz SYNCHRONOUS RECTIFIED STEP-DOWN CONVERTER
APPLICATIONS INFORMATION
Where VOUT is the output voltage, VIN is the
input voltage, fS is the switching frequency, and
ΔIL is the peak-to-peak inductor ripple current.
COMPONENT SELECTION
Setting the Output Voltage
The output voltage is set using a resistive
voltage divider from the output voltage to FB pin.
The voltage divider divides the output voltage
down to the feedback voltage by the ratio:
Choose an inductor that will not saturate under
the maximum inductor peak current. The peak
inductor current can be calculated by:
R2
⎛
⎜
⎝
⎞
VOUT
VOUT
VIN
VFB = VOUT
⎜
⎟
⎟
⎠
ILP = ILOAD
+
× 1−
R1+ R2
2× fS ×L
Thus the output voltage is:
Where ILOAD is the load current.
R1+ R2
VOUT = 0.925 ×
The choice of which style inductor to use mainly
depends on the price vs. size requirements and
any EMI constraints.
R2
R2 can be as high as 100kΩ, but a typical value
is 10kΩ. Using the typical value for R2, R1 is
determined by:
Optional Schottky Diode
During the transition between high-side switch
and low-side switch, the body diode of the low-
side power MOSFET conducts the inductor
current. The forward voltage of this body diode
is high. An optional Schottky diode may be
paralleled between the SW pin and GND pin to
improve overall efficiency. Table 2 lists example
Schottky diodes and their Manufacturers.
R1 = 10.81× (VOUT − 0.925) (kꢀ)
For example, for a 3.3V output voltage, R2 is
10kꢀ, and R1 is 26.1kꢀ. Table 1 lists
recommended resistance values of R1 and R2
for standard output voltages.
Table 1—Recommended Resistance Values
Table 2—Diode Selection Guide
Voltage/Current
VOUT
1.8V
2.5V
3.3V
5V
R1
R2
9.53kꢀ
16.9kꢀ
26.1kꢀ
44.2kꢀ
121kꢀ
10kꢀ
10kꢀ
10kꢀ
10kꢀ
10kꢀ
Part Number
Vendor
Rating
30V, 1A
30V, 1A
B130
SK13
Diodes, Inc.
Diodes, Inc.
International
Rectifier
12V
MBRS130
30V, 1A
Inductor
Input Capacitor
The inductor is required to supply constant
current to the output load while being driven by
the switched input voltage. A larger value
inductor will result in less ripple current that will
in turn result in lower output ripple voltage.
However, the larger value inductor will have a
larger physical size, higher series resistance,
and/or lower saturation current. A good rule is
to allow the inductor peak-to-peak ripple current
to be approximately 30% of the maximum
switch current limit. Also, make sure that the
peak inductor current is below the maximum
switch current limit. The inductance value can
be calculated by:
The input current to the step-down converter is
discontinuous, therefore a capacitor is required
to supply the AC current to the step-down
converter while maintaining the DC input
voltage. Use low ESR capacitors for the best
performance. Ceramic capacitors are preferred,
but tantalum or low-ESR electrolytic capacitors
may also suffice. Choose X5R or X7R
dielectrics when using ceramic capacitors.
⎛
⎜
⎝
⎞
⎟
⎟
⎠
VOUT
VOUT
VIN
⎜
L =
× 1−
fS × ΔIL
MP28315 Rev. 1.2
12/12/2007
www.MonolithicPower.com
MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.
© 2007 MPS. All Rights Reserved.
6
TM
MP28315 – 3A, 16V, 340KHz SYNCHRONOUS RECTIFIED STEP-DOWN CONVERTER
Since the input capacitor (C1) absorbs the input
switching current it requires an adequate ripple
current rating. The RMS current in the input
capacitor can be estimated by:
In the case of tantalum or electrolytic capacitors,
the ESR dominates the impedance at the
switching frequency. For simplification, the
output ripple can be approximated to:
VOUT
VOUT
VIN
⎛
⎞
⎛
⎞
⎟
VOUT
VOUT
⎜
ΔVOUT
=
× ⎜1−
⎟ ×RESR
IC1 = ILOAD
×
× 1−
⎜
⎟
⎜
⎝
⎟
⎠
fS ×L
V
V
⎝
⎠
IN
IN
The characteristics of the output capacitor also
affect the stability of the regulation system. The
MP28315 can be optimized for a wide range of
capacitance and ESR values.
The worst-case condition occurs at VIN = 2VOUT
,
where IC1 = ILOAD/2. For simplification, choose
the input capacitor whose RMS current rating
greater than half of the maximum load current.
Compensation Components
The input capacitor can be electrolytic, tantalum
or ceramic. When using electrolytic or tantalum
capacitors, a small, high quality ceramic
capacitor, i.e. 0.1μF, should be placed as close
to the IC as possible. When using ceramic
capacitors, make sure that they have enough
capacitance to provide sufficient charge to
prevent excessive voltage ripple at input. The
input voltage ripple for low ESR capacitors can
be estimated by:
MP28315 employs current mode control for
easy compensation and fast transient response.
The system stability and transient response are
controlled through the COMP pin. COMP pin is
the output of the internal transconductance
error amplifier. A series capacitor-resistor
combination sets a pole-zero combination to
control the characteristics of the control system.
The DC gain of the voltage feedback loop is
given by:
⎛
⎜
⎝
⎞
⎟
⎟
⎠
ILOAD
VOUT
VIN
VOUT
⎜
ΔV
=
×
× 1−
IN
C1× fS
V
VFB
IN
AVDC = RLOAD × GCS × AEA
×
VOUT
Where C1 is the input capacitance value.
Where VFB is the feedback voltage, 0.925V;
AVEA is the error amplifier voltage gain; GCS is
the current sense transconductance and RLOAD
is the load resistor value.
Output Capacitor
The output capacitor (C2) is required to
maintain the DC output voltage. Ceramic,
tantalum, or low ESR electrolytic capacitors are
recommended. Low ESR capacitors are
preferred to keep the output voltage ripple low.
The output voltage ripple can be estimated by:
The system has two poles of importance. One
is due to the compensation capacitor (C3) and
the output resistor of the error amplifier, and the
other is due to the output capacitor and the load
resistor. These poles are located at:
⎛
⎜
⎝
⎞
⎟
⎟
⎠
⎛
⎜
⎝
⎞
⎟
⎟
⎠
VOUT
VOUT
VIN
1
⎜
⎜
ΔVOUT
=
× 1−
× RESR
+
fS × L
8 × fS × C2
GEA
fP1
=
Where C2 is the output capacitance value and
RESR is the equivalent series resistance (ESR)
value of the output capacitor.
2π× C3× AVEA
1
fP2
=
2π × C2× RLOAD
In the case of ceramic capacitors, the
impedance at the switching frequency is
dominated by the capacitance. The output
voltage ripple is mainly caused by the
capacitance. For simplification, the output
voltage ripple can be estimated by:
Where GEA is the error amplifier transconductance.
⎛
⎜
⎝
⎞
VOUT
VOUT
VIN
⎜
⎟
⎟
⎠
ΔVOUT
=
× 1−
2
8 × fS × L × C2
MP28315 Rev. 1.2
12/12/2007
www.MonolithicPower.com
MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.
© 2007 MPS. All Rights Reserved.
7
TM
MP28315 – 3A, 16V, 340KHz SYNCHRONOUS RECTIFIED STEP-DOWN CONVERTER
The system has one zero of importance, due to the
compensation capacitor (C3) and the compensation
resistor (R3). This zero is located at:
2. Choose the compensation capacitor (C3) to
achieve the desired phase margin. For
applications with typical inductor values, setting
the compensation zero, fZ1, below one-forth of
the crossover frequency provides sufficient
phase margin.
1
fZ1
=
2π × C3×R3
The system may have another zero of
importance, if the output capacitor has a large
capacitance and/or a high ESR value. The zero,
due to the ESR and capacitance of the output
capacitor, is located at:
Determine the C3 value by the following equation:
4
C3 >
2π × R3 × fC
Where R3 is the compensation resistor.
1
fESR
=
3. Determine if the second compensation
capacitor (C6) is required. It is required if the
ESR zero of the output capacitor is located at
less than half of the switching frequency, or the
following relationship is valid:
2π × C2× RESR
In this case, a third pole set by the
compensation capacitor (C6) and the
compensation resistor (R3) is used to
compensate the effect of the ESR zero on the
loop gain. This pole is located at:
fS
2
1
<
2π × C2× RESR
1
fP3
=
If this is the case, then add the second
compensation capacitor (C6) to set the pole fP3
at the location of the ESR zero. Determine the
C6 value by the equation:
2π× C6×R3
The goal of compensation design is to shape
the converter transfer function to get a desired
loop gain. The system crossover frequency
where the feedback loop has the unity gain is
important. Lower crossover frequencies result
in slower line and load transient responses,
while higher crossover frequencies could cause
system instability. A good rule of thumb is to set
the crossover frequency below one-tenth of the
switching frequency.
C2 × RESR
C6 =
R3
External Bootstrap Diode
It is recommended that an external bootstrap
diode be added when the system has a 5V
fixed input or the power supply generates a 5V
output. This helps improve the efficiency of the
regulator. The bootstrap diode can be a low
cost one such as IN4148 or BAT54.
To optimize the compensation components, the
following procedure can be used.
5V
1. Choose the compensation resistor (R3) to set
the desired crossover frequency.
BS
Determine the R3 value by the following
equation:
10nF
MP28315
SW
2π × C2 × fC VOUT 2π × C2 × 0.1× fS VOUT
R3 =
×
<
×
GEA × GCS
VFB
GEA × GCS
VFB
MP28315_F02
Where fC is the desired crossover frequency
which is typically below one tenth of the
switching frequency.
Figure 2—External Bootstrap Diode
This diode is also recommended for high duty
VOUT
cycle operation (when
>65%) and high
VIN
output voltage (VOUT>12V) applications.
MP28315 Rev. 1.2
12/12/2007
www.MonolithicPower.com
MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.
© 2007 MPS. All Rights Reserved.
8
TM
MP28315 – 3A, 16V, 340KHz SYNCHRONOUS RECTIFIED STEP-DOWN CONVERTER
TYPICAL APPLICATION CIRCUITS
C5
10nF
INPUT
5V to 16V
2
1
IN
BS
OUTPUT
2.5V
3A
3
5
7
EN
SW
MP28315
8
SS
FB
GND
COMP
6C3
4.7nF
4
D1
B130
(optional)
C6
(optional)
MP28315_F03
Figure 3—MP28315 with AVX 47μF, 6.3V Ceramic Output Capacitor
C5
10nF
INPUT
5V to 16V
2
1
IN
BS
OUTPUT
2.5V
3A
7
8
3
5
EN
SS
SW
MP28315
FB
GND
COMP
4
6
D1
B130
(optional)
C3
4.7nF
C6
200pF
MP28315_F04
Figure 4—MP28315 with Panasonic 47μF, 6.3V Solid Polymer Output Capacitor
MP28315 Rev. 1.2
12/12/2007
www.MonolithicPower.com
MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.
© 2007 MPS. All Rights Reserved.
9
TM
MP28315 – 3A, 16V, 340KHz SYNCHRONOUS RECTIFIED STEP-DOWN CONVERTER
B130
INPUT
6V
C5
10nF
2
1
IN
BS
OUTPUT
5V
3A
7
8
3
5
EN
SS
SW
MP28315
FB
GND
COMP
4
6
D1
B130
(optional)
C3
3.3nF
C6
100pF
MP28315_F05
Figure 5—MP28315 Application Circuit with VIN = 6V and VO = 5V
MP28315 Rev. 1.2
12/12/2007
www.MonolithicPower.com
MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.
© 2007 MPS. All Rights Reserved.
10
TM
MP28315 – 3A, 16V, 340KHz SYNCHRONOUS RECTIFIED STEP-DOWN CONVERTER
PACKAGE INFORMATION
SOIC8N (EXPOSED PAD)
0.229(5.820)
0.244(6.200)
PIN 1 IDENT.
NOTE 4
0.150(3.810)
0.157(4.000)
0.0075(0.191)
0.0098(0.249)
SEE DETAIL "A"
NOTE 2
0.011(0.280)
0.020(0.508)
x 45o
0.013(0.330)
0.020(0.508)
0.050(1.270)BSC
0o-8o
0.016(0.410)
0.050(1.270)
DETAIL "A"
NOTE 3
0.189(4.800)
0.197(5.000)
.050
.028
0.049(1.250)
0.060(1.524)
0.053(1.350)
0.068(1.730)
0.200 (5.07 mm)
SEATING PLANE
0.001(0.030)
0.004(0.101)
0.140 (3.55mm)
0.060
Land Pattern
NOTE:
1) Control dimension is in inches. Dimension in bracket is millimeters.
2) Exposed Pad Option (N-Package) ; 2.31mm -2.79mm x 2.79mm - 3.81mm.
Recommend Solder Board Area: 2.80mm x 3.82mm = 10.7mm2 (16.6 mil2)
3) The length of the package does not include mold flash. Mold flash shall not exceed 0.006in. (0.15mm) per side.
With the mold flash included, over-all length of the package is 0.2087in. (5.3mm) max.
4) The width of the package does not include mold flash. Mold flash shall not exceed 0.10in. (0.25mm) per side.
With the mold flash included, over-all width of the package is 0.177in. (4.5mm) max.
NOTICE: The information in this document is subject to change without notice. Please contact MPS for current specifications.
Users should warrant and guarantee that third party Intellectual Property rights are not infringed upon when integrating MPS
products into any application. MPS will not assume any legal responsibility for any said applications.
MP28315 Rev. 1.2
12/12/2007
www.MonolithicPower.com
MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.
© 2007 MPS. All Rights Reserved.
11
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