MP28317DS [MPS]
Switching Regulator, Current-mode, 2A, 340kHz Switching Freq-Max, PDSO8, MS-012AA, SOIC-8;
| 型号： | MP28317DS |
| 厂家： | 
MONOLITHIC POWER SYSTEMS |
| 描述： | Switching Regulator, Current-mode, 2A, 340kHz Switching Freq-Max, PDSO8, MS-012AA, SOIC-8 开关 光电二极管 输出元件 |
| 文件： | 总10页 (文件大小：325K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
MP28317
1A, 23V, 340KHz Synchronous Rectified
Step-Down Converter
The Future of Analog IC Technology
DESCRIPTION
FEATURES
The MP28317 is a monolithic synchronous buck
regulator. The device integrates 140mΩ
MOSFETS that provide 1A continuous load
current over a wide operating input voltage of
4.75V to 23V. Current mode control provides
fast transient response and cycle-by-cycle
current limit.
•
•
•
•
•
•
•
•
•
•
1A Output Current
Wide 4.75V to 23V Operating Input Range
Integrated 140mΩ Power MOSFET Switches
Output Adjustable from 0.923V to 20V
Up to 95% Efficiency
Programmable Soft-Start
Stable with Low ESR Ceramic Output Capacitors
Fixed 340KHz Frequency
An adjustable soft-start prevents inrush current
at turn-on. Shutdown mode drops the supply
current to 1μA.
Cycle-by-Cycle Over Current Protection
Input Under Voltage Lockout
This device, available in an 8-pin SOIC
package, provides a very compact system
solution with minimal reliance on external
components.
APPLICATIONS
•
•
•
•
•
Distributed Power Systems
Networking Systems
FPGA, DSP, ASIC Power Supplies
Green Electronics/ Appliances
Notebook Computers
“MPS” and “The Future of Analog IC Technology” are Trademarks of Monolithic
Power Systems, Inc.
TYPICAL APPLICATION
C5
10nF
Efficiency vs
INPUT
4.75V to 23V
Load Current
100
90
80
2
1
IN
BS
OUTPUT
3.3V
1A
V
= 5V
IN
3
5
7
8
EN
SS
SW
70
60
50
40
30
20
V
= 12V
IN
MP28317
FB
COMP
V
= 23V
IN
GND
1%
4
6
C3
3.3nF
0
0.25
0.5
0.75
1.0
LOAD CURRENT (A)
MP28317 Rev. 1.0
12/13/2007
www.MonolithicPower.com
MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.
© 2007 MPS. All Rights Reserved.
1
MP28317 – 1A, 23V, 340KHz SYNCHRONOUS RECTIFIED STEP-DOWN CONVERTER
PACKAGE REFERENCE
ABSOLUTE MAXIMUM RATINGS (1)
Supply Voltage VIN.......................–0.3V to +26V
Switch Voltage VSW.................. –1V to VIN +0.3V
Boost Voltage VBS..........VSW – 0.3V to VSW + 6V
All Other Pins.................................–0.3V to +6V
Junction Temperature...............................150°C
Lead Temperature....................................260°C
Storage Temperature .............–65°C to +150°C
Recommended Operating Conditions (2)
Input Voltage VIN............................ 4.75V to 23V
Output Voltage VOUT .................... 0.923V to 20V
Ambient Operating Temperature .... –40°C to +85°C
TOP VIEW
BS
IN
1
2
3
4
8
7
6
5
SS
EN
SW
GND
COMP
FB
Thermal Resistance (3)
θJA
θJC
SOIC8.....................................90...... 45... °C/W
Part Number*
Package
Temperature
Notes:
MP28317DS
SOIC8
–40° to +85°C
1) Exceeding these ratings may damage the device.
2) The device is not guaranteed to function outside of its
operating conditions.
For Tape & Reel, add suffix –Z (eg. MP28317DS–Z)
For RoHS Compliant Packaging, add suffix –LF
(eg. MP28317DS–LF–Z)
*
3) Measured on approximately 1” square of 1 oz copper.
ELECTRICAL CHARACTERISTICS
VIN = 12V, TA = +25°C, unless otherwise noted.
Parameter
Symbol Condition
Min
Typ
1
Max
3.0
Units
μA
mA
V
Shutdown Supply Current
Supply Current
VEN = 0V
VEN = 2.0V, VFB = 1.0V
4.75V ≤ VIN ≤ 23V
1.3
1.5
Feedback Voltage
VFB
0.900
0.923
1.1
0.946
Feedback Overvoltage Threshold
Error Amplifier Voltage Gain (4)
Error Amplifier Transconductance
High-Side Switch On Resistance (4)
Low-Side Switch On Resistance (4)
High-Side Switch Leakage Current
Upper Switch Current Limit
Lower Switch Current Limit
V
AEA
400
800
140
140
V/V
μA/V
mΩ
mΩ
μA
A
GEA
ΔIC = ±10μA
RDS(ON)1
RDS(ON)2
VEN = 0V, VSW = 0V
Minimum Duty Cycle
From Drain to Source
10
1.4
2
0.8
A
COMP to Current Sense
Transconductance
GCS
2.4
A/V
Oscillation Frequency
Fosc1
Fosc2
340
100
90
KHz
KHz
%
Short Circuit Oscillation Frequency
VFB = 0V
Maximum Duty Cycle
Minimum On Time (4)
DMAX VFB = 0.8V
220
1.5
nS
V
EN Shutdown Threshold
EN Shutdown Threshold Hysteresis
EN Lockout Threshold Voltage
EN Lockout Hysteresis
VEN Rising
1.1
2.2
2.0
2.7
210
2.5
mV
V
210
mV
MP28317 Rev. 1.0
12/13/2007
www.MonolithicPower.com
MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.
© 2007 MPS. All Rights Reserved.
2
MP28317 – 1A, 23V, 340KHz SYNCHRONOUS RECTIFIED STEP-DOWN CONVERTER
ELECTRICAL CHARACTERISTICS (continued)
VIN = 12V, TA = +25°C, unless otherwise noted.
Parameter
Symbol Condition
Min
Typ
Max
Units
Input Under Voltage Lockout
Threshold
VIN Rising
3.80
4.10
4.40
V
Input Under Voltage Lockout
Threshold Hysteresis
210
mV
Soft-Start Current
Soft-Start Period
VSS = 0V
CSS = 0.1μF
6
15
160
μA
ms
°C
Thermal Shutdown (4)
Note:
4) Guaranteed by design, not tested.
PIN FUNCTIONS
Pin # Name Description
High-Side Gate Drive Boost Input. BS supplies the drive for the high-side N-Channel MOSFET
switch. Connect a 0.01μF or greater capacitor from SW to BS to power the high side switch.
1
2
BS
IN
Power Input. IN supplies the power to the IC, as well as the step-down converter switches.
Drive IN with a 4.75V to 23V power source. Bypass IN to GND with a suitably large capacitor
to eliminate noise on the input to the IC. See Input Capacitor.
Power Switching Output. SW is the switching node that supplies power to the output. Connect
the output LC filter from SW to the output load. Note that a capacitor is required from SW to
BS to power the high-side switch.
3
4
5
SW
GND Ground.
Feedback Input. FB senses the output voltage to regulate that voltage. Drive FB with a
resistive voltage divider from the output voltage. The feedback threshold is 0.923V. See
FB
Setting the Output Voltage.
Compensation Node. COMP is used to compensate the regulation control loop. Connect a
series RC network from COMP to GND to compensate the regulation control loop. In some
cases, an additional capacitor from COMP to GND is required. See Compensation
Components.
6
COMP
Enable Input. EN is a digital input that turns the regulator on or off. Drive EN high to turn on
the regulator, drive it low to turn it off. Pull up with 100kΩ resistor for automatic startup.
7
8
EN
SS
Soft-Start Control Input. SS controls the soft-start period. Connect a capacitor from SS to GND
to set the soft-start period. A 0.1μF capacitor sets the soft-start period to 15ms. To disable the
soft-start feature, leave SS unconnected.
MP28317 Rev. 1.0
12/13/2007
www.MonolithicPower.com
MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.
© 2007 MPS. All Rights Reserved.
3
MP28317 – 1A, 23V, 340KHz SYNCHRONOUS RECTIFIED STEP-DOWN CONVERTER
TYPICAL PERFORMANCE CHARACTERISTICS
VIN = 12V, VOUT = 3.3V, L = 10µH, C1 = 10µF, C2 = 22µF, TA = +25°C, unless otherwise noted.
No Load Operation
Full Load Operation
No Load
1A Load
V
V
IN, AC
20mV/div.
IN, AC
V
200mV/div.
EN
5V/div.
V
V
O, AC
O, AC
V
20mV/div.
20mV/div.
OUT
2V/div.
I
I
L
L
I
1A/div.
1A/div.
L
1A/div.
V
V
SW
SW
V
10V/div.
10V/div.
SW
10V/div.
2ms/div.
Shutdown through Enable
Shutdown through Enable
V
= 12V, V
= 3.3V,
IN
OUT
= 1A (Resistance Load)
V
= 12V, V
= 3.3V, No Load
IN
OUT
I
OUT
V
EN
V
V
EN
EN
5V/div.
5V/div.
5V/div.
V
OUT
2V/div.
V
V
OUT
OUT
2V/div.
2V/div.
I
I
L
L
I
L
1A/div.
1A/div.
1A/div.
V
V
V
SW
SW
SW
10V/div.
10V/div.
10V/div.
2ms/div.
2ms/div.
2ms/div.
Load Transient Test
Short Circuit Recovery
Short Circuit Entry
V
= 12V, V
= 3.3V,
IN
OUT
= 0.2A to 1A steps
I
OUT
V
OUT
V
OUT
V
200mV/div.
OUT
2V/div.
2V/div.
I
L
1A/div.
i
LOAD
I
L
I
1A/div.
L
1A/div.
1A/div.
MP28317 Rev. 1.0
12/13/2007
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4
MP28317 – 1A, 23V, 340KHz SYNCHRONOUS RECTIFIED STEP-DOWN CONVERTER
OPERATION
The converter uses internal N-Channel
MOSFET switches to step-down the input
voltage to the regulated output voltage. Since
the high side MOSFET requires a gate voltage
greater than the input voltage, a boost capacitor
connected between SW and BS is needed to
drive the high side gate. The boost capacitor is
charged from the internal 5V rail when SW is low.
FUNCTIONAL DESCRIPTION
The MP28317 is a synchronous rectified,
current-mode, step-down regulator. It regulates
input voltages from 4.75V to 23V down to an
output voltage as low as 0.923V, and supplies
up to 1A of load current.
The MP28317 uses current-mode control to
regulate the output voltage. The output voltage
is measured at FB through a resistive voltage
divider and amplified through the internal
transconductance error amplifier. The voltage at
the COMP pin is compared to the switch current
measured internally to control the output
voltage.
When the MP28317 FB pin exceeds 20% of the
nominal regulation voltage of 0.923V, the over
voltage comparator is tripped and the COMP
pin and the SS pin are discharged to GND,
forcing the high-side switch off.
+
CURRENT
2
IN
OVP
SENSE
AMPLIFIER
+
--
--
+
1.1V
0.3V
5V
RAMP
CLK
OSCILLATOR
100/340KHz
5
FB
1
3
BS
--
S
Q
Q
--
+
--
+
+
SW
R
CURRENT
COMPARATOR
8
6
SS
ERROR
AMPLIFIER
0.923V
COMP
4
GND
OVP
1.2V
+
--
2.5V
EN
IN
IN < 4.10V
EN OK
LOCKOUT
COMPARATOR
7
+
--
EN
INTERNAL
REGULATORS
5V
SHUTDOWN
COMPARATOR
1.5V
Figure 1—Functional Block Diagram
MP28317 Rev. 1.0
12/13/2007
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5
MP28317 – 1A, 23V, 340KHz SYNCHRONOUS RECTIFIED STEP-DOWN CONVERTER
APPLICATIONS INFORMATION
the maximum switch current limit. The inductance
value can be calculated by:
COMPONENT SELECTION
Setting the Output Voltage
The output voltage is set using a resistive
voltage divider from the output voltage to FB
pin. The voltage divider divides the output
voltage down to the feedback voltage by the
ratio:
⎛
⎜
⎝
⎞
⎟
⎟
⎠
VOUT
VOUT
VIN
⎜
L =
× 1−
fS × ΔL
Where VIN is the input voltage, fS is the switching
frequency, and ΔIL is the peak-to-peak inductor
ripple current.
R2
VFB = VOUT
R1+ R2
Choose an inductor that will not saturate under
the maximum inductor peak current. The peak
inductor current can be calculated by:
Thus the output voltage is:
R1+ R2
VOUT = 0.923 ×
⎛
⎞
⎟
⎟
⎠
VOUT
VOUT
VIN
R2
⎜
ILP = ILOAD
+
× 1−
⎜
⎝
2× fS ×L
Where VOUT is the output voltage and VFB is
the feedback voltage.
Where ILOAD is the load current.
R2 can be as high as 100kΩ, but a typical
value is 10kΩ. Using the typical value for R2,
R1 is determined by:
The choice of which style inductor to use mainly
depends on the price vs. size requirements and
any EMI requirements.
R1 = 10.87 × (VOUT − 0.923)
Optional Schottky Diode
During the transition between high-side switch
and low-side switch, the body diode of the low-
side power MOSFET conducts the inductor
current. The forward voltage of this body diode is
high. An optional Schottky diode may be
paralleled between the SW pin and GND pin to
improve overall efficiency. Table 2 lists example
Schottky diodes and their Manufacturers.
For example, for a 3.3V output voltage, R2 is
10kΩ, and R1 is 26.1kΩ.
Table 1 lists recommended resistor values.
Table1—Recommended Resistors
VOUT
1.8V
2.5V
3.3V
5V
R1
R2
9.53kΩ
16.9kΩ
26.1kΩ
44.2Ω
121kΩ
10kΩ
10kΩ
10kΩ
10kΩ
10kΩ
Table 2—Diode Selection Guide
Voltage/Current
Part Number
B130
Rating
30V, 1A
30V, 1A
30V, 1A
Vendor
12V
Diodes, Inc.
Diodes, Inc.
SK13
Inductor
MBRS130
International
Rectifier
The inductor is required to supply constant
current to the output load while being driven
by the switched input voltage. A larger value
inductor will result in less ripple current that
will result in lower output ripple voltage.
However, the larger value inductor will have a
larger physical size, higher series resistance,
and/or lower saturation current. A good rule
for determining the inductance to use is to
allow the peak-to-peak ripple current in the
inductor to be approximately 30% of the
maximum switch current limit. Also, make
sure that the peak inductor current is below
Input Capacitor
The input current to the step-down converter is
discontinuous, therefore a capacitor is required to
supply the AC current to the step-down converter
while maintaining the DC input voltage. Use low
ESR capacitors for the best performance.
Ceramic capacitors are preferred, but tantalum or
low-ESR electrolytic capacitors may also suffice.
Choose X5R or X7R dielectrics when using
ceramic capacitors.
MP28317 Rev. 1.0
12/13/2007
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6
MP28317 – 1A, 23V, 340KHz SYNCHRONOUS RECTIFIED STEP-DOWN CONVERTER
Since the input capacitor (C1) absorbs the input
In the case of tantalum or electrolytic capacitors,
the ESR dominates the impedance at the
switching frequency. For simplification, the
output ripple can be approximated to:
switching current it requires an adequate ripple
current rating. The RMS current in the input
capacitor can be estimated by:
VOUT
VOUT
VIN
⎛
⎞
⎛
⎞
⎟
VOUT
VOUT
⎜
ΔVOUT
=
× ⎜1−
⎟ ×RESR
IC1 = ILOAD
×
× 1−
⎜
⎟
⎜
⎝
⎟
⎠
fS ×L
V
V
⎝
⎠
IN
IN
The characteristics of the output capacitor also
affect the stability of the regulation system. The
MP28317 can be optimized for a wide range of
capacitance and ESR values.
The worst-case condition occurs at VIN = 2VOUT
,
where IC1 = ILOAD/2. For simplification, choose
the input capacitor whose RMS current rating
greater than half of the maximum load current.
Compensation Components
The input capacitor can be electrolytic, tantalum
or ceramic. When using electrolytic or tantalum
capacitors, a small, high quality ceramic
capacitor, i.e. 0.1μF, should be placed as close
to the IC as possible. When using ceramic
capacitors, make sure that they have enough
capacitance to provide sufficient charge to
prevent excessive voltage ripple at input. The
input voltage ripple caused by capacitance can
be estimated by:
MP28317 employs current mode control for
easy compensation and fast transient response.
The system stability and transient response are
controlled through the COMP pin. COMP pin is
the output of the internal transconductance
error amplifier. A series capacitor-resistor
combination sets a pole-zero combination to
control the characteristics of the control system.
The DC gain of the voltage feedback loop is
given by:
⎛
⎜
⎝
⎞
⎟
⎟
⎠
ILOAD
VOUT
VIN
VOUT
⎜
ΔV
=
×
× 1−
IN
fS × C1
V
VFB
IN
AVDC = RLOAD × GCS × AVEA
×
VOUT
Output Capacitor
The output capacitor is required to maintain the
DC output voltage. Ceramic, tantalum, or low
ESR electrolytic capacitors are recommended.
Low ESR capacitors are preferred to keep the
output voltage ripple low. The output voltage
ripple can be estimated by:
Where VFB is the feedback voltage, 0.923V;
AVEA is the error amplifier voltage gain; GCS is
the current sense transconductance and RLOAD
is the load resistor value.
The system has 2 poles of importance. One is
due to the compensation capacitor (C3) and the
output resistor of error amplifier, and the other
is due to the output capacitor and the load
resistor. These poles are located at:
⎛
⎜
⎝
⎞
⎟
⎟
⎛
⎞
⎟
⎟
⎠
VOUT
VOUT
VIN
1
⎜
⎜
ΔVOUT
=
× 1−
× RESR
+
⎜
⎝
fS × L
8 × fS × C2
⎠
Where C2 is the output capacitance value and
RESR is the equivalent series resistance (ESR)
value of the output capacitor.
GEA
fP1
=
2π× C3× AVEA
1
In the case of ceramic capacitors, the
impedance at the switching frequency is
dominated by the capacitance. The output
voltage ripple is mainly caused by the
capacitance. For simplification, the output
voltage ripple can be estimated by:
fP2
=
2π × C2× RLOAD
Where GEA is the error amplifier transconductance.
⎛
⎜
⎝
⎞
VOUT
VOUT
VIN
⎜
⎟
⎟
⎠
ΔVOUT
=
× 1−
2
8 × fS × L × C2
MP28317 Rev. 1.0
12/13/2007
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7
MP28317 – 1A, 23V, 340KHz SYNCHRONOUS RECTIFIED STEP-DOWN CONVERTER
The system has one zero of importance, due to the
compensation capacitor (C3) and the compensation
resistor (R3). This zero is located at:
2. Choose the compensation capacitor (C3) to
achieve the desired phase margin. For
applications with typical inductor values, setting
the compensation zero, fZ1, below one-forth of
the crossover frequency provides sufficient
phase margin.
1
fZ1
=
2π × C3×R3
The system may have another zero of
importance, if the output capacitor has a large
capacitance and/or a high ESR value. The zero,
due to the ESR and capacitance of the output
capacitor, is located at:
Determine the C3 value by the following equation:
4
C3 >
2π × R3 × fC
Where R3 is the compensation resistor.
1
fESR
=
3. Determine if the second compensation
capacitor (C6) is required. It is required if the
ESR zero of the output capacitor is located at
less than half of the switching frequency, or the
following relationship is valid:
2π × C2× RESR
In this case (as shown in Figure 2), a third pole
set by the compensation capacitor (C6) and the
compensation resistor (R3) is used to
compensate the effect of the ESR zero on the
loop gain. This pole is located at:
fS
2
1
<
2π × C2× RESR
1
fP3
=
If this is the case, then add the second
compensation capacitor (C6) to set the pole fP3
at the location of the ESR zero. Determine the
C6 value by the equation:
2π× C6×R3
The goal of compensation design is to shape
the converter transfer function to get a desired
loop gain. The system crossover frequency
where the feedback loop has the unity gain is
important. Lower crossover frequencies result
in slower line and load transient responses,
while higher crossover frequencies could cause
system unstable. A good rule of thumb is to set
the crossover frequency below one-tenth of the
switching frequency. Determine the R3 value by
the following equation:
C2 × RESR
C6 =
R3
External Bootstrap Diode
It is recommended that an external bootstrap
diode be added when the system has a 5V
fixed input or the power supply generates a 5V
output. This helps improve the efficiency of the
regulator. The bootstrap diode can be a low
cost one such as IN4148 or BAT54.
2π × C2 × fC VOUT 2π × C2 × 0.1× fS VOUT
R3 =
×
<
×
5V
GEA × GCS
VFB
GEA × GCS
VFB
Where fC is the desired crossover frequency
which is typically below one tenth of the
switching frequency.
BS
10nF
MP28317
To optimize the compensation components, the
following procedure can be used.
SW
1. Choose the compensation resistor (R3) to set
the desired crossover frequency.
Figure 2—External Bootstrap Diode
This diode is also recommended for high duty
VOUT
cycle operation (when
>65%) and high
VIN
output voltage (VOUT>12V) applications.
MP28317 Rev. 1.0
12/13/2007
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8
MP28317 – 1A, 23V, 340KHz SYNCHRONOUS RECTIFIED STEP-DOWN CONVERTER
TYPICAL APPLICATION CIRCUIT
C5
10nF
INPUT
4.75V to 23V
2
1
IN
BS
OUTPUT
3.3V
1A
3
5
7
8
EN
SS
SW
MP28317
FB
COMP
GND
1%
4
6
D1
C3
3.3nF
B130
C6
(optional)
(optional)
Figure 3—MP28317 with 3.3V Output, 22uF/6.3V Ceramic Output Capacitor
MP28317 Rev. 1.0
12/13/2007
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9
MP28317 – 1A, 23V, 340KHz SYNCHRONOUS RECTIFIED STEP-DOWN CONVERTER
PACKAGE INFORMATION
SOIC8
0.189(4.80)
0.197(5.00)
0.050(1.27)
0.024(0.61)
0.063(1.60)
8
5
0.150(3.80)
0.157(4.00)
0.228(5.80)
0.244(6.20)
0.213(5.40)
PIN 1 ID
1
4
TOP VIEW
RECOMMENDED LAND PATTERN
0.053(1.35)
0.069(1.75)
SEATING PLANE
0.004(0.10)
0.010(0.25)
0.0075(0.19)
0.0098(0.25)
0.013(0.33)
0.020(0.51)
SEE DETAIL "A"
0.050(1.27)
BSC
SIDE VIEW
FRONT VIEW
0.010(0.25)
0.020(0.50)
x 45o
NOTE:
1) CONTROL DIMENSION IS IN INCHES. DIMENSION IN
BRACKET IS IN MILLIMETERS.
GAUGE PLANE
0.010(0.25) BSC
2) PACKAGE LENGTH DOES NOT INCLUDE MOLD FLASH,
PROTRUSIONS OR GATE BURRS.
3) PACKAGE WIDTH DOES NOT INCLUDE INTERLEAD FLASH
OR PROTRUSIONS.
4) LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING)
SHALL BE 0.004" INCHES MAX.
0.016(0.41)
0.050(1.27)
0o-8o
5) DRAWING CONFORMS TO JEDEC MS-012, VARIATION AA.
6) DRAWING IS NOT TO SCALE.
DETAIL "A"
NOTICE: The information in this document is subject to change without notice. Users should warrant and guarantee that third
party Intellectual Property rights are not infringed upon when integrating MPS products into any application. MPS will not
assume any legal responsibility for any said applications.
MP28317 Rev. 1.0
12/13/2007
www.MonolithicPower.com
MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.
© 2007 MPS. All Rights Reserved.
10
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