MP28163GQ [MPS]
High Efficiency Single Inductor Buck-Boost Converter with 2.9A Switches;
| 型号： | MP28163GQ |
| 厂家： | 
MONOLITHIC POWER SYSTEMS |
| 描述： | High Efficiency Single Inductor Buck-Boost Converter with 2.9A Switches |
| 文件： | 总18页 (文件大小：1031K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
MP28163
High Efficiency
Single Inductor Buck-Boost Converter
with 2.9A Switches
The Future of Analog IC Technology
DESCRIPTION
FEATURES
•
•
•
•
•
High efficiency up to 95%.
Load disconnect during shutdown
Input voltage range: 2V to 5.5V
Adjustable output voltage from 1.5V to 5V
3.3V/1.3A load capability from 2.7V-to-5.5V
VIN
The MP28163 is a highly efficient, low
quiescent current Buck-Boost converter, which
operates from input voltage above, below and
equal to the output voltage. The device
provides power solution for products powered
by a one-cell Lithium-Ion or multi-cell alkaline
battery applications where the output voltage is
within battery voltage range.
•
•
•
•
1.1MHz switching frequency
Pulse skipping mode at light load
Typical 70μA Quiescent current
Internal loop compensation for fast
response
The MP28163 uses a current mode, fixed
frequency PWM control for optimal stability and
transient response. The fixed 1.1MHz switching
frequency and integrated low RDS(ON) N-channel
and P-channel MOSFETs minimize the solution
footprint while maintaining high efficiency.
•
•
•
Internal soft start
OTP, hiccup SCP
Available in small 3x3mm QFN10 package
APPLICATIONS
To ensure the longest battery life MP28163 has
an optional pulse skipping mode that reduces
switching frequency under light load conditions.
For other low noise applications where variable
frequency power save mode may cause
interference, the logic control input MODE pin
forces fixed frequency PWM operation under all
load conditions.
•
•
•
•
•
Battery-powered products
Portable instruments
Tablet PCs
POS systems
GSM/GPRS
All MPS parts are lead-free and adhere to the RoHS directive. For MPS green
status, please visit MPS website under Products, Quality Assurance page.
“MPS” and “The Future of Analog IC Technology” are registered trademarks of
Monolithic Power Systems, Inc.
The MP28163 operates with input voltage from
2V to 5.5V to provide adjustable output voltage
(1.5V to 5V). With an input from 2.7V to 5.5V, it
can supply a maximum 1.3A current to load at
3.3V output voltage. The MP28163 is available
in small QFN10-3x3mm package.
TYPICAL APPLICATION
MP28163 Rev. 1.0
1/26/2014
www.MonolithicPower.com
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© 2014 MPS. All Rights Reserved.
1
MP28163 –HIGH EFFICIENCY SINGLE INDUCTOR BUCK-BOOST CONVERTER WITH 2.9A SWITCHES
ORDERING INFORMATION
Part Number*
Package
Top Marking
MP28163GQ*
QFN10 (3X3)
AJL
* For Tape & Reel, add suffix –Z (e.g. MP28163GQ–Z);
PACKAGE REFERENCE
TOP VIEW
VOUT
SW2
PGND
SW1
VIN
1
FB
10
9
AGND
VCC
2
3
EP
8
MODE/
SYNC
4
5
7
6
EN
ABSOLUTE MAXIMUM RATINGS (1)
IN to GND .....................................–0.3V to 6.5V
SW1/2 to GND......–0.3V(-2V for <10ns) to 6.5V
All Other Pins...............................–0.3V to 6.5 V
Junction Temperature...............................150°C
Lead Temperature ....................................260°C
Continuous Power Dissipation (TA = +25°C)
QFN10 3X3mm.......................................... 2.5W
Storage Temperature............... -65°C to +150°C
Recommended Operating Conditions (3)
Supply Voltage VIN .............................2V to 5.5V
Output Voltage VOUT...........................1.5V to 5V
Operating Junct. Temp. (TJ).... –40°C to +125°C
Thermal Resistance (4)
3X3 QFN10.............................50...... 12... °C/W
θJA
θJC
Notes:
1) Exceeding these ratings may damage the device
2) The maximum allowable power dissipation is a function of the
maximum junction temperature TJ (MAX), the junction-to-
ambient thermal resistance θJA, and the ambient temperature
TA. The maximum allowable continuous power dissipation at
any ambient temperature is calculated by PD (MAX) = (TJ
(MAX)-TA)/θJA. Exceeding the maximum allowable power
dissipation will cause excessive die temperature, and the
regulator will go into thermal shutdown. Internal thermal
shutdown circuitry protects the device from permanent
damage.
(2)
3) The device is not guaranteed to function outside of its
operating conditions.
4) Measured on JESD51-7, 4-layer PCB.
MP28163 Rev. 1.0
1/26/2014
www.MonolithicPower.com
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© 2014 MPS. All Rights Reserved.
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MP28163 –HIGH EFFICIENCY SINGLE INDUCTOR BUCK-BOOST CONVERTER WITH 2.9A SWITCHES
ELECTRICAL CHARACTERISTICS
VIN = VCC=VEN=3.3V, TJ = 25°C, unless otherwise noted.
Parameter
Symbol Condition
Min
Typ
Max
Units
VCC rising
VUVLO
1.8
1.9
V
Under voltage lockout threshold
VCC falling
1.7
V
Feedback voltage
VFB
486
900
496
506
mV
Oscillator frequency
1100
1300
kHz
kHz
FREQ
Frequency
synchronization
range
for
1000
2.25
2000
Primary current limit
2.9
1.8
85
A
A
Isw
Secondary current limit
NMOS switch on resistance
PMOS switch on resistance
Quiescent current
RDS(ON)-N
mΩ
mΩ
μA
μA
V
RDS(ON)-P
100
70
IQ
IS
VFB=0.65V
VEN=0V
85
1
Shutdown current
MODE input low voltage
MODE input high voltage
EN input low voltage
EN input high voltage
0.4
1.2
1.2
V
0.4
V
V
VEN=3.3V
VEN=0V
3.1
0
μA
μA
℃
℃
EN input current
IEN
Thermal shutdown(5)
Thermal shutdown hysteresis(5)
TSHDN
THYS
160
20
Notes:
5) Guaranteed by engineering sample Characterization, not tested in production.
MP28163 Rev. 1.0
1/26/2014
www.MonolithicPower.com
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MP28163 –HIGH EFFICIENCY SINGLE INDUCTOR BUCK-BOOST CONVERTER WITH 2.9A SWITCHES
TYPICAL CHARACTERISTICS
VIN = 3.3V, VOUT = 3.3V, L = 3.3µH, COUT=2x22uF, TA = +25ºC, unless otherwise noted.
MP28163 Rev. 1.0
1/26/2014
www.MonolithicPower.com
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MP28163 –HIGH EFFICIENCY SINGLE INDUCTOR BUCK-BOOST CONVERTER WITH 2.9A SWITCHES
TYPICAL PERFORMANCE CHARACTERISTICS
VIN = 3.3V, VOUT = 3.3V, L = 3.3µH, COUT=2x22uF, TA = +25ºC, unless otherwise noted.
MP28163 Rev. 1.0
1/26/2014
www.MonolithicPower.com
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© 2014 MPS. All Rights Reserved.
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MP28163 –HIGH EFFICIENCY SINGLE INDUCTOR BUCK-BOOST CONVERTER WITH 2.9A SWITCHES
TYPICAL PERFORMANCE CHARACTERISTICS (continued)
VIN = 3.3V, VOUT = 3.3V, L = 3.3µH, COUT=2x22uF, TA = +25ºC, unless otherwise noted.
Notes:
6) Tested with 2.25A inductor peak current at 3.3V input point. Under other VIN conditions, it takes the same current limit variation trend with
VIN into consideration as “Current Limit vs. Input Voltage” curve shows". Some margin is recommended for max load design。
MP28163 Rev. 1.0
1/26/2014
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© 2014 MPS. All Rights Reserved.
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MP28163 –HIGH EFFICIENCY SINGLE INDUCTOR BUCK-BOOST CONVERTER WITH 2.9A SWITCHES
TYPICAL PERFORMANCE CHARACTERISTICS (continued)
VIN = 3.3V, VOUT = 3.3V, L = 3.3µH, COUT=2x22uF, TA = +25ºC, unless otherwise noted.
MP28163 Rev. 1.0
1/26/2014
www.MonolithicPower.com
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© 2014 MPS. All Rights Reserved.
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MP28163 –HIGH EFFICIENCY SINGLE INDUCTOR BUCK-BOOST CONVERTER WITH 2.9A SWITCHES
TYPICAL PERFORMANCE CHARACTERISTICS (continued)
VIN = 3.3V, VOUT = 3.3V, L = 3.3µH, COUT=2x22uF, TA = +25ºC, unless otherwise noted.
MP28163 Rev. 1.0
1/26/2014
www.MonolithicPower.com
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MP28163 –HIGH EFFICIENCY SINGLE INDUCTOR BUCK-BOOST CONVERTER WITH 2.9A SWITCHES
TYPICAL PERFORMANCE CHARACTERISTICS (continued)
VIN = 3.3V, VOUT = 3.3V, L = 3.3µH, COUT=2x22uF, TA = +25ºC, unless otherwise noted.
MP28163 Rev. 1.0
1/26/2014
www.MonolithicPower.com
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MP28163 –HIGH EFFICIENCY SINGLE INDUCTOR BUCK-BOOST CONVERTER WITH 2.9A SWITCHES
TYPICAL PERFORMANCE CHARACTERISTICS (continued)
VIN = 3.3V, VOUT = 3.3V, L = 3.3µH, COUT=2x22uF, TA = +25ºC, unless otherwise noted.
MP28163 Rev. 1.0
1/26/2014
www.MonolithicPower.com
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MP28163 –HIGH EFFICIENCY SINGLE INDUCTOR BUCK-BOOST CONVERTER WITH 2.9A SWITCHES
PIN FUNCTIONS
Pin #
Name Description
1
VOUT Buck-Boost converter output.
Switch pin-Internal switches are connected to this pin. Connect inductor between SW1 and
SW2.
2
3
4
SW2
PGND Power ground.
Switch pin-Internal switches are connected to this pin. Connect inductor between SW1 and
SW2.
SW1
5
6
VIN
EN
Supply voltage for power stage.
ON/OFF control, it’s not recommended to leave this pin float.
Operation mode selection. If MODE pin is low, the MP28163 automatically switches
between PSM and fixed frequency PWM according to the load level. If MODE pin is pulled
high, the MP28163 works always in PWM mode.
External clock can be applied to MODE pin for changing switching frequency.
This pin is sensitive to noise, so it should be strongly pulled up above 1.2V or pulled down
below 0.4V. Must NOT leave it float.
MODE/
SYNC
7
8
9
VCC
Supply voltage for control stage.
AGND Signal ground, should be connected to PGND externally.
Feedback to set output voltage. Keeps this pin and associated trace far from noise source
like SW.
10
-
FB
EP
Thermal pad, which is recommended to connected to PGND.
MP28163 Rev. 1.0
1/26/2014
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MP28163 –HIGH EFFICIENCY SINGLE INDUCTOR BUCK-BOOST CONVERTER WITH 2.9A SWITCHES
L
SW1
SWA
SW2
SWD
OUTPUT
INPUT
Cin
VOUT
VIN
Current
sense
SWC
Cout
SWB
Gate
PGND
drivers
Oscillator
Reverse
Comparator
Buck
Comparator
FB
Vc-Buck
EA
Level
shift
Buck Boost
-
Control logic
VCC
Voltage
Reference
MODE
/SYNC
PSM
Control
EN
Vc- Boost
Boost
Slope
Generator
Comparator
Current
sense
AGND
SS Cap
Figure 1— Function Block Diagram
MP28163 Rev. 1.0
1/26/2014
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MP28163 –HIGH EFFICIENCY SINGLE INDUCTOR BUCK-BOOST CONVERTER WITH 2.9A SWITCHES
OPERATION
The MP28163 is a high efficiency, dual mode
buck-boost converter that provides output voltage
above, equal to or below the input voltage. When
the MODE pin is held high, the MP28163
operates in constant-frequency PWM mode with
peak current mode control. As shown in Figure 1,
the output voltage is sensed via the FB pin
through an external resistor-divider from the
output to ground. The voltage difference between
FB pin and the internal reference is amplified by
Buck-Boost Region (VIN ≈VOUT
)
When Vin is close to Vout, due to duty cycle limit
of SWA the converter isn’t able to provide wanted
energy to load. In this case SWA will be turned
on over all the period, that is, there is no BD
operation(SWB and SWD being turned on
simultaneously). Now a new period begins. Since
there is no BD in last period, an offset voltage is
added to the ramp signal to make the ramp
signal easily hit VC-Buck. At the same time due to
loop regulation VC-Boost (as well as VC-Buck) rises
to some level, so that the ramp signal can
intersect it to produce the PWM driving signal for
Boost operation. After SWC is turned off the
ramp signal continues rising (the actual inductor
current may rise or fall depending on the
difference between Vin and Vout), when the
ramp intersects VC-Buck, PWM signal for Buck
operation then is generated. Now the buck’s duty
cycle is within its limit, so there is BD operation in
current period, which means next period the
offset voltage will be removed. This is the so-
called buck-boost region. With heavy load due to
voltage drop on switches the actual input range
for this region may be a little wide.
error amplifier to generate control signal VC-Buck
.
By comparing VC-Buck with internal compensation
ramp (the sensed SWA’s current with slope
compensation) through Buck comparator, a PWM
control signal for PWM buck mode is outputted.
Another control signal VC-Boost is derived from VC-
through level shift. Similarly, VC-Boost
Buck
compares with the same ramp signal through
Boost comparator and generates the PWM
control signal for PWM boost mode. The switch
topology for the buck-boost converter is shown in
Figure 2.
Boost Region (VIN < VOUT
)
When the input voltage is significantly lower than
output voltage, the converter operates in boost
mode. The control signal VC-Buck is always higher
than compensation ramp even with the offset
voltage always added, thus switch A turns on
Figure 2—Buck-Boost Switch Topology
Buck Region (VIN > VOUT
)
continuously and switch
B
remains off.
Meanwhile, VC-Boost compares compensation
ramp normally and generates PWM signal,
therefore, switches C and D are pulse-width-
modulated to produce the required duty cycle to
support the output regulation voltage.
When the input voltage is significantly greater
than output voltage, which means the converter
can deliver energy to load within the maximum
duty cycle of SWA, so the converter operates in
buck mode. The control signal VC-Boost is always
lower than compensation ramp because Buck
can deliver enough energy to load, thus switch D
turns on constantly and switch C remains off.
Meanwhile, VC-Buck compares with compensation
ramp normally and generates PWM signal,
therefore, switches A and B are pulse-width-
modulated to produce the required duty cycle to
support the output voltage.
PSM
When Mode Pin is pulled down below the low
level threshold, the MP28163 will automatically
enter PSM if load is light. When working in PSM,
a train of SW pulses are initiated by a Boost
operation, and ended with BD operation. During
this process, SWD will be turned off if inductor
current is below about 100mA. In actual
MP28163 Rev. 1.0
1/26/2014
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MP28163 –HIGH EFFICIENCY SINGLE INDUCTOR BUCK-BOOST CONVERTER WITH 2.9A SWITCHES
waveforms the current may be much lower than
this value when SWD is turned off because of
internal delay.
Enable
The MP28163 has a dedicated enable control pin
(EN). The device operates when it is set high. If it
is set low the device stops switching, all the
internal blocks are turned off. Tie EN to Vin
through a resistor for automatic start up. Due to
EN bias or leakage current, the value of this
resistor should be set to provide EN pin with a
current above 10uA. Any signal to drive this pin
should be limited to 100uA if the maximum
voltage of this signal is above 6.5V.
SCP/OCP vs. two current limits
There are two current limits in MP28163. The
primary one is for steady PWM operation and it’s
typically 2.9A at 3.3V input.; The secondary one
is for limiting inrush current at startup, it’s
typically 1.6A to 1.9A, depending on Vin, too.
When load is over heavy, the primary limit would
protect MP28163 from being over thermal.
Therefore Vout would drop due to OCP. If Vout
drops below 0.6 times normal output, a hiccup
period is initiated to protect MP28163. this is the
SCP. In hiccup period, SWA and SWC are turned
off while SWB and SWD are turned on. After the
hiccup period ends, a soft re-startup begins.
Because Vout is below 1V (due to over load or
output short), the secondary current takes charge
of this process. After Vo rises above 1V, primary
current limit get in charge of. Now if load is still
over heavy (or output short still exists) such that
after SS ends Vout is still below 0.6*VOUT_NORMAL
and current hits one of the limits, another hiccup
period begins. However if the load recovers to
normal value during re-startup so that current
doesn’t hit its limit, or, Vout already rises above
0.6*VOUT_NORMAL, the re-startup succeeds, and
MP28163 enter normal operation.
Internal Soft-start
When EN pin is pulled high, and at the same time
the voltage on Vcc pin is above its UVLO rising
threshold MP28163 will start up with Soft-start
function to eliminate output overshoot. Soft-start
also functions during SCP recovery.
Under-Voltage Lockout
The under voltage lockout (UVLO) is implement
to protect the device from improper operating at
insufficient supply voltage. When the supply
voltage at VCC is below the UVLO threshold the
device is in shutdown mode. The UVLO rising
threshold is about 1.8V with 200mV hysteresis.
Over-Temperature Protection
An internal temperature sensor continuously
monitors the IC junction temperature. If the IC
temperature exceeds 160ºC typically the device
stops operating. As soon as the temperature falls
below 140 ºC typically normal operation is
restored.
As to the input/EN startup, the cases are same
as the SCP recovery process.
MP28163 Rev. 1.0
1/26/2014
www.MonolithicPower.com
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14
MP28163 –HIGH EFFICIENCY SINGLE INDUCTOR BUCK-BOOST CONVERTER WITH 2.9A SWITCHES
APPLICATION INFORMATION
The minimum inductor value for the application is
the higher one between Equation 2 and Equation
3. In addition to the inductance value the
maximum current the inductor can handle must
be calculated in order to avoid saturation.
Setting the Output Voltage
To use MP28163 correctly, A resistor divider
must be connected between Vout and GND, and
the middle point of the divider connected to FB
pin as shown in Typically Application on page 1.
VOUT ×(V
− VOUT )
IOUT
IN(MAX)
VOUT
IPEAK−BUCK
=
+
(4)
R1= (
−1)×R2
(1)
η
2× VIN(MAX) ×FREQ ×L
VFB
VIN(MIN) ×(VOUT − VIN(MIN)
VOUT ×FREQ ×L
)
VOUT ×IOUT
η× VIN(MIN)
High R2 resistance (eg. 100kꢀ) can reduce the
power consumption, while lower than 1Mꢀ
resistance is recommended for R1 for good
output accuracy.
(
IPEAK−BOOST
=
+
5)
Where η is the estimated efficiency of MP28163.
The maximum of the two values above must be
considered when selecting the inductor.
Inductor Selection
The inductor is the key passive component for
switching converters. With a buck-boost device,
the inductor selection affects the boundary
conditions in which the converter works, as buck
at the maximum input voltage and as a boost at
the minimum input voltage.
Input and Output Capacitor Selection
It is recommended to use ceramic capacitors with
low ESR as input and output capacitors in order
to filter any disturbance present in the input line
and to obtain stable operation.
Two critical inductance values are then obtained
according to the following formulas.
Minimum values of 10uF for both capacitors are
needed to achieve good behavior of the device.
VOUT ×(V
− VOUT
)
IN(MAX)
LMIN−BUCK
=
=
The input capacitor must be placed as close as
possible to the device.
(2)
(3)
VIN(MAX) ×FREQ × ΔIL
VIN(MIN) ×(VOUT − V
)
IN(MIN)
Other Consideration
LMIN−BOOST
Where:
VOUT ×FREQ × ΔIL
MP28163 employs the classic hiccup mode for
SCP. This method has an inherited drawback: if
the output short is released at a time closed to
SS end, then Vo would has overshoot. To
attenuate Vo overshoot at SCP recovery, a
forward RC series can be connected in parallel
with high side resistor of FB divider, as R3 and
C5 in Figure 5 shows. The RC acts as a soft
startup when Vo short is released at the time of
internal SS’s end.
FREQ: minimum switching frequency
∆IL: the peak-to-peak inductor ripple inductor
current. As a rule of thumb, the peak-to-peak
ripple can be set at 10%-20% of the output
current.
PCB Layout Guide
1. Input and output capacitors should be close to
MP28163’s Vin, Vout and PGND pins.
2. The wire connecting input capacitor to Vcc pin
should be as short as possible. For better
performance in noisy environment, an additional
capacitor very close to Vcc pin can be used to
bypass noise for Vcc.
MP28163 Rev. 1.0
1/26/2014
www.MonolithicPower.com
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15
MP28163 –HIGH EFFICIENCY SINGLE INDUCTOR BUCK-BOOST CONVERTER WITH 2.9A SWITCHES
3. FB resistor divider should be very close to FB
pin, and keep FB trace far away from noise.
Figure 3 shows an example of PCB layout for
which the reference schematic is shown on
Figure 4.
Figure 4—Reference Circuit for PCB Guide
L1
Design Example
Below is a design example following the
application guidelines for the specifications:
Table 1: Design Example
VIN (V)
VOUT (V)
2-5.5
3.3V
Cin
Cout
R1
The detailed application schematic is shown in
Figure 5 and its performance can be found in
TPC section.
EN
MODE
R2
Top Layer
Bottom Layer
Figure 3—PCB Layout
MP28163 Rev. 1.0
1/26/2014
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MP28163 –HIGH EFFICIENCY SINGLE INDUCTOR BUCK-BOOST CONVERTER WITH 2.9A SWITCHES
TYPICAL APPLICATION CIRCUITS
Figure 5—3.3V Output Application Circuit
Figure 6—5V Output Application Circuit
MP28163 Rev. 1.0
1/26/2014
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MP28163 –HIGH EFFICIENCY SINGLE INDUCTOR BUCK-BOOST CONVERTER WITH 2.9A SWITCHES
PACKAGE INFORMATION
QFN10 (3mmX3mm)
2.90
3.10
0.30
0.50
1.45
1.75
PIN 1 ID
SEE DETAIL A
PIN 1 ID
MARKING
0.18
0.30
10
1
5
2.25
2.55
2.90
3.10
PIN 1 ID
INDEX AREA
0.50
BSC
6
TOP VIEW
BOTTOM VIEW
PIN 1 ID OPTION A
R0.20 TYP.
PIN 1 ID OPTION B
R0.20TYP.
0.80
1.00
0.20 REF
0.00
0.05
SIDE VIEW
DETAIL A
NOTE:
2.90
1.70
1) ALL DIMENSIONS ARE IN MILLIMETERS.
0.70
0.25
2) EXPOSED PADDLE SIZE DOES NOT INCLUDE MOLD FLASH.
3) LEAD COPLANARITY SHALL BE0.10 MILLIMETER MAX.
4) DRAWING CONFORMS TO JEDEC MO-229, VARIATION VEED-5.
5) DRAWING IS NOT TO SCALE.
2.50
0.50
RECOMMENDED LAND PATTERN
NOTICE: The information in this document is subject to change without notice. Please contact MPS for current specifications.
Users should warrant and guarantee that third party Intellectual Property rights are not infringed upon when integrating MPS
products into any application. MPS will not assume any legal responsibility for any said applications.
MP28163 Rev. 1.0
1/26/2014
www.MonolithicPower.com
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© 2014 MPS. All Rights Reserved.
18
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MPS
MP28224DQ-LF-Z
Switching Regulator, Current-mode, 2.4A, 1800kHz Switching Freq-Max, 3 X3 MM, ROHS COMPLIANT, MO-229VEED-5, QFN-10
MPS
MP28224DQ-Z
Switching Regulator, Current-mode, 2.4A, 1800kHz Switching Freq-Max, 3 X3 MM, MO-229VEED-5, QFN-10
MPS
MP28225DL
Switching Regulator, Current-mode, 1600kHz Switching Freq-Max, PDSO14, 3 X 4 MM, MO-229VEED-5, QFN-14
MPS
MP28225DL-LF
Switching Regulator, Current-mode, 1600kHz Switching Freq-Max, PDSO14, 3 X 4 MM, ROHS COMPLIANT, MO-229VEED-5, QFN-14
MPS
MP28225DL-LF-Z
Switching Regulator, Current-mode, 1600kHz Switching Freq-Max, PDSO14, 3 X 4 MM, ROHS COMPLIANT, MO-229VEED-5, QFN-14
MPS
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