MP28164 [MPS]
High-Efficiency, Single-Inductor, Buck-Boost Converter with 4.2A Switches;
| 型号： | MP28164 |
| 厂家： | 
MONOLITHIC POWER SYSTEMS |
| 描述： | High-Efficiency, Single-Inductor, Buck-Boost Converter with 4.2A Switches |
| 文件： | 总20页 (文件大小：1632K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
MP28164
High-Efficiency, Single-Inductor,
Buck-Boost Converter with 4.2A Switches
The Future of Analog IC Technology
DESCRIPTION
The MP28164 is
FEATURES
1.8V Minimum Start-Up Input Voltage
1.2V to 5.5V Input Work Range
1.5V to 5V Output Range
4.2A Switching Current Limit
3.3V/2A Load Capability from a 2.5V-to-
5.5V Input Supply
a
high-efficiency, low-
quiescent current, buck-boost converter that
operates from an input voltage above, equal to,
or below the output voltage. The device
provides a compact solution for products
powered by one-cell Lithium-Ion or multi-cell
alkaline batteries where the output voltage is
within the battery voltage range.
2MHz Fixed or External Synchronous
Switching Frequency
Selectable PSM/PWM Mode
Typical 25μA Quiescent Current
High Efficiency up to 95%
Load Disconnect during Shutdown
Internal Soft Start and Compensation
Power Good Indicator
Hiccup Mode for Short-Circuit Protection
(SCP)
Over-Temperature Protection (OTP)
Available in a Small QFN-11 (2mmx3mm)
Package
The MP28164 uses current-mode control with
fixed PWM frequency for optimal stability and
transient response. The fixed 2MHz switching
frequency and integrated low RDS(ON) MOSFETs
minimize the solution footprint while maintaining
high efficiency.
To ensure the longest possible battery life, the
MP28164 uses an optional pulse skipping mode
that reduces the switching frequency under
light-load conditions. For other low-noise
applications where pulse skipping mode may
cause interference, a high-logic input on
MODE/SYNC guarantees fixed-frequency PWM
operation under all load conditions.
APPLICATIONS
Battery-Powered Devices
Portable Instruments
Tablet PC
The MP28164 operates with an input voltage
from 1.2V to 5.5V to provide an adjustable
output voltage from 1.5V to 5V. With an input
from 2.5V to 5.5V, the device can supply 2A of
current to the load with a 3.3V output voltage.
Super-Cap Charger
All MPS parts are lead-free, halogen-free, and adhere to the RoHS directive.
For MPS green status, please visit the MPS website under Quality
Assurance. “MPS” and “The Future of Analog IC Technology” are registered
trademarks of Monolithic Power Systems, Inc.
The MP28164 is available in a small QFN-11
(2mmx3mm) package.
TYPICAL APPLICATION
100
95
90
85
80
75
70
65
60
55
50
0.001 0.01
0.1
1
10
MP28164 Rev. 1.0
3/28/2016
www.MonolithicPower.com
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© 2016 MPS. All Rights Reserved.
1
MP28164 – SINGLE-INDUCTOR, BUCK-BOOST CONVERTER WITH 4.2A SWITCHES
ORDERING INFORMATION
Part Number*
Package
Top Marking
MP28164GD
QFN-11 (2mmx3mm)
See Below
* For Tape & Reel, add suffix –Z (e.g. MP28164GD–Z)
TOP MARKING
ANA: Product code of MP28164GD
Y: Year code
WW: Week code
LLL: Lot number
PACKAGE REFERENCE
TOP VIEW
QFN-11 (2mmx3mm)
MP28164 Rev. 1.0
3/28/2016
www.MonolithicPower.com
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© 2016 MPS. All Rights Reserved.
2
MP28164 – SINGLE-INDUCTOR, BUCK-BOOST CONVERTER WITH 4.2A SWITCHES
ABSOLUTE MAXIMUM RATINGS (1)
Thermal Resistance (5) θJA θJC
QFN-11 (2mmx3mm) ….…..70.......15.......°C/W
VIN to GND.......................................-0.3V to 6V
SW1/2 to GND..................-0.3V (-2V for <10ns)
to 6.5V (8.5V for <10ns)
NOTES:
1) Exceeding these ratings may damage the device.
2) The maximum allowable power dissipation is a function of the
maximum junction temperature TJ (MAX), the junction-to-
ambient thermal resistance θJA, and the ambient temperature
TA. The maximum allowable continuous power dissipation at
any ambient temperature is calculated by PD (MAX) = (TJ
(MAX)-TA)/θJA. Exceeding the maximum allowable power
dissipation produces an excessive die temperature, causing
the regulator to go into thermal shutdown. Internal thermal
shutdown circuitry protects the device from permanent
damage.
All other pins.....................................-0.3V to 6V
Junction temperature................................150°C
Lead temperature .....................................260°C
(2)
Continuous power dissipation (TA = +25°C)
QFN-11 (2mmx3mm)............................... 1.78W
Storage temperature................ -65C to +150C
Recommended Operating Conditions (3)
3) The device is not guaranteed to function outside of its
operating conditions.
4) If VCC is powered from a source higher than 1.8V (such as
Startup supply voltage (VST)............1.8V to 5.5V
(4)
Operation voltage (VIN) ...............1.2V to 5.5V
VOUT), the MP28164 can work down to VIN = 1.2V, but the load
capability is lower when VIN = 1.2V because of the high
RDS(ON) of SWA and low current limit.
Output voltage (VOUT).........................1.5V to 5V
Operating junction. temp. (TJ)...-40°C to +125°C
5) Measured on JESD51-7, 4-layer PCB.
MP28164 Rev. 1.0
3/28/2016
www.MonolithicPower.com
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© 2016 MPS. All Rights Reserved.
3
MP28164 – SINGLE-INDUCTOR, BUCK-BOOST CONVERTER WITH 4.2A SWITCHES
ELECTRICAL CHARACTERISTICS
VIN = VEN = VOUT = 3.3V, TJ = -40°C to 125°C. Typical value is tested at 25°C, unless otherwise
noted.
Parameter
Symbol Condition
VCC floating, VIN rising, test VIN
when IC starts up
Min
Typ
Max
Units
VIN under-voltage lockout rising
threshold
VIN-UVLO-R
1.63
1.7
1.77
V
VIN under-voltage lockout falling
threshold
VIN-UVLO-F VOUT = 3.3V, VIN falling
VCC-UVLO-F VIN = 1.2V, VCC falling
0.69
1.56
V
V
VCC under-voltage lockout
falling threshold
1.45
1.67
TJ = 25°C
VREF
495
500
500
505
mV
mV
Feedback voltage reference
Oscillator frequency
TJ = -40°C to +125°C
492.5
507.5
1700
1000
2000
2300
kHz
kHz
FREQ
Frequency range for
synchronization
3000
5
Steady state current limit
Start-up current limit
ISW1
ISW2
VFB > 60%VREF
VFB < 60%VREF
3.5
1.7
4.2
2.5
22
A
A
NMOS switch on resistance
PMOS switch on resistance
RDS(ON)-N SWB, SWC
RDS(ON)-P SWA, SWD
mΩ
mΩ
27.5
VFB = 0.55V, VIN = 2.5V,
VOUT = 3.3V, test VOUT
25
μA
μA
Quiescent current
IQ
VFB = 0.55V, VIN = 2.5V,
VOUT = 3.3V, test VIN
3.3
Shutdown current
IS
VEN = 0V
3
μA
ms
V
Soft-start time
TSS
Internal VREF from 0V to 0.5V
1.5
EN/MODE input low voltage
EN/MODE input high voltage
0.4
1.2
V
VEN = 3.3V
VEN = 0V
2.1
0
μA
μA
VREF
VREF
EN input current
IEN
Power good rising threshold
Power good falling threshold
PGVTH-HI
PGVTH-LO
87.5% 91.5% 95.5%
72%
76%
118
19
80%
Low to high
High to low
Power good delay
PGDT
VPG
μs
Power good sink current
capability
Sink 3mA
0.3
V
Thermal shutdown(6)
Thermal shutdown hysteresis(6)
NOTE:
TSHDN
THYS
160
20
°C
°C
6) Guaranteed by characterization, not tested in production.
MP28164 Rev. 1.0
3/28/2016
www.MonolithicPower.com
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© 2016 MPS. All Rights Reserved.
4
MP28164 – SINGLE-INDUCTOR, BUCK-BOOST CONVERTER WITH 4.2A SWITCHES
TYPICAL PERFORMANCE CHARACTERISTICS
VIN = 3.3V, VOUT = 3.3V, L = 1µH, COUT = 2x22µF, TA = 25°C, unless otherwise noted.
5
4.5
4
50
45
40
35
30
25
20
15
10
5
5
4.5
4
Limit for Steady State
Limit for Steady State
Limit for Start-Up
3.5
3
3.5
3
Supplied by VOUT
2.5
2
2.5
2
Limit for Start-Up
1.5
1.5
1
1
0
1.5
2.5
3.5
4.5
5.5
3.5
4 4.5 5 5.5
-40 -20 0 20 40 60 80100 120140
1 1.5 2 2.5
3
1.9
1.2
1.0
0.8
0.6
0.4
0.2
520
515
510
505
500
495
490
485
480
1.8
1.7
1.6
1.5
1.4
V
Rising
Falling
IN
Rising
V
CC
Falling
-40 -20 0 20 40 60 80100 120140
-40 -20 0 20 40 60 80100 120140
-40 -20 0 20 40 60 80100 120140
2200
1.0
2150
2100
2050
2000
1950
1900
1850
1800
0.8
0.6
0.4
0.2
0.0
-40 -20 0 20 40 60 80100 120140
-40 -20 0 20 40 60 80100 120140
MP28164 Rev. 1.0
3/28/2016
www.MonolithicPower.com
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© 2016 MPS. All Rights Reserved.
5
MP28164 – SINGLE-INDUCTOR, BUCK-BOOST CONVERTER WITH 4.2A SWITCHES
TYPICAL PERFORMANCE CHARACTERISTICS (continued)
VIN = 3.3V, VOUT = 3.3V, L = 1µH, COUT = 2x22µF, TA = 25°C, unless otherwise noted.
100
95
90
85
80
75
70
65
60
100
95
90
85
80
75
70
65
60
100
95
90
85
80
75
70
65
60
55
50
55
50
1.5
55
50
0.001
0.001 0.01
0.1
1
10
2
2.5
3
3.5
4
4.5
5
5.5
0.01
0.1
1
10
0.6
0.4
0.2
0.6
0.4
0.2
100
90
80
70
60
0
-0.2
-0.4
-0.6
0
-0.2
-0.4
-0.6
50
40
1.5
2
2.5
3
3.5
4
4.5
5
5.5
0
0.5
1
1.5
2
1 1.5 2 2.5 3 3.5 4 4.5 5 5.5
40
35
30
25
20
15
10
1
0.8
0.6
0.4
0.2
0
45
40
35
30
25
20
15
10
5
0
5
0
0
0.5
1
1.5
2
2.5
3
3.5
0
0.5
1
1.5
2
2.5
1 1.5 2 2.5 3 3.5 4 4.5 5 5.5
MP28164 Rev. 1.0
3/28/2016
www.MonolithicPower.com
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© 2016 MPS. All Rights Reserved.
6
MP28164 – SINGLE-INDUCTOR, BUCK-BOOST CONVERTER WITH 4.2A SWITCHES
TYPICAL PERFORMANCE CHARACTERISTICS (continued)
VIN = 3.3V, VOUT = 3.3V, L = 1µH, COUT = 2x22µF, TA = 25°C, unless otherwise noted.
3
4
2.5
3
2
1.5
2
1
1
0.5
0
0
1 1.5 2 2.5 3 3.5 4 4.5 5 5.5
1 1.5 2 2.5 3 3.5 4 4.5 5 5.5
NOTE:
7) Tested with a 3.5A inductor peak current at a 3.3V input.
MP28164 Rev. 1.0
3/28/2016
www.MonolithicPower.com
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© 2016 MPS. All Rights Reserved.
7
MP28164 – SINGLE-INDUCTOR, BUCK-BOOST CONVERTER WITH 4.2A SWITCHES
TYPICAL PERFORMANCE CHARACTERISTICS (continued)
VIN = 3.3V, VOUT = 3.3V, L = 1µH, COUT = 2x22µF, TA = 25°C, unless otherwise noted.
V
V
V
OUT_AC
OUT_AC
OUT_AC
50mV/div.
10mV/div.
50mV/div.
V
V
V
SW1
SW1
SW1
2V/div.
2V/div.
2V/div.
V
V
SW2
SW2
2V/div.
2V/div.
V
SW2
2V/div.
I
I
I
L
L
L
2A/div.
2A/div.
2A/div.
V
V
V
OUT_AC
OUT_AC
OUT_AC
10mV/div.
10mV/div.
10mV/div.
V
V
V
SW1
SW1
SW1
2V/div.
2V/div.
2V/div.
V
V
V
SW2
SW2
SW2
2V/div.
2V/div.
2V/div.
I
L
500mA/div.
I
I
L
L
500mA/div.
500mA/div.
V
V
V
OUT_AC
OUT_AC
OUT_AC
100mV/div.
100mV/div.
100mV/div.
V
V
V
SW1
SW1
SW1
2V/div.
2V/div.
2V/div.
V
V
V
SW2
SW2
SW2
2V/div.
2V/div.
2V/div.
I
I
I
L
L
L
1A/div.
1A/div.
1A/div.
MP28164 Rev. 1.0
3/28/2016
www.MonolithicPower.com
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© 2016 MPS. All Rights Reserved.
8
MP28164 – SINGLE-INDUCTOR, BUCK-BOOST CONVERTER WITH 4.2A SWITCHES
TYPICAL PERFORMANCE CHARACTERISTICS (continued)
VIN = 3.3V, VOUT = 3.3V, L = 1µH, COUT = 2x22µF, TA = 25°C, unless otherwise noted.
V
V
V
OUT_AC
OUT_AC
OUT_AC
50mV/div.
50mV/div.
20mV/div.
V
V
V
SW1
SW1
SW1
2V/div.
2V/div.
2V/div.
V
V
V
SW2
SW2
SW2
2V/div.
2V/div.
2V/div.
I
I
I
L
L
L
2A/div.
2A/div.
2A/div.
V
V
V
OUT
OUT
OUT
2V/div.
V
2V/div.
2V/div.
V
2V/div.
V
PG
PG
PG
2V/div.
2V/div.
V
IN
V
V
IN
IN
2V/div.
2V/div.
2V/div.
V
V
SW1
V
SW1
SW1
2V/div.
2V/div.
2V/div.
V
V
V
SW2
SW2
SW2
2V/div.
2V/div.
2V/div.
I
I
L
L
1A/div.
500mA/div.
I
L
2A/div.
V
V
V
OUT
OUT
OUT
2V/div.
V
2V/div.
2V/div.
V
2V/div.
2V/div.
V
2V/div.
PG
PG
PG
V
IN
V
V
IN
IN
2V/div.
2V/div.
2V/div.
V
V
V
SW1
SW1
SW1
2V/div.
2V/div.
2V/div.
V
V
V
SW2
SW2
SW2
2V/div.
2V/div.
2V/div.
I
L
1A/div.
I
I
L
L
5A/div.
1A/div.
MP28164 Rev. 1.0
3/28/2016
www.MonolithicPower.com
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© 2016 MPS. All Rights Reserved.
9
MP28164 – SINGLE-INDUCTOR, BUCK-BOOST CONVERTER WITH 4.2A SWITCHES
TYPICAL PERFORMANCE CHARACTERISTICS (continued)
VIN = 3.3V, VOUT = 3.3V, L = 1µH, COUT = 2x22µF, TA = 25°C, unless otherwise noted.
V
V
OUT
V
OUT
OUT
2V/div.
2V/div.
V
2V/div.
V
PG
V
PG
PG
2V/div.
2V/div.
2V/div.
V
V
EN
V
EN
EN
5V/div.
5V/div.
5V/div.
V
SW1
V
V
SW1
SW1
2V/div.
2V/div.
2V/div.
V
V
SW2
SW2
V
SW2
2V/div.
2V/div.
2V/div.
I
I
L
L
I
L
500mA/div.
500mA/div.
2A/div.
V
V
V
OUT
OUT
OUT
2V/div.
V
2V/div.
V
2V/div.
V
2V/div.
V
2V/div.
V
PG
PG
PG
2V/div.
V
EN
EN
EN
5V/div.
5V/div.
5V/div.
V
SW1
2V/div.
V
V
SW1
SW1
2V/div.
2V/div.
V
SW2
V
2V/div.
SW2
V
SW2
2V/div.
2V/div.
I
L
I
I
L
L
1A/div.
2A/div.
1A/div.
V
V
OUT_AC
V
OUT_AC
200mV/div.
OUT_AC
200mV/div.
200mV/div.
I
I
I
LOAD
LOAD
LOAD
500mA/div.
500mA/div.
500mA/div.
MP28164 Rev. 1.0
3/28/2016
www.MonolithicPower.com
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© 2016 MPS. All Rights Reserved.
10
MP28164 – SINGLE-INDUCTOR, BUCK-BOOST CONVERTER WITH 4.2A SWITCHES
TYPICAL PERFORMANCE CHARACTERISTICS (continued)
VIN = 3.3V, VOUT = 3.3V, L = 1µH, COUT = 2x22µF, TA = 25°C, unless otherwise noted.
V
V
OUT
OUT
2V/div.
2V/div.
V
V
SW1
SW1
2V/div.
2V/div.
V
V
SW2
SW2
2V/div.
2V/div.
I
I
L
L
2A/div.
2A/div.
MP28164 Rev. 1.0
3/28/2016
www.MonolithicPower.com
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© 2016 MPS. All Rights Reserved.
11
MP28164 – SINGLE-INDUCTOR, BUCK-BOOST CONVERTER WITH 4.2A SWITCHES
PIN FUNCTIONS
Pin #
Name Description
On/off control. Pull EN high to enable the MP28164; pull EN down or leave EN floating to
disable all internal circuits. EN is pulled down to AGND with 1.5Mꢀ internally.
1
EN
Operation mode selection. If MODE/SYNC is low, the MP28164 switches between PSM
and fixed frequency PWM automatically, according to the load level. If MODE/SYNC is high,
MODE/ the MP28164 works in fixed frquency PWM mode continuously. An external clock can be
SYNC applied to MODE/SYNC for switching frequency synchronization. MODE/SYNC is pulled
down to AGND with 1Mꢀ internally. MODE/SYNC should be pulled high or low through a
resistor smaller than 10kꢀ.
2
3
4
5
6
PG
Power good indicator. PG switches high and low based on the feedback voltage (FB).
Supply voltage for control stage. VCC is powered by the higher value of VIN or VOUT.
Decouple VCC with a 1μF capacitor.
VCC
AGND Signal ground.
Output voltage feedback. Keep FB and its associated traces far from noise sources like
SW.
FB
Buck-boost converter output. An output capacitor should be placed close to VOUT and
PGND.
7
VOUT
SW2
Switch. Internal switches are connected to SW2. Connect an inductor between SW1 and
SW2.
8
9
PGND Power ground.
Switch. Internal switches are connected to SW1. Connect an inductor between SW1 and
SW2.
10
11
SW1
VIN
Supply voltage for power stage.
MP28164 Rev. 1.0
3/28/2016
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12
MP28164 – SINGLE-INDUCTOR, BUCK-BOOST CONVERTER WITH 4.2A SWITCHES
BLOCK DIAGRAM
Figure 1: Functional Block Diagram
MP28164 Rev. 1.0
3/28/2016
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13
MP28164 – SINGLE-INDUCTOR, BUCK-BOOST CONVERTER WITH 4.2A SWITCHES
in the secondary period) and an offset voltage is
OPERATION
added to the current ramp signal to allow it to
reach VC-Buck. SWC turns off when the current
ramp signal intersects with VC-Boost in the
secondary period, and SWD conducts the
inductor current when SWC is off. This is called
boost operation.
The MP28164 is a high-efficiency, dual-mode,
buck-boost converter that provides an output
voltage above, equal to, or below the input
voltage. The output voltage is sensed via FB
through an external resistor divider from the
output to ground (see Figure 1). The voltage
difference between FB and the internal reference
is amplified by the error amplifier to generate a
control signal (VC-Buck). By comparing VC-Buck with
the internal current ramp signal (the sensed
SWA’s current with slope compensation) through
the buck comparator, a pulse-width modulation
(PWM) control signal for the buck leg (SWA,
SWB) is generated.
SWA turns off when the current ramp signal
intersects with VC-Buck in the secondary period,
and SWB turns on to conduct the inductor current
after SWA turns off. This is called buck operation.
If SWB turns on in the secondary period, the
boost operation (SWC on) is disabled in the
following cycle. If SWA continues to conduct with
100% duty in the secondary cycle, the boost
operation is also enabled in the following duty
cycle. SWA/SWB and SWC/SWD switch during
this condition simultaneously. This is called buck-
boost mode.
Another control signal (VC-Boost) is derived from VC-
through the level shift. Similarly, VC-Boost is
Buck
compared with the same ramp signal through the
boost comparator and generates a PWM control
signal for the boost leg (SWC, SWD). The switch
topology for the buck-boost converter is shown in
Figure 2.
Boost Region (VIN < VOUT)
When the input voltage is significantly lower than
the output voltage, the control voltage (VC-Buck) is
always higher than the current ramp signal. The
offset voltage is added to the current signal, so
SWB cannot turn on in all cycles. The boost
operation (SWC on) is enabled in every cycle
based on the logic, so only SWC and SWD
switch. This is called boost mode. In this
condition, SWC/SWD are pulse-width modulated
to produce the required duty cycle and eventually
support the output regulation voltage.
Figure 2: Buck-Boost Switch Topology
Buck Region (VIN > VOUT)
When the input voltage is significantly higher
than the output voltage, the converter can deliver
energy to the load within SWA’s maximum duty
cycle by switching SWA and SWB. The converter
operates in buck mode. In this condition, SWD
remains on and SWC remains off. VC-Buck
compares with the current ramp signal normally
and generates a PWM output. Therefore,
SWA/SWB are pulse-width modulated to produce
the required duty cycle and eventually support
the output voltage.
Under-Voltage Lockout (UVLO)
Under-voltage lockout (UVLO) is used to protect
the device from operating at an insufficient
supply voltage. The MP28164’s UVLO circuit
monitors the VCC voltage. During start-up, VIN
must rise higher than VIN-UVLO-R to support enough
VCC voltage and enable the IC. After the IC is
enabled, VCC is powered by VIN or VOUT
(depending on which is higher), so the IC can
work, even if VIN drops to 1.2V, unless VCC
drops to the VCC-UVLO-F threshold.
Buck-Boost Region (VIN ≈ VOUT)
During start-up, if VCC has a bias voltage from
another power supply, the MP28164 can work
with 1.2V of input power. If VIN is much lower
than 1.2V, SWA RDS(ON) is high, and the
MP28164 cannot supply high power to the output.
If VIN drops to 0.69V, the MP28164 stops
working.
When VIN is close to VOUT, the converter is
unable to provide enough energy to load due to
SWA’s maximum duty cycle, so the current ramp
signal cannot trigger VC-Buck in the first period, and
SWA remains on with 100% duty cycle. If SWB is
not turned on in the first period, boost begins
working in the secondary period (SWC switches
MP28164 Rev. 1.0
3/28/2016
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14
MP28164 – SINGLE-INDUCTOR, BUCK-BOOST CONVERTER WITH 4.2A SWITCHES
VCC Power Supply
When MODE/SYNC is pulled low, the MP28164
enters PSM automatically when the load
decreases. In PSM, a group of switching pulses
are initiated when the internal VC-Buck rises higher
than the PSM threshold (group pulses start with
SWA/SWC on and end with SWB/SWD on).
SWD is turned off if the SWD current flows from
VOUT to SW2 in each period.
When EN is high and VIN ramps up, VIN charges
VCC. If VIN is higher than VIN-UVLO-R, the
MP28164 begins working. All internal circuits of
the MP28164 are supplied by VCC, and VCC
only needs to be decoupled with a ceramic
capacitor less than 1µF. After the system starts
up, VCC is powered by the higher value of VIN or
VOUT internally. If VCC is powered by VOUT,
the MP28164 does not shut down until VIN drops
to the UVLO falling threshold (0.69V) or VCC
drops to the VCC UVLO falling threshold (1.56V).
It is not suggested to supply the MP28164 with
an input lower than 1.2V, even if VCC has a bias
voltage due to SWA (P-FET) having an RDS(ON)
that is too high when VIN is low. Even with 1.2V
of input power, the load capability is weaker than
During start-up or short-circuit protection (SCP)
recovery condition, the MP28164 works in fixed-
frequency PWM mode, even if MODE/SYNC is
low. The negative inductor current is limited to
-1A, the same as in constant frequency mode.
OCP/SCP and Two Current Limits
There are two peak-current limits in the MP28164.
One is a steady-state switching current limit with
a 4.2A typical value. Another one is a start-up
switching current limit with a 2.5A typical value.
The start-up current limit can control the input
inrush current at a lower level when VFB < 60% x
the high input condition due to the RDS(ON)
.
Internal Soft Start (SS)
When EN is high and VIN is above the UVLO
rising threshold, the MP28164 starts up with a
soft-start function. The internal soft-start (SS)
signal ramps up and controls the feedback
reference voltage. After 4ms of blank time, if
VOUT has not risen to 60% of the normal output
voltage, or if VOUT is pulled down to 60% of the
normal output voltage due to an overload, the
soft-start signal is pulled down to GND and
hiccup protection is initiated. During start-up or
hiccup recovery condition, an internal SS signal
is clamped to VFB + 0.3V if VOUT does not rise
up. This limit can prevent a VOUT overshoot if
the heavy load disappears suddenly during start-
up.
VREF during start-up.
In overload or short-circuit condition, VOUT
drops due to the steady-state switching current
limit. If VOUT drops below 60% of its normal
output, the MP28164 stops switching and
recovers after ~8ms with hiccup mode protection.
After the switching stops in hiccup protection, the
internal soft-start signal is clamped to VFB + 0.3V,
where VFB is the divided voltage from the residual
VOUT. This smooths the soft start-up when the
MP28164 recovers from hiccup protection.
During the soft-start time, the MP28164 blanks
during hiccup protection for about 4ms. After the
4ms blank time, if VOUT is still lower than 60% of
the normal voltage, the MP28164 resumes
hiccup mode. If VOUT rises above 60% of the
normal value, the MP28164 enters normal
operation.
During start-up or recovery from hiccup, if there
is already some voltage on the output, this
voltage is discharged by the negative current limit
(-1A when the MP28164 operates in PWM mode
regardless of the MODE/SYNC setting) to equal
the SS voltage. VOUT then rises normally.
MODE/SYNC Setting
The MP28164 can be set in PSM or fixed-
frequency PWM mode in light load through the
MODE/SYNC setting. When MODE/SYNC is
pulled high, the MP28164 operates in fixed-
frequency PWM mode. The current conducts
while the inductor current direction reverses. In
this mode, the VOUT ripple is lower than in
power-save mode (PSM), but the power loss is
higher due to the high-frequency switching.
MP28164 Rev. 1.0
3/28/2016
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© 2016 MPS. All Rights Reserved.
15
MP28164 – SINGLE-INDUCTOR, BUCK-BOOST CONVERTER WITH 4.2A SWITCHES
Power Good (PG)
Over-Voltage Protection (OVP)
The MP28164 has a power-good (PG) output.
PG is the open drain of the MOSFET. Pull PG up
to VCC through a resistor (typically 100kꢀ)
during application. After the FB voltage reaches
91.5% of the VREF voltage, PG is pulled high.
When the FB voltage drops to 76% of the VREF
voltage, PG is pulled low.
If VOUT is higher than the typical 6.3V value, the
switching stops. This helps protect the device
from high-voltage stress. After the output drops
below 5.3V, the switching recovers automatically.
Over-Temperature Protection (OTP)
An internal temperature sensor continuously
monitors the IC junction temperature. If the IC
temperature exceeds 160°C, the device stops
operating. Once the temperature falls below
140°C, normal operation resumes.
PG has self-driving capability. If the MP28164 is
off and PG is pulled up to another DC power
source through a resistor, PG can also be pulled
low (~0.7V) by the self-driving circuit.
MP28164 Rev. 1.0
3/28/2016
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© 2016 MPS. All Rights Reserved.
16
MP28164 – SINGLE-INDUCTOR, BUCK-BOOST CONVERTER WITH 4.2A SWITCHES
Input and Output Capacitor Selection
APPLICATION INFORMATION
Setting the Output Voltage
It is recommended to use ceramic capacitors with
a low ESR as input and output capacitors to filter
any disturbance present in the input and output
line and to achieve stable operation.
A resistor divider from VOUT to FB is necessary
to set the MP28164’s output voltage. The high-
side feedback resistor (R1) can be calculated
with Equation (1):
Output capacitors with a minimum 10µF input
and 22µF output are required to achieve optimal
behavior from the device. The output capacitor
affects loop stability. The input and output
capacitors must be placed as close as possible
to the device. Refer to the Typical Application
Circuits section for optimized capacitor selection
details.
VOUT
R1 (
1)R2
(1)
VFB
Where R2 is the low-side feedback resistor with a
recommended value from 60kꢀ through 360kꢀ
to balance the stability and transient response.
Inductor Selection
With one buck-boost topology circuit, the inductor
must support the buck application with the
maximum input voltage and boost application
with the minimum input voltage. Two critical
inductance values can be determined according
to the buck mode and boost mode current ripple,
as shown in Equation (2) and Equation (3):
VOUT (V
VOUT
)
IN(MAX)
LMINBUCK
(2)
(3)
VIN(MAX) FREQ IL
VIN(MIN) (VOUT V
)
IN(MIN)
LMINBOOST
VOUT FREQ IL
Where FREQ is the switching frequency, and ∆IL is
the peak-to-peak inductor current ripple. The
peak-to-peak ripple can be set to 10%-30% of
the inductor current. The minimum inductor value
for the application must be higher than the
calculated value from both Equation 2 and
Equation 3.
In addition to the inductance value, the inductor
must support the peak current based on Equation
(4) and Equation (5) to avoid saturation:
V
OUT (VIN(MAX) V )
OUT
IPEAKBUCK IOUT
(4)
(5)
2VIN(MAX) FREQ L
VIN(MIN) (VOUT V
)
VOUT IOUT
IN(MIN)
IPEAKBOOST
V
2 VOUT FREQ L
IN(MIN)
Where η is the estimated efficiency.
MP28164 Rev. 1.0
3/28/2016
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17
MP28164 – SINGLE-INDUCTOR, BUCK-BOOST CONVERTER WITH 4.2A SWITCHES
PCB Layout Guidelines
Efficient PCB layout of the high-frequency
switching power supplies is critical for stable
operation. Poor layout can result in reduced
performance, excessive EMI, resistive loss, and
system instability. For best results, refer to Figure
3 and follow the guidelines below.
1. Place the input capacitor and output capacitor
close to VIN, VOUT, and PGND.
2. Place the VCC decoupling capacitor close to
VCC and AGND.
Figure 4: Reference Circuit for PCB Guide
Design Example
3. Keep the FB resistor divider very close to FB.
Table 1 is a design example following the
application guidelines for the specifications
below:
4. Keep the FB trace far away from noise
sources, such as SW1 and SW2.
5. Ensure the layout of the copper of GND, VIN,
and VOUT is wide enough to conduct high
current and lower the die temperature.
Table 1: Design Example
Start-Up VIN (V)
Operation VIN (V)
VOUT (V)
1.8 - 5.5
1.2 - 5.5
3.3V
6. Place vias in the GND copper around the chip
for better thermal performance.
The detailed application schematic is shown in
Figure 5, and the performance can be found in
the
Typical
Performance
Characteristics
sections.
Top Layer
GND
Bottom Layer
Figure 3: PCB Layout Recommendation
MP28164 Rev. 1.0
3/28/2016
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18
MP28164 – SINGLE-INDUCTOR, BUCK-BOOST CONVERTER WITH 4.2A SWITCHES
TYPICAL APPLICATION CIRCUITS
Figure 5: 3.3V Output Application Circuit
Figure 6: 5V Output Application Circuit
MP28164 Rev. 1.0
3/28/2016
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19
MP28164 – SINGLE-INDUCTOR, BUCK-BOOST CONVERTER WITH 4.2A SWITCHES
PACKAGE INFORMATION
QFN-11 (2mmx3mm)
PIN 1 ID
PIN 1 ID
MARKING
PIN 1 ID
INDEX AREA
TOP VIEW
BOTTOM VIEW
SIDE VIEW
NOTE:
1) ALL DIMENSIONS ARE IN MILLIMETERS.
2) EXPOSED PADDLE SIZE DOES NOT INCLUDE
MOLD FLASH.
3) LEAD COPLANARITY SHALL BE 0.10
MILLIMETERS MAX.
4) JEDEC REFERENCE IS MO-220.
5) DRAWING IS NOT TO SCALE.
RECOMMENDED LAND PATTERN
NOTICE: The information in this document is subject to change without notice. Please contact MPS for current specifications.
Users should warrant and guarantee that third party Intellectual Property rights are not infringed upon when integrating MPS
products into any application. MPS will not assume any legal responsibility for any said applications.
MP28164 Rev. 1.0
3/28/2016
www.MonolithicPower.com
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© 2016 MPS. All Rights Reserved.
20
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