TDA2030音频功率放大器 [ETC]
TDA2030音频功率放大器;
| 型号： | TDA2030音频功率放大器 |
| 厂家： | 
ETC |
| 描述： | TDA2030音频功率放大器 放大器 功率放大器 |
| 文件： | 总40页 (文件大小：1212K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
TDA2030
®
14W Hi-Fi AUDIO AMPLIFIER
DESCRIPTION
The TDA2030 is a monolithic integrated circuit in
Pentawatt® package, intended for use as a low
frequency class AB amplifier. Typically it provides
14W output power (d = 0.5%) at 14V/4Ω; at ± 14V
or 28V, the guaranteed output power is 12W on a
4Ω load and 8W on a 8Ω (DIN45500).
The TDA2030 provides high output current and has
very low harmonic and cross-over distortion.
Further the device incorporates an original (and
patented) short circuit protection system compris-
ing an arrangement for automatically limiting the
dissipated power so as to keep the working point
of the output transistors within their safe operating
area. A conventional thermal shut-down system is
also included.
Pentawatt
ORDERING NUMBERS : TDA2030H
TDA2030V
ABSOLUTE MAXIMUM RATINGS
Symbol
Parameter
Value
Unit
Vs
Vi
Supply voltage
V
18 (36)
Vs
±
Input voltage
Vi
Differential input voltage
V
A
15
±
Io
Output peak current (internally limited)
3.5
20
Ptot
W
Power dissipation at Tcase = 90 C
°
T
stg, Tj
Stoprage and junction temperature
-40 to 150
C
°
TYPICAL APPLICATION
1/12
June 1998
TDA2030
PIN CONNECTION (top view)
+VS
OUTPUT
-VS
INVERTING INPUT
NON INVERTING INPUT
TEST CIRCUIT
2/12
TDA2030
THERMAL DATA
Symbol
Parameter
Value
Unit
Rth j-case
Thermal resistance junction-case
max
3
C/W
°
ELECTRICAL CHARACTERISTICS (Refer to the test circuit, Vs = ± 14V , Tamb = 25°C unless otherwise
specified) for single Supply refer to fig. 15 Vs = 28V
Symbol
Parameter
Supply voltage
Test conditions
Min.
Typ.
Max.
18
Unit
V
6
±
±
Vs
12
36
Id
Ib
Quiescent drain current
Input bias current
Input offset voltage
Input offset current
Output power
40
60
2
mA
0.2
A
µ
V = 18V (Vs = 36V)
±
s
Vos
Ios
Po
mV
nA
2
20
±
±
20
200
±
±
d = 0.5%
Gv = 30 dB
f = 40 to 15,000 Hz
R = 4
12
8
14
9
W
W
Ω
L
R = 8
Ω
L
d = 10%
f = 1 KHz
Gv = 30 dB
R = 4
R = 8
L
18
11
W
W
Ω
Ω
L
Po = 0.1 to 12W
R = 4
d
Distortion
Gv = 30 dB
Ω
L
0.2
0.5
0.5
%
f = 40 to 15,000 Hz
Po = 0.1 to 8W
R = 8
Gv = 30 dB
Ω
L
0.1
%
f = 40 to 15,000 Hz
B
Power Bandwidth
(-3 dB)
Gv = 30 dB
Po = 12W
10 to 140,000
Hz
R = 4
Ω
L
Ri
Gv
Input resistance (pin 1)
Voltage gain (open loop)
Voltage gain (closed loop)
Input noise voltage
0.5
5
M
Ω
90
30
3
dB
dB
Gv
f = 1 kHz
B = 22 Hz to 22 KHz
29.5
30.5
10
eN
V
µ
iN
Input noise current
80
50
200
pA
dB
SVR
Supply voltage rejection
R = 4
Gv = 30 dB
40
Ω
L
R = 22 k
g
Ω
V
ripple = 0.5 Veff
fripple = 100 Hz
Id
Drain current
Po = 14W
Po = W
R = 4
R = 8
L
900
500
mA
mA
Ω
Ω
L
3/12
TDA2030
Figure 1. Output power vs.
supply voltage
Figure 2. Output power vs.
supply voltage
Figure 3. Distortion vs.
output power
Figure 4. Distortion vs.
output power
Figure 5. Distortion vs.
output power
Figure 6. Distortion vs.
frequency
Figure 8. Frequency re-
sponse with different values
of the rolloff capacitor C8
(see fig. 13)
Figure 7. Distortion vs.
frequency
Figure 9. Quiescent current
vs. supply voltage
4/12
TDA2030
Figure 10. Supply voltage
rejection vs. voltage gain
Figure 11. Power dissipa-
tion and efficiency vs. output
power
Figure 12. Maximum power
dissipation vs. supply volt-
age (sine wave operation)
APPLICATION INFORMATION
Figure 13. Typical amplifier
with split power supply
Figure 14. P.C. board and component layout for
the circuit of fig. 13 (1 : 1 scale)
5/12
TDA2030
APPLICATION INFORMATION (continued)
Figure 15. Typical amplifier
with single power supply
Figure 16. P.C. board and component layout for
the circuit of fig. 15 (1 : 1 scale)
Figure 17. Bridge amplifier configuration with split power supply (Po = 28W, Vs = ±14V)
6/12
TDA2030
PRACTICAL CONSIDERATIONS
Printed circuit board
The layout shown in Fig. 16 should be adopted by
the designers. If different layouts are used, the
ground points of input 1 and input 2 must be well
decoupled from the ground return of the output in
which a high current flows.
package and the heatsinkwith single supply voltage
configuration.
Application suggestions
The recommended values of the components are
those shown on application circuit of fig. 13.
Different values can be used. The following table
can help the designer.
Assembly suggestion
No electrical isolation is needed between the
Recomm.
value
Larger than
recommended value
Smaller than
recommended value
Component
Purpose
R1
Closed loop gain
setting
Increase of gain
Decrease of gain (*)
Increase of gain
22 k
680
22 k
Ω
Ω
Ω
R2
R3
R4
Closed loop gain
setting
Decrease of gain (*)
Non inverting input
biasing
Increase of input
impedance
Decrease of input
impedance
Frequency stability
Danger of osccilat. at
high frequencies
1
Ω
with induct. loads
R5
C1
Upper frequency
cutoff
Poor high frequencies
attenuation
Danger of
oscillation
3 R2
Input DC
decoupling
Increase of low
frequencies cutoff
1 F
µ
C2
Inverting DC
decoupling
Increase of low
frequencies cutoff
22 F
µ
C3, C4
C5, C6
Supply voltage
bypass
Danger of
oscillation
0.1
100
0.22
F
µ
Supply voltage
bypass
Danger of
oscillation
F
µ
C7
C8
Frequency stability
Danger of oscillation
Larger bandwidth
F
µ
1
Upper frequency
cutoff
Smaller bandwidth
2
π
B R1
D1, D2
1N4001
To protect the device against output voltage spikes
(*) Closed loop gain must be higher than 24dB
7/12
TDA2030
SINGLE SUPPLY APPLICATION
Recomm.
Component
Larger than
recommended value
Smaller than
recommended value
Purpose
value
R1
R2
R3
R4
Closed loop gain
setting
Increase of gain
Decrease of gain (*)
Increase of gain
150 k
Ω
Closed loop gain
setting
Decrease of gain (*)
4.7 k
Ω
Non inverting input
biasing
Increase of input
impedance
Decrease of input
impedance
100 k
Ω
Frequency stability
Danger of osccilat. at
high frequencies
with induct. loads
1
Ω
RA/RB
C1
Non inverting input Biasing
Power Consumption
100 k
1 F
Ω
Input DC
decoupling
Increase of low
frequencies cutoff
µ
C2
C3
C5
Inverting DC
decoupling
Increase of low
frequencies cutoff
22 F
µ
Supply voltage
bypass
Danger of
oscillation
0.1 F
µ
Supply voltage
bypass
Danger of
oscillation
100 F
µ
C7
C8
Frequency stability
Danger of oscillation
Larger bandwidth
0.22 F
µ
1
Upper frequency
cutoff
Smaller bandwidth
2
π
B R1
D1, D2
1N4001
To protect the device against output voltage spikes
(*) Closed loop gain must be higher than 24dB
8/12
TDA2030
SHORT CIRCUIT PROTECTION
The TDA2030 has an original circuit which limits the
current of the output transistors. Fig. 18 shows that
the maximum output current is a function of the
collector emitter voltage; hence the output transis-
tors work within their safe operating area (Fig. 2).
This function can therefore be considered as being
peak power limiting rather than simple current lim-
iting.
It reduces the possibility that the device gets dam-
aged during an accidental short circuit from AC
output to ground.
Figure 19. Safe operating area and
collector characteristics of the
protected power transistor
Figure 18. Maximum
output current vs.
voltage [VCEsat] across
each output transistor
THERMAL SHUT-DOWN
The presence of a thermal limiting circuit offers the
following advantages:
1. An overload on the output (even if it is perma-
nent), or an above limitambient temperature can
be easily supported since the Tj cannot be
higher than 150°C.
junction temperature increases up to 150°C, the
thermal shut-down simply reduces the power
dissipation at the current consumption.
The maximum allowable power dissipation de-
pends upon the size of the external heatsink (i.e. its
thermal resistance); fig. 22 shows this dissipable
power as a function of ambient temperature for
different thermal resistance.
2. The heatsink can have a smaller factor of safety
compared with that of a conventional circuit.
There is no possibility of device damage due to
high junction temperature. If for any reason, the
9/12
TDA2030
Figure 20. Output power and
drain current vs. case
temperature (RL = 4Ω)
Figure 21. Output power and
drain current vs. case
temperature (RL = 8Ω)
Figure
allowable power dissipation
vs. ambient temperature
22.
Maximum
Dimension : suggestion.
Figure 23. Example of heat-sink
The following table shows the length that
the heatsink in fig. 23 must have for several
values of Ptot and Rth.
Ptot (W)
12
60
8
6
Length of heatsink
40
30
(mm)
Rth of heatsink
4.2
6.2
8.3
( C/W)
°
10/12
TDA2030
PENTAWATT PACKAGE MECHANICAL DATA
mm
inch
TYP.
DIM.
MIN.
TYP.
MAX.
4.8
MIN.
MAX.
0.189
0.054
0.110
0.053
0.022
0.047
0.041
0.055
0.142
0.276
0.409
0.409
0.715
0.628
0.850
0.894
0.051
0.118
0.622
0.260
A
C
1.37
2.8
D
2.4
1.2
0.35
0.76
0.8
1
0.094
0.047
0.014
0.030
0.031
0.039
0.126
0.260
D1
E
1.35
0.55
1.19
1.05
1.4
E1
F
F1
G
3.2
6.6
3.4
6.8
3.6
0.134
0.268
G1
H2
H3
L
7
10.4
10.4
18.15
15.95
21.6
22.7
1.29
3
10.05
17.55
15.55
21.2
0.396
0.691
0.612
0.831
0.878
17.85
15.75
21.4
0.703
0.620
0.843
0.886
L1
L2
L3
L4
L5
L6
L7
L9
M
22.3
22.5
2.6
15.1
6
0.102
0.594
0.236
15.8
6.6
0.2
4.5
4
0.008
0.177
0.157
4.23
3.75
4.75
4.25
0.167
0.148
0.187
0.167
M1
V4
Dia
40° (typ.)
3.65
3.85
0.144
0.152
L
L1
L8
V3
R
V
V
E
V
V
R
V1
M1
M
A
R
B
D
C
D1
V4
L2
L3
H2
L5
F
E1
E
V4
H3
G G1
H1
Dia.
F
F1
L7
H2
V4
L9
L6
RESIN BETWEEN
LEADS
11/12
TDA2030
Information furnished is believed to be accurate and reliable. However, STMicroelectronics assumes no responsibility for the consequences of
use of such information nor for any infringement of patents or other rights of third parties which may result from its use. No license is granted
by implication or otherwise under any patent or patent rights of STMicroelectronics. Specification mentioned in this publication are subject to
change without notice. This publication supersedes and replaces all information previously supplied. STMicroelectronics products are not
authorized for use as critical components in life support devices or systems without express written approval of STMicroelectronics.
The ST logo is a registered trademark of STMicroelectronics
© 1998 STMicroelectronics – Printed in Italy – All Rights Reserved
STMicroelectronics GROUP OF COMPANIES
Australia - Brazil - Canada - China - France - Germany - Italy - Japan - Korea - Malaysia - Malta - Mexico - Morocco - The Netherlands -
Singapore - Spain - Sweden - Switzerland - Taiwan - Thailand - United Kingdom - U.S.A.
12/12
UTCTDA2030 LINEAR INTEGRATED CIRCUIT
14W HI-FI AUDIO AMPLIFIER
DESCRIPTION
The UTC TDA2030 is a monolithic audio power amplifier
1
integrated circuit.
TO-220B
FEATURES
*Very low external component required.
*High current output and high operating voltage.
*Low harmonic and crossover distortion.
1
*Built-in Over temperature protection.
*Short circuit protection between all pins.
*Safety Operating Area for output transistors.
TO-220-5
PIN CONFIGURATIONS
1
2
3
4
5
Non inverting input
Inverting input
-VS
Output
+VS
ABSOLUTE MAXIMUM RATINGS(Ta=25°C)
PARAMETER
Supply Voltage
SYMBOL
VALUE
+-18
Vs
UNIT
V
V
Vs
Vi
Input Voltage
Differential Input Voltage
Peak Output Current(internally limited)
Total Power Dissipation at Tcase=90°C
Storage Temperature
Vdi
Io
Ptot
Tstg
Tj
+-15
3.5
20
-40~+150
-40~+150
V
A
W
°C
°C
Junction Temperature
ELECTRICAL CHARACTERISTICS(Refer to the test circuit, Vs =+-16V,Ta=25°C)
PARAMETER
Supply Voltage
Quiescent Drain
Current
SYMBOL
TEST CONDITIONS
MIN
+-6
TYP
MAX
+-18
60
UNIT
V
mA
Vs
Id
40
Input Bias Current
Input Offset Voltage
Input Offset Current
Ib
Vos
Ios
0.2
+-2
+-20
2
µA
MV
NA
Vs=+-18v
+-20
+-200
UTC UNISONIC TECHNOLOGIES CO., LTD.
1
QW-R107-004,B
UTCTDA2030 LINEAR INTEGRATED CIRCUIT
(Continued)
d=0.5%,Gv=30dB
f=40 to 15,000Hz
Output Power
Po
RL=4Ω
RL=8Ω
12
8
14
9
W
W
d=10%,Gv=30dB
f=1KHz
18
W
RL=4Ω
RL=8Ω
Po=12W,RL=4Ω, Gv=30dB
11
10~140,000
90
W
Hz
dB
Power Bandwidth
Open Loop Voltage
Gain
B
Gvo
Closed Loop
Voltage Gain
Distortion
Gvc
d
f=1kHz
29.5
30
0.2
0.1
30 .5
0.5
dB
%
Po=0.1 to 12W,RL=4Ω
f=40 to 15,000Hz, Gv=30dB
Po=0.1 to 8W,RL=8Ω
f=40 to 15,000Hz, Gv=30dB
B= 22Hz to 22kHz
0.5
%
Input Noise Voltage
Input Noise Current
Input
Resistance(pin 1)
Supply Voltage
Rejection
eN
iN
Ri
3
80
5
10
200
µV
pA
MΩ
B= 22Hz to 22kHz
0.5
40
SVR
RL=4Ω,Gv=30dB
Rg=22kΩ,fripple=100Hz,
Vripple=0.5Veff
50
dB
Thermal
Tj
145
°C
Shut-Down
Junction
Temperature
UTC UNISONIC TECHNOLOGIES CO., LTD.
2
QW-R107-004,B
UTCTDA2030 LINEAR INTEGRATED CIRCUIT
TEST CIRCUIT
+Vs
C5
100
C3
µ
F
100nF
C1
D1
1
µ
F
Vi
1N4001
1
2
5
3
R3
22k
UTC
4
Ω
TDA2030
R4
C8
R5
1Ω
RL
R3
R1
22k
D1
1N4001
680
Ω
Ω
C2
C6
C4
C7
22
µ
F
100
µ
F
100nF 220nF
-Vs
APPLICATION CIRCUIT
+Vs
C5
220
C3
100nF
D1
µ
F
C1
1 µF
Vi
1N4001
1
2
5
3
R3
22k
UTC
TDA2030
4
Ω
R4
1Ω
R1
13k
Ω
RL
R3
680Ω
D1
1N4001
C2
µ
C6
C4 C7
100nF 220nF
22
F
100
µ
F
-Vs
UTC UNISONIC TECHNOLOGIES CO., LTD.
3
QW-R107-004,B
UTCTDA2030 LINEAR INTEGRATED CIRCUIT
TYPICAL PERFORMANCE CHARACTERISTICS
Fig.2 Open loop frequency
Fig.3 Output power vs. Supply
response
voltage
140
100
Po 24
(W)
180
90
Gv
(dB)
Gv=26dB
d=0.5%
Phase
Gain
20
f=40 to 15kHz
RL=4
Ω
60
20
0
16
12
RL=8
Ω
-20
-60
8
4
1
2
3
4
5
6
7
10
24
28
32
36
40
44
10
10
10
10
10
10
Frequency (Hz)
Vs (V)
Fig.4 Total harmonic distortion
vs. output power
Fig.5 Two tone CCIF
intermodulation distortion
Po (W)
2
2
d
10
10
d
( % )
( % )
1
1
10
10
Gv=26dB
Vs=32V
Po=4W
0
0
10
10
RL=4
Ω
Vs=38V
Gv=26dB
Order (2f1-f2)
Order (2f2-f1)
RL=8
Ω
f=15kHz
f=1kHz
-1
10
-1
10
Vs=32V
RL=4
Ω
-2
10
-2
10
-2
10
-1
10
0
1
2
10
1
10
2
3
4
5
10
10
10
10
10 Po (W)
Freq1u0ency (Hz)
Fig.7 Maximum allowable power
dissipation vs. ambient
temperture
Fig.6 Large signal frequency
response
30
Vo
Ptot30
(W)
Vs=+-15V
RL=8
(Vp-p)
Ω
25
25
Vs=+-15V
RL=4
20
15
Ω
20
15
h
e
a
t
s
R
i
n
t
h
k
=
h
4
a
°
v
C
i
n
/
W
g
10
5
10
5
1
2
3
4
-50
0
50
100
150
200
10
10
10
Frequency (kHz) 10
Tamb (°C)
UTC UNISONIC TECHNOLOGIES CO., LTD.
4
QW-R107-004,B
UTCTDA2030 LINEAR INTEGRATED CIRCUIT
+Vs
C5
220
µ
F
R1
R6
1.5
C1
2.2
BD908
/40V
56k
Ω
Ω
µ
F
Vi
1
2
C8
5
3
2200
µ
F
R3
56k
UTC
4
Ω
TDA2030
R2
R8
56k
Ω
1Ω
R5
BD907
R4
3.3k
30k
Ω
Ω
R7
1.5
C4
10
C7
0.22
Ω
µ
F
µ
F
Fig. 8 Single supply high power amplifier(UTC TDA2030+BD908/BD907)
TYPICAL PERFORMANCE OF THE CIRCUIT OF FIG. 8
PARAMETER
Supply Voltage
Quiescent Drain
Current
SYMBOL
TEST CONDITIONS
MIN
TYP
36
50
MAX
44
UNIT
Vs
Id
V
Vs=36V
mA
d=0.5%,RL=4Ω
f=40Hz to 15kHz,Vs=39V
d=0.5%,RL=4Ω
35
28
44
35
Output Power
Po
f=40Hz to 15kHz,Vs=36V
W
d=0.5%,f=1kHz,
RL=4Ω,Vs=39V
d=0.5%,RL=4Ω
f=1kHz,Vs=36V
f=1kHz
Voltage Gain
Slew Rate
Total Harmonic
Distortion
Gv
SR
d
19.5
20
8
0.02
0.05
890
20.5
dB
V/µsec
%
%
mV
Po=20W,f=1kHz
Po=20W,f=40Hz to 15kHz
Gv=20dB,Po=20W,
f=1kHz,RL=4Ω
Input Sensitivity
Vi
RL=4Ω,Rg=10kΩ
Signal to Noise
Ratio
S/N
B=curve A,Po=25W
RL=4Ω,Rg=10kΩ
108
100
dB
B=curve A,Po=25W
UTC UNISONIC TECHNOLOGIES CO., LTD.
5
QW-R107-004,B
UTCTDA2030 LINEAR INTEGRATED CIRCUIT
TYPICAL PERFORMANCE CHARACTERISTICS
Fig. 10 Output power vs. supply
Fig. 11 Total harmonic distortion
voltage
vs. output power
Po
d
(W)
(%)
Vs=36V
45
RL=4
Ω
Gv=20dB
0
10
35
25
15
-1
10
f=15kHz
f=1kHz
-2
5
10
40
24
28
32
34
36
-1
10
0
1
Po
Vs
10
10
(W)
(V)
Fig. 12 Output power vs.
Input level
Fig. 13 Power dissipation vs.
output power
Ptot
(W)
Po
(W)
20
20
Complete
Amplifier
Gv=26dB
15
10
15
10
Gv=20dB
BD908/
BD907
UTC
TDA2030
5
0
5
0
Vi
(mV)
Po
100
250
400
550
700
0
8
16
24
32
(W)
UTC UNISONIC TECHNOLOGIES CO., LTD.
6
QW-R107-004,B
UTCTDA2030 LINEAR INTEGRATED CIRCUIT
+Vs
C5
100
C3
µ
F
100nF
C1
D1
1
µ
F
Vi
1N4001
1
2
5
3
R3
22k
UTC
4
Ω
TDA2030
R4
C8
R5
1Ω
RL
R3
R1
22k
D2
680
Ω
Ω
1N4001
C2
C6
C4
C7
22
µ
F
100
µ
F
100nF 220nF
-Vs
Fig. 14 Typical amplifier with split power supply
Vs+
C6
100 µF
C7
100nF
C1
220
µ
F
1
2
5
UTC TDA2030
IN
4
R1
22k
Ω
3
R3
22kΩ
R8
1Ω
C4
22 µ
F
RL
8Ω
R4
680
Ω
R7
22k
Ω
1
2
5
UTC TDA2030
R2
22k
4
Ω
3
R5
22kΩ
R9
1Ω
Vs-
C5
22 µ
F
R6
680
C2
100
C3
100nF
Ω
µ
F
Fig. 16 Bridge amplifier with split power supply(Po=34W,Vs+=16V,Vs-=16V)
UTC UNISONIC TECHNOLOGIES CO., LTD.
7
QW-R107-004,B
UTCTDA2030 LINEAR INTEGRATED CIRCUIT
MULTIWAY SPEAKER SYSTEMS AND ACTIVE BOXES
Multiway loudspeaker systems provide the best possible acoustic performance since each loudspeaker is
specially designed and optimized to handle a limited range of frequencies. Commonly, these loudspeaker systems
divide the audio spectrum two or three bands.
To maintain a flat frequency response over the Hi-Fi audio range the bands cobered by each loudspeaker must
overlap slightly. Imbalance between the loudspeakers produces unacceptable results therefore it is important to
ensure that each unit generates the correct amount of acoustic energy for its segments of the audio spectrum. In this
respect it is also important to know the energy distribution of the music spectrum to determine the cutoff frequencies
of the crossover filters(see Fig. 18).As an example,1 100W three-way system with crossover frequencies of 400Hz
and 3khz would require 50W for the woofer,35W for the midrange unit and 15W for the tweeter.
Both active and passive filters can be used for crossovers but active filters cost significantly less than a good
passive filter using aircored inductors and non-electrolytic capacitors. In addition active filters do not suffer from the
typical defects of passive filters:
--Power less;
--Increased impedance seen by the loudspeaker(lower damping)
--Difficulty of precise design due to variable loudspeaker impedance.
Obviously, active crossovers can only be used if a power amplifier is provide for each drive unit. This makes it
particularly interesting and economically sound to use monolithic power amplifiers.
In some applications complex filters are not relay necessary and simple RC low-pass and high-pass
networks(6dB/octave) can be recommended.
The result obtained are excellent because this is the best type of audio filter and the only one free from phase and
transient distortion.
The rather poor out of band attenuation of single RC filters means that the loudspeaker must operate linearly well
beyond the crossover frequency to avoid distortion.
A more effective solution, named "Active power Filter" by SGS is shown in Fig. 19.
The proposed circuit can realize combined power amplifiers and 12dB/octave or 18dB octave high-pass or
low-pass filters.
In proactive, at the input pins amplifier two equal and in-phase voltages are available, as required for the active
filter operations.
The impedance at the Pin(-) is of the order of 100Ω,while that of the Pin (+) is very high, which is also what was
wanted.
Fig. 18 Power distribution vs.
frequency
Fig. 19 Active power filter
100
80
Vs+
C1 C2 C3
IEC/DIN NOISE
SPECTRUM
FOR SPEAKER
TESTING
Morden
Music
RL
Spectrum
60
R1 R2 R3
3.3k
Ω
Vs-
40
20
0
100
Ω
1
2
3
4
5
10
10
10
10
10
UTC UNISONIC TECHNOLOGIES CO., LTD.
8
QW-R107-004,B
UTCTDA2030 LINEAR INTEGRATED CIRCUIT
The components values calculated for fc=900Hz using a Bessel 3rd Sallen and Key structure are:
C1=C2=C3=22nF,R1=8.2KΩ,R2=5.6KΩ,R3=33KΩ.
Using this type of crossover filter, a complete 3-way 60W active loudspeaker system is shown in Fig. 20.
It employs 2nd order Buttherworth filter with the crossover frequencies equal to 300Hz and 3kHz.
The midrange section consistors of two filters a high pass circuit followed by a low pass network. With Vs=36V the
output power delivered to the woofer is 25W at d=0.06%( 30W at d=0.5%).The power delivered to the midrange and
the tweeter can be optimized in the design phase taking in account the loudspeaker efficiency and
impedance(RL=4Ω to 8Ω).
It is quite common that midrange and tweeter speakers have an efficiency 3dB higher than woofers.
Vs+
Low-pass
300Hz
1 µF
IN
22k
Ω
22kΩ
BD908
BD907
1
2
5
UTC
4
TDA2030
2200 µF
3
100 µF
Woofer
Vs+
Band-pass
300Hz to 3kHz
0.22 µF
1N4001
0.1
µF
0.1 µF
22k
Ω
22k
Ω
1
2
5
220 µF
UTC
4
TDA2030
3
1N4001
100 µF
2.2k
Ω
Midrange
Vs+
0.22 µF
High-pass
3kHz
1N4001
Vs+
0.1
µF
0.1 µF
1
2
5
100 µF
UTC
4
TDA2030
3
1N4001
47 µF
2.2k
Ω
Tweeter
High-pass
3kHz
UTC UNISONIC TECHNOLOGIES CO., LTD.
9
QW-R107-004,B
UTCTDA2030 LINEAR INTEGRATED CIRCUIT
MUSICAL INSTRUMENTS AMPLIFIERS
Another important field of application for active system is music.
In this area the use of several medium power amplifiers is more convenient than a single high power amplifier, and it
is also more reliable. A typical example(see Fig. 21) consist of four amplifiers each driving a low-cost, 12 inch
loudspeaker. This application can supply 80 to 160W rms.
TRANSIENT INTER-MODULATION DISTORTION(TIM)
Transient inter-modulation distortion is an unfortunate phenomena associated with negative-feedback amplifiers.
When a feedback amplifier receives an input signal which rises very steeply, i.e. contains high-frequency
components, the feedback can arrive too late so that the amplifiers overloads and a burst of inter-modulation
distortion will be produced as in Fig.22.Since transients occur frequently in music this obviously a problem for the
designed of audio amplifiers. Unfortunately, heavy negative feedback is frequency used to reduce the total harmonic
distortion of an amplifier, which tends to aggravate the transient inter-modulation(TIM situation.)The best known
Fig.21 High power active box for musical
instrument
Fig.22 Overshoot phenomenon in
feedback amplifiers
FEEDBACK
PATH
20 to 40W
Amplifier
汕
V4
V3
INPUT
OUTPUT
PRE
POWER
AMPLIFIER
AMPLIFIER
V1
V2
V4
20 to 40W
Amplifier
V1
20 to 40W
Amplifier
V2
20 to 40W
Amplifier
V3
V4
method for the measurement of TIM consists of feeding sine waves superimposed onto square wavers, into the
amplifier under test. The output spectrum is then examined using a spectrum analyzer and compared to the input.
This method suffers from serious disadvantages: the accuracy is limited, the measurement is a tatter delicate
operation and an expensive spectrum analyzer is essential. A new approach (see Technical Note 143(Applied by
SGS to monolithic amplifiers measurement is fast cheap, it requires nothing more sophisticated than an
oscilloscope-and sensitive-and it can be used down to the values as low as 0.002% in high power amplifiers.
The "inverting-sawtooth" method of measurement is based on the response of an amplifier to a 20KHz saw-tooth
wave-form. The amplifier has no difficulty following the slow ramp but it cannot follow the fast edge. The output will
follow the upper line in Fig.23 cutting of the shade area and thus increasing the mean level. If this output signal is
filtered to remove the saw-tooth, direct voltage remains which indicates the amount of TIM distortion, although it is
difficult to measure because it is indistinguishable from the DC offset of the amplifier. This problem is neatly avoided
in the IS-TIM method by periodically inverting the saw-tooth wave-form at a low audio frequency as shown in
Fig.24.Inthe case of the saw-tooth in Fig. 25 the means level was increased by the TIM distortion, for a saw-tooth in
the other direction the opposite is true.
UTC UNISONIC TECHNOLOGIES CO., LTD.
10
QW-R107-004,B
UTCTDA2030 LINEAR INTEGRATED CIRCUIT
Input
SR(V/µs)
Signal
m2
m1
Filtered
Output
Siganal
Fig.23 20kHz sawtooth waveform
Fig.24 Inverting sawtooth waveform
The result is an AC signal at the output whole peak-to-peak value is the TIM voltage, which can be measured
easily with an oscilloscope. If the peak-topeak value of the signal and the peak-to-peak of the inverting sawtooth are
measured, the TIM can be found very simply from:
VOUT
TIM =
* 100
Vsawtooth
Fig. 25 TIM distortion Vs.
Output Power
Fig. 26 TIM design
diagram(fc=30kHz)
1
2
10
10
SR(V/
米
s)
TIM(%)
RC Filter fc=30kHz
UTC2030A
BD908/907
Gv=26dB
Vs=36V
0
1
10
10
RL=4Ω
-1
0
RC Filter fc=30kHz
10
10
-2
-1
10
10
-1
0
1
2
-1
10
0
1
2
10
10
10
10
10
10
10
Po(W)
Vo(Vp-p)
In Fig.25 The experimental results are shown for the 30W amplifier using the UTC2030A as a driver and a
low-cost complementary pair. A simple RC filter on the input of the amplifier to limit the maximum signal slope(SS) is
an effective way to reduce TIM.
The Diagram of Fig.26 originated by SGS can be used to find the Slew-Rate(SR) required for a given output power
or voltage and a TIM design target.
For example if an anti-TIM filter with a cutoff at 30kHz is used and the max. Peak to peak output voltage is 20V then,
referring to the diagram, a Slew-Rate of 6V/µs is necessary for 0.1% TIM.
As shown Slew-Rates of above 10V/µs do not contribute to a further reduction in TIM.
Slew-Rates of 100V/µs are not only useless but also a disadvantage in hi-fi audio amplifiers because they tend to
turn the amplifier into a radio receiver.
POWER SUPPLY
Using monolithic audio amplifier with non regulated supply correctly. In any working case it must provide a supply
voltage less than the maximum value fixed by the IC breakdown voltage.
UTC UNISONIC TECHNOLOGIES CO., LTD.
11
QW-R107-004,B
UTCTDA2030 LINEAR INTEGRATED CIRCUIT
It is essential to take into account all the working conditions, in particular mains fluctuations and supply voltage
variations with and without load. The UTC2030(Vsmax=44V) is particularly suitable for substitution of the standard
IC power amplifiers(with Vsmax=36V) for more reliable applications.
An example, using a simple full-wave rectifier followed by a capacitor filter, is shown in the table and in the diagram
of Fig.27.
A regulated supply is not usually used for the power output stages because of its dimensioning must be done
taking into account the power to supply in signal peaks. They are not only a small percentage of the total music
signal, with consequently large overdimensioning of the circuit.
Even if with a regulated supply higher output power can be obtained(Vs is constant in all working conditions),the
additional cost and power dissipation do not usually justify its use. using non-regulated supplies, there are fewer
designee restriction. In fact, when signal peaks are present, the capacitor filter acts as a flywheel supplying the
required energy.
In average conditions, the continuous power supplied is lower. The music power/continuous power ratio is greater
in case than for the case of regulated supplied, with space saving and cost reduction.
Fig.27 DC characteristics of
50W non-regulated supply
Ripple
(Vp-p)
Vo(V)
36
34
32
30
Ripple
4
2
0
220V
Vo
3300 F
µ
Vout
28
0
0.4
0.8
1.2
1.6
2.0
Io(A)
Mains(220V)
Secondary Voltage
DC Output Voltage(Vo)
Io=0
Io=0.1A
42V
40.3V
38.5V
35V
31.5V
29.8V
28V
Io=1A
37.5V
35.8V
34.2V
31V
27.8V
26V
+20%
+15%
+10%
—
28.8V
27.6V
26.4V
24V
21.6V
20.4V
19.2V
43.2V
41.4V
39.6V
36.2V
32.4V
30.6V
28.8V
-10%
-15%
-20%
24.3
UTC UNISONIC TECHNOLOGIES CO., LTD.
12
QW-R107-004,B
UTCTDA2030 LINEAR INTEGRATED CIRCUIT
SHORT CIRCUIT PROTECTION
The UTC TDA2030 has an original circuit which limits the current of the output transistors. This function can be
considered as being peak power limiting rather than simple current limiting. It reduces the possibility that the device
gets damaged during an accidental short circuit from AC output to Ground.
THERMAL SHUT-DOWN
The presence of a thermal limiting circuit offers the following advantages:
1).An overload on the output (even if it is permanent),or an above limit ambient temperature can be easily supported
since the Tj can not be higher than 150°C
2).The heatsink can have a smaller factor of safety compared with that of a congenital circuit, There is no possibility
of device damage due to high junction temperature increase up to 150, the thermal shut-down simply reduces the
power dissipation and the current consumption.
APPLICATION SUGGESTION
The recommended values of the components are those shown on application circuit of Fig.14. Different values can
be used. The following table can help the designer.
COMPONENT
RECOMMENDED
VALUE
PURPOSE
LARGE THAN
RECOMMENDED
VALUE
LARGE THAN
RECOMMENDED
VALUE
R1
R2
R3
R4
22KΩ
680Ω
22KΩ
1Ω
Closed loop gaon
setting.
Increase of Gain
Decrease of Gain
Closed loop gaon
Decrease of Gain
Increase of Gain
setting.
Non inverting input
biasing
Frequency stacility
Increase of input
impedance
Danger of oscillation
at high frequencies
with inductive loads.
Decrease of input
impedance
R5
C1
≈3R2
1µF
Upper frequency
cutoff
Input DC decoupling
Poor high frequencies Dange of oscillation
attenuation
Increase of low
frequencies cutoff
C2
22µF
0.1µF
100µF
Inverting DC
decoupling
Increase of low
frequencies cutoff
C3,C4
C5,C6
Supply voltage
Dange of oscillation
bypass
Supply voltage
bypass
Dange of oscillation
C7
C8
0.22µF
≈1/(2π*B*R1)
Frequency stability
Upper frequency
cutoff
Larger bandwidth
Larger bandwidth
smaller bandwidth
D1,D2
1N4001
To protect the device
against output voltage
spikes.
UTC UNISONIC TECHNOLOGIES CO., LTD.
13
QW-R107-004,B
相关型号：
TDA2039A
TDA2039 是一块具有静音和待机功能的8W 单声道或4W 双声道音频功放电路，该电路最适合用在多媒体音响和电视伴音系统。TDA2039A可以根据要求使用立体声和BTL 单声道功能，TDA2039B只能使用BTL 单声道功能。
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