U211B-MFPY [ATMEL]
Analog Circuit;
| 型号： | U211B-MFPY |
| 厂家： | 
ATMEL |
| 描述： | Analog Circuit |
| 文件： | 总29页 (文件大小：1703K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
Features
• Internal Frequency-to-voltage Converter
• Externally Controlled Integrated Amplifier
• Overload Limitation with “Fold Back” Characteristic
• Optimized Soft-start Function
• Tacho Monitoring for Shorted and Open Loop
• Automatic Retriggering Switchable
• Triggering Pulse Typically 155 mA
• Voltage and Current Synchronization
• Internal Supply-voltage Monitoring
• Temperature Reference Source
Product
Description
• Current Requirement ≤ 3 mA
1. Description
The integrated circuit U211B is designed as a phase-control circuit in bipolar technol-
ogy with an internal frequency-to-voltage converter. The device includes an internal
control amplifier which means it can be used for speed-regulated motor applications.
U211B
Amongst others, the device features integrated load limitation, tacho monitoring and
soft-start functions, to realize sophisticated motor control systems.
Figure 1-1. Block Diagram
17(16)
1(1)
5*
4(4)
6(5)
Voltage/current
Automatic
retriggering
Output
pulse
detector
Control
11(10)
10(9)
amplifier
+
-
7(6)
3(3)
Phase-
-VS
Supply
voltage
limitation
control unit
ϕ
2(2)
= f (V12)
GND
16(15)
Reference
voltage
14(13)
Load limitation
speed/time
controlled
Voltage
monitoring
15(14)
Controlled
current sink
Frequency
to voltage
converter
Pulse blocking
tacho
monitoring
18
*
Soft start
-VRef
12(11)
13(12)
9(8)
8(7)
Pin numbers in brackets refer to SO16
Pins 5 and 18 connected internally
*
4752B–INDCO–09/05
2. Pin Configuration
Figure 2-1. Pinning DIP18
Isync
GND
VS
1
2
3
4
5
6
7
8
9
18 PB/TM
17 Vsync
16 VRef
Output
Retr
VRP
15 OVL
U211B
14 Isense
13 Csoft
CP
12 CTR/OPO
11 OP+
10 OP
F/V
CRV
Table 2-1.
Pin Description
Pin
1
Symbol
Isync
Function
Current synchronization
Ground
2
GND
VS
3
Supply voltage
4
Output
Retr
Trigger pulse output
Retrigger programming
Ramp current adjust
Ramp voltage
5
6
VRP
7
CP
8
F/V
Frequency-to-voltage converter
Charge pump
9
CRV
10
11
12
13
14
15
16
17
18
OP-
OP inverting input
OP non-inverting input
Control input/OP output
Soft start
OP+
CTR/OPO
Csoft
Isense
OVL
Load-current sensing
Overload adjust
VRef
Reference voltage
Voltage synchronization
Pulse blocking/tacho monitoring
Vsync
PB/TM
2
U211B
4752B–INDCO–09/05
U211B
Figure 2-2. Pinning SO16
Isync
GND
VS
1
2
3
4
5
6
7
8
16 Vsync
15 VRef
14 OVL
Output
VRP
13 Isense
12 Csoft
U211B
CP
11 CTR/OPO
10 OP+
F/V
CRV
9
OP
Table 2-2.
Pin Description
Pin
1
Symbol
Isync
Function
Current synchronization
Ground
2
GND
VS
3
Supply voltage
4
Output
VRP
Trigger pulse output
Ramp current adjust
Ramp voltage
5
6
CP
7
F/V
Frequency-to-voltage converter
Charge pump
8
CRV
9
OP-
OP inverting input
OP non-inverting input
Control input/OP output
Soft start
10
11
12
13
14
15
16
OP+
CTR/OPO
Csoft
Isense
OVL
VRef
Load-current sensing
Overload adjust
Reference voltage
Voltage synchronization
Vsync
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4752B–INDCO–09/05
3. Mains Supply
The U211B is equipped with voltage limiting and can therefore be supplied directly from the
mains. The supply voltage between pin 2 (+ pol/_|_) and pin 3 builds up across D1 and R1 and
is smoothed by C1. The value of the series resistance can be approximated using:
V
– V
S
M
R
= ---------------------
1
2 I
S
Further information regarding the design of the mains supply can be found in the section
“Design Hints” on page 9. The reference voltage source on pin 16 of typically –8.9V is derived
from the supply voltage and is used for regulation.
Operation using an externally stabilized DC voltage is not recommended.
If the supply cannot be taken directly from the mains because the power dissipation in R1
would be too large, the circuit as shown in Figure 3-1 should be used.
Figure 3-1. Supply Voltage for High Current Requirements
~
24V
~
1
2
3
4
5
+
C1
R1
4. Phase Control
The phase angle of the trigger pulse is derived by comparing the ramp voltage (which is mains
synchronized by the voltage detector) with the set value on the control input pin 12. The slope
of the ramp is determined by C2 and its charging current. The charging current can be varied
using R2 on pin 6. The maximum phase angle αmax can also be adjusted by using R2.
When the potential on pin 7 reaches the nominal value predetermined at pin 12, a trigger
pulse is generated whose width tp is determined by the value of C2 (the value of C2 and hence
the pulse width can be evaluated by assuming 8 µs/nF). At the same time, a latch is set, so
that as long as the automatic retriggering has not been activated, no more pulses can be gen-
erated in that half cycle.
The current sensor on pin 1 ensures that, for operations with inductive loads, no pulse will be
generated in a new half cycle as long as a current from the previous half cycle is still flowing in
the opposite direction to the supply voltage at that instant. This makes sure that “gaps” in the
load current are prevented.
The control signal on pin 12 can be in the range of 0V to –7V (reference point pin 2).
If V12 = –7V, the phase angle is at maximum (αmax), i.e., the current flow angle, is at minimum.
The phase angle is minimum (αmin) when V12 = V2.
4
U211B
4752B–INDCO–09/05
U211B
5. Voltage Monitoring
As the voltage is built up, uncontrolled output pulses are avoided by internal voltage surveil-
lance. At the same time, all latches in the circuit (phase control, load limit regulation, soft start)
are reset and the soft-start capacitor is short circuited. Used with a switching hysteresis of
300 mV, this system guarantees defined start-up behavior each time the supply voltage is
switched on or after short interruptions of the mains supply.
6. Soft Start
As soon as the supply voltage builds up (t1), the integrated soft start is initiated. Figure 6-1
shows the behavior of the voltage across the soft-start capacitor, which is identical with the
voltage on the phase-control input on pin 12. This behavior guarantees a gentle start-up for
the motor and automatically ensures the optimum run-up time.
Figure 6-1. Soft Start
VC3
V12
V0
t
t1
t2
t3
ttot
t1 = Build-up of supply voltage
t2 = Charging of C3 to starting voltage
t1 + t2 Dead time
t3 = Run-up time
ttot = Total start-up time to required speed
C3 is first charged up to the starting voltage V0 with a current of typically 45 µA (t2). By reducing
the charging current to approximately 4 µA, the slope of the charging function is also substan-
tially reduced, so that the rotational speed of the motor only slowly increases. The charging
current then increases as the voltage across C3 increases, resulting in a progressively rising
charging function which accelerates the motor more and more with increasing rotational
speed. The charging function determines the acceleration up to the set point. The charging
current can have a maximum value of 55 µA.
5
4752B–INDCO–09/05
7. Frequency-to-voltage Converter
The internal frequency-to-voltage converter (f/V converter) generates a DC signal on pin 10
which is proportional to the rotational speed, using an AC signal from a tacho generator or a
light beam whose frequency is in turn dependent on the rotational speed. The high-impedance
input pin 8 compares the tacho voltage to a switch-on threshold of typically –100 mV. The
switch-off threshold is –50 mV. The hysteresis guarantees very reliable operation even when
relatively simple tacho generators are used.
The tacho frequency is given by:
n
60
------
f =
× p (Hz)
where:
n
p
= Revolutions per minute
= Number of pulses per revolution
The converter is based on the charge pumping principle. With each negative half-wave of the
input signal, a quantity of charge determined by C5 is internally amplified and then integrated
by C6 at the converter output on pin 10. The conversion constant is determined by C5, its
charge transfer voltage of Vch, R6 (pin 10) and the internally adjusted charge transfer gain.
I
10
------
G
= 8.3
i
I
9
k = Gi × C5 × R6 × Vch
The analog output voltage is given by
VO = k × f
The values of C5 and C6 must be such that for the highest possible input frequency, the maxi-
mum output voltage VO does not exceed 6V. While C5 is charging up, the Ri on pin 9 is
approximately 6.7 kΩ. To obtain good linearity of the f/V converter, the time constant resulting
from Ri and C5 should be considerably less (1/5) than the time span of the negative half-cycle
for the highest possible input frequency. The amount of remaining ripple on the output voltage
on pin 10 is dependent on C5, C6 and the internal charge amplification.
G × V × C
5
i
ch
ΔV = ------------------------------------
O
C
6
The ripple ΔVO can be reduced by using larger values of C6. However, the increasing speed
will then also be reduced.
The value of this capacitor should be chosen to fit the particular control loop where it is going
to be used.
6
U211B
4752B–INDCO–09/05
U211B
7.1
Pulse Blocking
The output of pulses can be blocked by using pin 18 (standby operation) and the system reset
via the voltage monitor if V18 ≥ –1.25V. After cycling through the switching point hysteresis, the
output is released when V18 ≤ –1.5V, followed by a soft start such as after turn-on.
Monitoring of the rotation can be carried out by connecting an RC network to pin 18. In the
event of a short or open circuit, the triac triggering pulses are cut off by the time delay which is
determined by R and C. The capacitor C is discharged via an internal resistance Ri = 2 kΩwith
each charge transfer process of the f/V converter. If there are no more charge transfer pro-
cesses, C is charged up via R until the switch-off threshold is exceeded and the triac triggering
pulses are cut off. For operation without trigger pulse blocking or monitoring of the rotation,
pin 18 and pin 16 must be connected together.
Figure 7-1. Operation Delay
+
C = 1 µF
10V
18
17
16
15
R = 1 M
Ω
1
2
3
4
7.2
Control Amplifier
The integrated control amplifier (see Figure 10-17 on page 21) with differential input compares
the set value (pin 11) with the instantaneous value on pin 10, and generates a regulating volt-
age on the output pin 12 (together with the external circuitry on pin 12). This pin always tries to
keep the actual voltage at the value of the set voltages. The amplifier has a transmittance of
typically 1000 µA/V and a bipolar current source output on pin 12 which operates with typically
±110 µA. The amplification and frequency response are determined by R7, C7, C8 and R11
(can be left out). For open-loop operation, C4, C5, R6, R7, C7, C8 and R11 can be omitted.
Pin 10 should be connected with pin 12 and pin 8 with pin 2. The phase angle of the triggering
pulse can be adjusted by using the voltage on pin 11. An internal limitation circuit prevents the
voltage on pin 12 from becoming more negative than V16 + 1V.
7.3
Load Limitation
The load limitation, with standard circuitry, provides full protection against overloading of the
motor. The function of load limiting takes account of the fact that motors operating at higher
speeds can safely withstand larger power dissipations than at lower speeds due to the
increased action of the cooling fan. Similarly, considerations have been made for short-term
overloads for the motor which are, in practice, often required. These behaviors are not damag-
ing and can be tolerated.
7
4752B–INDCO–09/05
In each positive half-cycle, the circuit measures, via R10, the load current on pin 14 as a poten-
tial drop across R8 and produces a current proportional to the voltage on pin 14. This current is
available on pin 15 and is integrated by C9. If, following high-current amplitudes or a large
phase angle for current flow, the voltage on C9 exceeds an internally set threshold of approxi-
mately 7.3V (reference voltage pin 16), a latch is set and load limiting is turned on. A current
source (sink) controlled by the control voltage on pin 15 now draws current from pin 12 and
lowers the control voltage on pin 12 so that the phase angle α is increased to αmax
.
The simultaneous reduction of the phase angle during which current flows causes firstly a
reduction of the rotational speed of the motor which can even drop to zero if the angular
momentum of the motor is excessively large, and secondly a reduction of the potential on C9
which in turn reduces the influence of the current sink on pin 12. The control voltage can then
increase again and bring down the phase angle. This cycle of action sets up a “balanced con-
dition” between the “current integral” on pin 15 and the control voltage on pin 12.
Apart from the amplitude of the load current and the time during which current flows, the
potential on pin 12 and hence the rotational speed also affects the function of load limiting. A
current proportional to the potential on pin 10 gives rise to a voltage drop across R10, via
pin 14, so that the current measured on pin 14 is smaller than the actual current through R8.
This means that higher rotational speeds and higher current amplitudes lead to the same cur-
rent integral. Therefore, at higher speeds, the power dissipation must be greater than that at
lower speeds before the internal threshold voltage on pin 15 is exceeded. The effect of speed
on the maximum power is determined by the resistor R10 and can therefore be adjusted to suit
each individual application.
If, after load limiting has been turned on, the momentum of the load sinks below the
“o-momentum” set using R10, V15 will be reduced. V12 can then increase again so that the
phase angle is reduced. A smaller phase angel corresponds to a larger momentum of the
motor and hence the motor runs up, as long as this is allowed by the load momentum. For an
already rotating machine, the effect of rotation on the measured “current integral” ensures that
the power dissipation is able to increase with the rotational speed. The result is a current-con-
trolled acceleration run-up which ends in a small peak of acceleration when the set point is
reached. The load limiting latch is simultaneously reset. Then the speed of the motor is under
control again and is capable of carrying its full load. The above mentioned peak of accelera-
tion depends upon the ripple of actual speed voltage. A large amount of ripple also leads to a
large peak of acceleration.
The measuring resistor R8 should have a value which ensures that the amplitude of the volt-
age across it does not exceed 600 mV.
8
U211B
4752B–INDCO–09/05
U211B
7.4
Design Hints
Practical trials are normally needed for the exact determination of the values of the relevant
components for load limiting. To make this evaluation easier, the following table shows the
effect of the circuitry on the important parameters for load limiting and summarizes the general
tendencies.
Table 7-1.
Load Limiting Parameters
Component
Component
R9 Increasing
Decreases
Decreases
n.e.
Component
C9 Increasing
n.e.
Parameters
R10 Increasing
Increases
Increases
Increases
n.e.
Pmax
Pmin
Pmax/min
td
n.e.
n.e.
Increases
Increases
Increases
Increases
tr
n.e.
Pmax
Pmin
td
- Maximum continuous power dissipationP1 = f(n) n ≠ 0
- Power dissipation with no rotation
- Operation delay time
- Recovery time
P1 = f(n) n = 0
tr
n.e.
- No effect
7.5
7.6
Pulse-output Stage
The pulse-output stage is short-circuit protected and can typically deliver currents of 125 mA.
For the design of smaller triggering currents, the function IGT = f(RGT) can be taken from Figure
10-12 on page 18.
Automatic Retriggering
The variable automatic retriggering prevents half cycles without current flow, even if the triac
has been turned off earlier, e.g., due to a collector which is not exactly centered (brush lifter)
or in the event of unsuccessful triggering. If necessary, another triggering pulse is generated
after a time lapse which is determined by the repetition rate set by resistance between pin 5
and pin 3 (R5-3). With the maximum repetition rate (pin 5 directly connected to pin 3), the next
attempt to trigger comes after a pause of 4.5 tp and this is repeated until either the triac fires or
the half cycle finishes. If pin 5 is not connected, only one trigger pulse per half cycle is gener-
ated. Since the value of R5-3 determines the charging current of C2, any repetition rate set
using R5-3 is only valid for a fixed value of C2.
9
4752B–INDCO–09/05
7.7
General Hints and Explanation of Terms
To ensure safe and trouble-free operation, the following points should be taken into consider-
ation when circuits are being constructed or in the design of printed circuit boards.
• The connecting lines from C2 to pin 7 and pin 2 should be as short as possible. The
connection to pin 2 should not carry any additional high current such as the load current.
When selecting C2, a low temperature coefficient is desirable.
• The common (earth) connections of the set-point generator, the tacho generator and the
final interference suppression capacitor C4 of the f/V converter should not carry load
current.
• The tacho generator should be mounted without influence by strong stray fields from the
motor.
• The connections from R10 and C5 should be as short as possible.
To achieve a high noise immunity, a maximum ramp voltage of 6V should be used. The typical
resistance Rϕ can be calculated from Iϕ as follows:
3
T(ms) × 1.13(V) × 10
R (kΩ) = -------------------------------------------------------------
ϕ
C(nF) × 6(V)
T =
Cϕ =
Period duration for mains frequency (10 ms at 50 Hz)
Ramp capacitor, maximum ramp voltage 6 V and constant voltage drop at
Rϕ = 1.13 V
A 10% lower value of Rϕ (under worst case conditions) is recommended.
Figure 7-2. Explanation of Terms in Phase Relationship
V
Mains
Supply
π
/2
π
3/2
π
2π
VGT
Trigger
Pulse
tp
tpp = 4.5 tp
VL
Load
Voltage
ϕ
L
Load
Current
Φ
10
U211B
4752B–INDCO–09/05
U211B
7.8
Design Calculations for Main Supply
The following equations can be used for the evaluation of the series resistor R1 for worst case
conditions:
V
– V
Smax
V
– V
Smin
Mmin
M
-------------------------------------
R
= 0.85
R
= ----------------------------
1min
1max
2 I
2 I
tot
Smax
2
(V
– V
)
Smin
Mmax
P
= ---------------------------------------------
(R1max)
2 R
1
where:
VM
VS
Itot
= Mains voltage
= Supply voltage on pin 3
= Total DC current requirement of the circuit
= IS + Ip + Ix
ISmax
Ip
Ix
= Current requirement of the IC in mA
= Average current requirement of the triggering pulse
= Current requirement of other peripheral components
R1 can be easily evaluated from the Figure 10-14 on page 19, Figure 10-15 on page 19 and
Figure 10-16 on page 20.
11
4752B–INDCO–09/05
8. Absolute Maximum Ratings
Reference point pin 2, unless otherwise specified
Stresses beyond those listed under “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress rating
only and functional operation of the device at these or any other conditions beyond those indicated in the operational sections of this
specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability.
Parameters
Pins
3
Symbol
–IS
Value
30
Unit
mA
mA
mA
mA
mA
mA
Current requirement
t ≤10 µs
3
–is
100
5
Synchronization current
1
IsyncI
IsyncV
±iI
17
1
5
t < 10 µs
35
t < 10 µs
17
±iI
35
f/V Converter
Input current
t < 10 µs
8
8
II
3
mA
mA
±iI
13
Load Limiting
Limiting current,
negative half wave
14
II
5
mA
t < 10 µs
14
14
15
II
35
1
mA
V
±Vi
–VI
Input voltage
|V16| to 0
V
Phase Control
Input voltage
12
12
6
–VI
±II
0 to 7
500
1
V
µA
mA
Input current
–II
Soft Start
Input voltage
13
4
–VI
VR
|V16| to 0
VS to 5
V
V
V
Pulse Output
Reverse voltage
Pulse Blocking
Input voltage
18
–VI
|V16| to 0
Amplifier
Input voltage
11
10
VI
0 to VS
V
V
Pin 9 open
–VI
|V16| to 0
Reference Voltage Source
Output current
16
Io
Tstg
Tj
7.5
mA
°C
°C
°C
Storage temperature range
Junction temperature
Ambient temperature range
–40 to +125
125
Tamb
–10 to +100
12
U211B
4752B–INDCO–09/05
U211B
9. Thermal Resistance
Parameters
Symbol
Value
Unit
Junction ambient
DIP18
SO16 on p.c.
SO16 on ceramic
RthJA
RthJA
RthJA
120
180
100
K/W
K/W
K/W
10. Electrical Characteristics
–VS = 13.0V, Tamb = 25°C, reference point pin 2, unless otherwise specified
Parameters
Test Conditions
Pins
Symbol
Min.
Typ.
Max.
Unit
Supply voltage for mains operation
3
–VS
13.0
VLimit
V
–IS = 4 mA
–IS = 30 mA
14.6
14.7
16.6
16.8
V
V
Supply voltage limitation
DC current requirement
Reference voltage source
3
3
–VS
IS
–VS = 13.0 V
1.2
2.5
8.9
3.0
mA
–IL = 10 µA
–IL = 5 mA
8.6
8.3
9.2
9.1
V
V
16
16
–VRef
–TCVRef
Temperature coefficient
Voltage Monitoring
Turn-on threshold
0.5
mV/K
3
3
–VSON
11.2
9.9
13.0
10.9
V
V
Turn-off threshold
–VSOFF
Phase-control Currents
1
17
±IsyncI
±IsyncV
Synchronization current
Voltage limitation
0.35
1.4
2.0
1.8
mA
V
±IL = 5 mA
1, 17
±VI
1.6
20
Reference Ramp (see Figure 10-1 on page 15)
I7 = f(R6)
R6 = 50 kΩ to 1 MΩ
Charge current
7
I7
1
µA
Rϕ-reference voltage
α ≥ 180°
6, 3
6
VϕRef
1.06
1.13
0.5
1.18
V
Temperature coefficient
TCVϕRef
mV/K
Pulse Output (see Figure 10-12 on page 18, Pin 4)
Output pulse current
Reverse current
RGT = 0, VGT = 1.2 V
Io
Ior
tp
100
V16
155
0.01
80
190
3.0
mA
µA
µs
Output pulse width
Amplifier
Cϕ = 10 nF
Common-mode signal range
Input bias current
Input offset voltage
10, 11
11
V10, V11
IIO
–1
1
V
0.01
10
µA
mV
10, 11
V10
–IO
+IO
75
88
110
120
145
165
µA
µA
Output current
12
12
I
12 = f(V10-11), (see Figure
Short circuit forward, transmittance
Yf
1000
µA/V
10-7 on page 17)
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4752B–INDCO–09/05
10. Electrical Characteristics (Continued)
–VS = 13.0V, Tamb = 25°C, reference point pin 2, unless otherwise specified
Parameters
Test Conditions
Pins
Symbol
Min.
Typ.
Max.
Unit
Pulse Blocking, Tacho Monitoring
Logic-on
Logic-off
18
18
–VTON
3.7
1.5
1.25
0.3
V
V
–VTOFF
1.0
1
V
18 = VTOFF = 1.25 V
µA
µA
Input current
18
18
II
V18 = V16
14.5
1.5
Output resistance
RO
6
10
2
kΩ
Frequency-to-voltage Converter
Input bias current
8
8
IIB
0.6
µA
II = –1 mA
II = +1 mA
(see Figure 10-7 on page
17)
–VI
+VI
660
7.25
750
8.05
mV
V
Input voltage limitation
Turn-on threshold
Turn-off threshold
Charge Amplifier
8
8
–VTON
100
50
150
mV
mV
–VTOFF
20
C5 = 1 nF, (see Figure
10-17 on page 21)
Discharge current
9
Idis
0.5
mA
V
Charge transfer voltage
Charge transfer gain
9 to 16
9, 10
Vch
Gi
6.50
7.5
6.70
8.3
6.90
9.0
I10/I9
C5 = 1 nF, R6 = 100 kΩ
(see Figure 10-17 on page
21)
Conversion factor
K
5.5
mV/Hz
Output operating range
Linearity
10 to 16
VO
0-6
±1
V
%
Soft Start, f/V Converter Non-active (see Figure 10-2 on page 15 and Figure 10-4 on page 16)
Starting current
Final current
V13 = V16, V8 = V2
V13 = 0.5
13
13
IO
IO
20
50
45
85
55
µA
µA
130
f/V Converter Active (see Figure 10-3 on page 15, Figure 10-5 on page 16 and Figure 10-6 on page 16)
Starting current
Final current
V13 = V16
13
13
IO
IO
IO
2
4
55
3
7
µA
µA
V13 = 0.5
30
0.5
80
10
Discharge current
Restart pulse
mA
Automatic Retriggering (see Figure 10-13 on page 19, Pin 5)
Repetition rate
R5-3 = 0
tpp
tpp
3
4.5
20
6
tp
tp
R5-3 = 15 kΩ
Load Limiting (see Figure 10-9 on page 17, Figure 10-10 on page 18 and Figure 10-11 on page 18)
Operating voltage range
14
VI
–1.0
5
+1.0
V
V10 = V16
V14 = V2 via 1 kΩ
14
15-16
IO
IO
12
1.0
µA
µA
Offset current
0.1
90
Input current
Output current
Overload ON
V10 = 4.5V
14
II
IO
60
120
140
7.7
µA
µA
V
V14 = 300 mV
15-16
15-16
110
7.05
VTON
7.4
14
U211B
4752B–INDCO–09/05
U211B
Figure 10-1. Ramp Control
240
200
160
120
80
Reference Point Pin 2
10 nF
4.7 nF
2.2 nF
Cϕ = 1.5 nF
t
0
0
0.2
0.4
Rϕt (M
0.6
0.8
1.0
Ω)
Figure 10-2. Soft-start Charge Current (f/V Converter Non-active)
100
80
60
40
20
Reference Point Pin 16
0
0
2
4
6
8
10
V13
(V)
Figure 10-3. Soft-start Charge Current (f/V Converter Active)
100
80
Reference Point Pin 16
60
40
20
0
10
0
2
4
6
8
V13
(V)
15
4752B–INDCO–09/05
Figure 10-4. Soft-start Voltage (f/V Converter Non-active)
10
8
6
4
2
Reference Point Pin 16
0
t = f(C3)
Figure 10-5. Soft-start Voltage (f/V Converter Active)
10
8
Reference Point Pin 16
6
4
2
0
t = f(C3)
Figure 10-6. Soft-start Function
10
8
Reference Point Pin 16
6
4
2
0
t = f(C3)
Motor Standstill (Dead Time)
Motor in Action
16
U211B
4752B–INDCO–09/05
U211B
Figure 10-7. f/V Converter Voltage Limitation
500
250
Reference Point Pin 2
0
-250
-500
-10
-8
-6
-4
-2
0
2
4
V8 (V)
Figure 10-8. Amplifier Output Characteristics
100
50
0
-50
Reference Point
for I12 = -4V
-100
-300 -200
-100
0
100
200
300
V10-11
(V)
Figure 10-9. Load Limit Control
200
150
100
50
0
0
2
4
6
8
V15-16 (V)
17
4752B–INDCO–09/05
Figure 10-10. Load Limit Control f/V Dependency
200
150
100
50
0
0
2
4
6
8
V10-16 (V)
Figure 10-11. Load Current Detection
250
200
150
100
I15 = f (VShunt
V10 = V16
)
50
0
0
100 200 300 400 500 600 700
V
14-2 (mV)
Figure 10-12. Pulse Output
100
80
60
40
20
0
VGT = 0.8V
1.4V
0
200
400
600
800
1000
RGT (Ω)
18
U211B
4752B–INDCO–09/05
U211B
Figure 10-13. Automatic Retriggering Repetition Rate
20
15
10
5
0
0
6
12
18
24
30
24
40
tpp/tp
Figure 10-14. Determination of R1
50
40
Mains Supply
230V
30
20
10
0
0
6
12
18
ttot (mA)
Figure 10-15. Power Dissipation of R1
6
5
4
3
2
1
Mains Supply
230V
0
0
10
20
30
R1 (kΩ)
19
4752B–INDCO–09/05
Figure 10-16. Power Dissipation of R1 According to Current Consumption
6
5
Mains Supply
230V
4
3
2
1
0
0
3
6
9
12
15
I
tot (mA)
20
U211B
4752B–INDCO–09/05
U211B
Figure 10-17. Speed Control, Automatic Retriggering, Load Limiting, Soft Start
L
D1
1N4007
M
R1
18 k
2W
Ω
R13
R3
220 k
R4
470 kΩ
47 k
Ω
Ω
Set speed
voltage
VM =
17
1
5
TIC
226
R31
R12
180
230V
~
100 k
Ω
Ω
4
6
Voltage/current
Automatic
retriggering
Output
pulse
detector
R14
R19
R2
1 M
56 k
Ω
100 k
Ω
Ω
R8
33 M
Control
amplifier
11
10
C10
+
Ω
3.3 nF
+
-
7
1W
2.2 µF/16V
C2
3
Phase-
control unit
Supply
voltage
limitation
22 µF/
25V
-VS
C1
N
2
+
+
ϕ
= f (V )
12
GND
R10
22 µF
C11
16
1 k
Ω
Reference
voltage
14
15
Load limitation
speed/time
controlled
R9
1 M
C9
Ω
Voltage
monitoring
+
4.7 µF/16V
Controlled
current sink
Frequency
to voltage
converter
Pulse blocking
tacho
monitoring
18
Soft start
13
-VRef
12
9
8
R9
C4
C7
C8
220 nF
C5
1 nF
+
Actual speed
voltage
1 MΩ
220 nF
10 µF/16V
C6
100 nF
R6
100 k
C3
R5
1 k
+
Ω
R7
Speed sensor
22 k
Ω
2.2 µF/16V
Ω
21
4752B–INDCO–09/05
Figure 10-18. Speed Control, Automatic Retriggering, Load Switch-off, Soft Start
C11
BZX55
C9
C8
C10
R6
100 k
4.7 µF
10V
2.2 µF
10V
+
R9
2.2 µF
Ω
+
+
220 nF
R11
470 k
Ω
T1
C6
R14
10 k
C3
2.2 µF
10V
100 nF
Ω
R15
47 k
1 M
11
8
Ω
+
Ω
R31
R16
47 k
250 k
Ω
T2
Ω
Set speed
voltage
C7
+
R3
220 k
2.2 µF/10V
10
L
R13
Ω
18
17
16
15
14
13
12
47 k
Ω
R10
2.2 k
D1
Ω
1N4004
R7
U211B
15 k
Ω
R1
18 k
1.5W
M
Ω
230V
~
1
2
3
4
5
6
7
9
R4
C5
680 pF
GND -VS
R2
470 k
Ω
R
ϕ
R12
1 M
Ω
R5
1 k
Ω
C2
2.2 nF
C
ϕt
C4
220 nF
180
Ω
C1
22 µF
N
+
25V
Speed sensor
R8 = 3 x 11 m
Ω/
1W
The switch-off level at maximum load shows in principle the same speed dependency as the
original version (see Figure 10-17 on page 21), but when reaching the maximum load, the
motor is switched off completely. This function is effected by the thyristor (formed by T1 and
T2) which ignites when the voltage at pin 15 reaches typically 7.4V (reference point pin 16).
The circuit is thereby switched to standby mode over the release Pin 18.
22
U211B
4752B–INDCO–09/05
U211B
Figure 10-19. Speed Control, Automatic Retriggering, Load Switch-down, Soft Start
R15
C11
33 k
Ω
BZX55
C9
C8
C10
R6
100 k
4.7 µF
10V
2.2 µF
10V
+
R9
470 kΩ
2.2 µF
Ω
+
+
220 nF
R11
T1
C6
C3
R14
10 k
2.2 µF
10V
100 nF
Ω
1 M
11
8
Ω
+
R31
R16
47 k
250 k
Ω
T2
Ω
Set speed
voltage
C7
+
R3
220 k
2.2 µF/10V
10
L
R13
Ω
18
17
16
15
14
13
12
47 k
Ω
R10
2.2 k
D1
1N4004
Ω
R7
U211B
15 k
Ω
R1
18 k
1.5W
M
Ω
230V
~
1
2
3
4
5
6
7
9
R4
C5
680 pF
GND -VS
R2
470 k
Ω
R
ϕ
R12
1 M
Ω
R5
1 k
Ω
C2
2.2 nF
C
ϕt
C4
220 nF
180
Ω
C1
22 µF
N
+
25V
Speed sensor
R8 = 3 x 11 m
Ω/
1W
The maximum load regulation shows in principle the same speed dependency as the original
version (see Figure 10-17 on page 21). When reaching the maximum load, the control unit is
turned to αmax, adjustable with R2. Then, only IO flows. This function is effected by the thyristor,
formed by T1 and T2 which ignites as soon as the voltage at pin 15 reaches approximately
6.8V (reference point pin 16). The potential at pin 15 is lifted and kept by R14 over the internal
operating threshold whereby the maximum load regulation starts and adjusts the control unit
constantly to αmax (IO), inspite of a reduced load current. The motor shows that the circuit is still
in operation by produceing a buzzing sound.
23
4752B–INDCO–09/05
Figure 10-20. Speed Control, Automatic Retriggering, Load Limiting, Soft Start, Tacho Control
C11
C9
C8
C10
R6
68 k
2.2 µF
10V
22 nF
R9
Ω
+
+
4.7
µF
220 nF
R11
1 M
Ω
C6
C3
100 nF
2.2 µF
10V
1.5 M
Ω
+
R31
250 k
Ω
1 M
Ω
+
Set speed
voltage
C7
+
1 µF/10V
R3
2.2 µF/10V
10
L
R13
47 k
220 k
Ω
18
17
16
15
14
13
12
11
Ω
R10
1 k
D1
1N4004
Ω
R7
22 k
230V
~
U211B
Ω
R1
18 k
1.5W
M
Ω
1
2
3
4
5
6
7
8
9
N
R4
C5
1 nF
GND -VS
470 k
Ω
R2
R
ϕ
R12
1 M
Ω
R5
1 k
Ω
C2
2.2 nF
C
ϕt
C4
220 nF
220
Ω
C1
22 µF
25V
+
Speed sensor
R8 = 3 x 11 m
Ω/
1W
24
U211B
4752B–INDCO–09/05
U211B
Figure 10-21. Speed Control with Reflective Opto Coupler CNY70 as Emitter
C4
C13
4.7 µF
10V
R8
47 k
Ω
R18
+
220 nF
Set speed
min.
C3
2.2 µF
10V
+
R7
470 k
R31
100 k
Ω
Ω
C11
10 µF/10V
22 nF
R13
Set speed
max.
all Diodes BYW83
R4
+
C8
R11
16 k
L
220 k
Ω
Ω
18
17
16
15
14
13
12
11
10
C7
L1
470 nF
D1
1N4004
M
U211B
R1
L2
18 k
Ω
1.5W
CNY70
230V
~
1
2
3
4
5
6
7
8
9
R14
100
R5
GND -VS
C6
Ω
470 kΩ
R2
R6
680 pF
R
ϕ
100
Ω
1 M
Ω
R9
220 k
4.7
R3
C2
3.3 nF
Ω
k
Ω
C
C5
ϕ
t
C12
150 nF
250V
C1
~
470 nF
R10
R17
R16
470
47 µF
25V
+
1.5 k
Ω
100
Ω
Ω
N
BZX55
C9V1
100 µF
10V
Z3
C10
+
1N4004
D2
3.5 k
Ω/8W
R15
ca. 220 Pulses/Revolution
25
4752B–INDCO–09/05
Figure 10-22. Speed Control, Maximum Load Control with Reflective Opto Coupler CNY70 as Emitter
C9
+
C6
C10
+
4.7 µF
10V
R6
82 k
4.7 µF
10V
Ω
R14
Set speed
min.
470 nF
R9
220 k
C3
2.2 µF
10V
Ω
+
R31
220 k
R11
820 k
C11
Ω
Ω
22 nF
10 µF
R13
Set speed
max.
+
C7
R3
R7
16 k
Ω
L
110 k
Ω
18
17
16
15
14
13
12
11
10
C8
R10
1 k
D1
1N4004
Ω
470 nF
230V
~
U211B
R1
10 k
M
Ω
1.1W
150 pF
250V
CNY70
1
2
3
4
5
6
7
8
9
~
N
100
Ω
R4
220 k
GND -VS
C5
Ω
C12
R12
R2
R
680 pF
ϕ
1 M
Ω
100
Ω
I
= 50 mA
C2
3.3 nF
C
ϕt
9V
R16
10 k
GT
C13
1 µF
Ω
C1
C4
22 µF
25V
R17
100
R18
470
R5
2.2 k
+
Ω
Ω
Ω
1 nF
R8 = 3 x 0.1
Ω
The schematic diagram (see Figure 10-22 on page 26) is designed as a speed control IC
based on the reflection-coupled principle with 4 periods per revolution and a maximum speed
of 30000 rpm. The separation of the coupler from the rotating aperture should be about
approximately 1 mm. In the schematic diagram, the power supply for the coupler was provided
externally because of the relatively high current consumption.
Instructions for adjusting:
1. In the initial adjustment of the phase-control circuit, R2 should be adjusted so that
when R14 = 0 and R31 are in minimum position, the motor just turns.
2. The speed can now be adjusted as desired by means of R31 between the limits deter-
mined by R13 and R14.
3. The switch-off power of the limiting-load control can be set by R9. The lower R9, the
higher the switch-off power.
26
U211B
4752B–INDCO–09/05
U211B
11. Ordering Information
Extended Type Number
Package
DIP18
SO16
Remarks
Tube
U211B-xY
U211B-xFPY
Tube
U211B-xFPG3Y
SO16
Taped and reeled
12. Package Information
Package DIP18
Dimensions in mm
7.77
7.47
23.3 max
4.8 max
3.3
6.4 max
0.5 min
0.36 max
1.64
1.44
0.58
0.48
9.8
8.2
2.54
20.32
18
10
technical drawings
according to DIN
specifications
1
9
5.2
4.8
Package SO16
Dimensions in mm
10.0
9.85
3.7
1.4
0.2
0.25
0.10
0.4
3.8
1.27
6.15
5.85
8.89
16
9
technical drawings
according to DIN
specifications
1
8
27
4752B–INDCO–09/05
13. Revision History
Please note that the following page numbers referred to in this section refer to the specific revision
mentioned, not to this document.
Revision No.
History
• Put datasheet in a new template
• First page: Pb-free logo added
4752B-INDCO-09/05
• Page 27: Ordering Information changed
28
U211B
4752B–INDCO–09/05
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4752B–INDCO–09/05
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