U211B-X_技术文档

U211B

Phase-Control IC – Tacho Applications/Overload Limitation

Description

The integrated circuit U211B is designed as a phase-con- speed-regulated motor applications.

trol circuit in bipolar technology with an internal It has an integrated load limitation, tacho monitoring and

frequency-voltage converter. Furthermore, it has an inter- soft-start functions, etc. to realize sophisticated motor

nal control amplifier which means it can be used for control systems.

F_De_Ia_nt_teu_rnr_ae_ls_{frequency-to-voltage converter}

D Triggering pulse typ. 155 mA

D Externally-controlled integrated amplifier

D Overload limitation with a “fold back” characteristic

D Optimized soft-start function

D Voltage and current synchronization

D Internal supply-voltage monitoring

D Temperature reference source

D Current requirement ≤ 3 mA

D Tacho monitoring for shorted and open loop

D Automatic retriggering switchable

Block Diagram

17(16)

1(1)

5*)

4(4)

Automatic

retriggering

Voltage / current

detector

Output

pulse

Control

amplifier

6(5)

7(6)

11(10)

10(9)

+

–

Phase

3(3)

2(2)

–V

-

control unit

ö= f (V

Supply

voltage

limitation

S

)

12

GND

Reference

voltage

14(13)

15(14)

16(15)

Load limitation

speed / time

controlled

Voltage

monitoring

Pulse-blocking

tacho

monitoring

Frequency-

to-voltage

converter

controlled

current sink

Soft start

18*)

–V

Ref

12(11)

13(12)

9(8) 8(7)

Figure 1. Block diagram (Pins in brackets refer to SO16)

*) Pins 5 and 18 connected internally

Order Information

Extended Type Number

U211B-x

Package

Remarks

DIP18

SO16

Tube

Taped and reeled

U211B-xFP

U211B-xFPG3

Rev. A4, 11-Jan-01

1 (21)

U211B

Pin Description

1

2

3

4

5

6

7

8

Symbol

Function

Current synchronization

Ground

I

1

2

3

4

5

6

7

8

9

18

17

16

15

14

13

12

11

10

sync

PB/TM

I

sync

GND

V

sync

V

S

Supply voltage

Output Trigger pulse output

Retr

V

RP

C

P

V

Ref

V

S

Retrigger programming

Ramp current adjust

Ramp voltage

Frequency-voltage converter

Charge pump

OVL

Output

Retr

F/V

I

9

C

sense

U211B

RV

10

11

12

13

14

15

16

17

18

OP–

OP+

OP inverting input

OP non-inverting input

C

V

soft

RP

CTR/OPO Control input / OP output

C

Soft start

CTR/OPO

OP+

C

soft

P

I

Load-current sensing

Overload adjust

Reference voltage

Voltage synchronization

sense

OVL

F/V

V

ref

V

sync

C

OP–

RV

PB/TM Pulse blocking /

tacho monitoring

Figure 3. Pinning DIP18

1

2

3

4

5

6

7

8

Symbol

Function

Current synchronization

Ground

I

V

1

2

3

4

5

6

7

8

16

I

sync

GND

V

S

Supply voltage

15

14

13

12

11

10

9

GND

V

Ref

Output Trigger pulse output

V

RP

Ramp current adjust

Ramp voltage

Frequency-voltage converter

Charge pump

OP inverting input

OP non-inverting input

V

S

OVL

C

P

F/V

Output

I

sense

C

RV

OP–

OP+

U211B

9

V

C

RP

soft

10

11

12

13

14

15

16

CTR/OPO Control input / OP output

C

Soft start

C

CTR/OPO

OP+

soft

P

I

Load-current sensing

Overload adjust

Reference voltage

Voltage synchronization

sense

OVL

F/V

V

ref

V

sync

C

OP–

RV

Figure 4. Pinning SO16

Rev. A4, 11-Jan-01

3 (21)

U211B

Description

When the potential on Pin 7 reaches the nominal value

predetermined at Pin 12, then a trigger pulse is generated

Mains Supply

The U211B is fitted with voltage limiting and can

therefore be supplied directly from the mains. The supply

voltage between Pin 2 (+ pol/ă) and Pin 3 builds up

whose width t is determined by the value of C (the value

p

2

of C and hence the pulse width can be evaluated by

2

assuming 8 m s/nF). At the same time, a latch is set, so that

as long as the automatic retriggering has not been

activated, no more pulses can be generated in that half

cycle.

across D and R and is smoothed by C . The value of the

1

series resistance can be approximated using:

V_M– V_S

R₁+

2 I_S

The current sensor on Pin 1 ensures that, for operations

with inductive loads, no pulse will be generated in a new

half cycle as long as a current from the previous half cycle

is still flowing in the opposite direction to the supply

voltage at that instant. This makes sure that “gaps” in the

load current are prevented.

Further information regarding the design of the mains

supply can be found in the design hints. The reference

voltage source on Pin 16 of typ. –8.9 V is derived from

the supply voltage and is used for regulation.

Operation using an externally stabilized DC voltage is not

recommended.

The control signal on Pin 12 can be in the range 0 V to

–7 V (reference point Pin 2).

If the supply cannot be taken directly from the mains

If V = –7 V, the phase angle is at maximum = a max, i.e.,

the current flow angle is a minimum. The phase angle

12

because the power dissipation in R would be too large,

1

then the circuit shown in figure 5 should be used.

a_minis minimum when V = V .

12

2

~

Voltage Monitoring

As the voltage is built up, uncontrolled output pulses are

avoided by internal voltage surveillance. At the same

time, all latches in the circuit (phase control, load limit

regulation, soft start) are reset and the soft-start capacitor

is short circuited. Used with a switching hysteresis of

300 mV, this system guarantees defined start-up behavior

each time the supply voltage is switched on or after short

interruptions of the mains supply.

24 V~

1

2

3

4

5

C

1

R

1

Soft Start

Figure 5. Supply voltage for high current requirements

As soon as the supply voltage builds up (t ), the integrated

1

soft start is initiated. Figure 6 shows the behaviour of the

voltage across the soft-start capacitor which is identical

with the voltage on the phase-control input on Pin 12.

This behavior guarantees a gentle start-up for the motor

and automatically ensures the optimum run-up time.

Phase Control

The phase angle of the trigger pulse is derived by compar-

ing the ramp voltage (which is mains synchronized by the

voltage detector) with the set value on the control input

Pin 12. The slope of the ramp is determined by C and its

2

charging current. The charging current can be varied

using R on Pin 6. The maximum phase angle a

can

2

max

also be adjusted using R .

2

4 (21)

Rev. A4, 11-Jan-01

U211B

The converter is based on the charge pumping principle.

With each negative half wave of the input signal, a

V

C3

quantity of charge determined by C is internally

5

V

12

amplified and then integrated by C at the converter

6

output on Pin 10. The conversion constant is determined

by C , its charge transfer voltage of V , R (Pin 10) and

5

ch

6

the internally adjusted charge transfer gain.

I₁₀

I₉

ƪ ƫ_+ 8.3

G_i

V

0

k = G C R V

ch

i

5

6

The analog output voltage is given by

t

1

t

3

V = k f

O

t

2

The values of C and C must be such that for the highest

5

6

t

tot

possible input frequency, the maximum output voltage

V does not exceed 6 V. While C is charging up, the R

i

on Pin 9 is approximately 6.7 kW. To obtain good

O

5

Figure 6. Soft start

linearity of the f/V converter, the time constant resulting

t

= build-up of supply voltage

= charging of C to starting voltage

1

2

from R and C should be considerably less (1/5) than the

i

5

3

time span of the negative half-cycle for the highest

possible input frequency. The amount of remaining ripple

t + t = dead time

t

1

2

= run-up time

= total start-up time to required speed

3

on the output voltage on Pin 10is dependent on C , C and

5

6

tot

the internal charge amplification.

C is first charged up to the starting voltage V with a

current of typically 45 m A (t ). By then reducing the

charging current to approx. 4 m A, the slope of the

charging function is substantially reduced so that the

rotational speed of the motor only slowly increases. The

3

0

G V C

i

ch

5

2

∆V =

O

C

6

The ripple ∆V can be reduced by using larger values of

o

C . However, the increasing speed will then also be

6

charging current then increases as the voltage across C

3

reduced.

increases, resulting in a progressively rising charging

function which accelerates the motor more and more with

increasing rotational speed. The charging function

determines the acceleration up to the set-point. The

charging current can have a maximum value of 55 m A.

The value of this capacitor should be chosen to fit the

particular control loop where it is going to be used.

Pulse Blocking

The output of pulses can be blocked by using Pin 18

(standby operation) and the system reset via the voltage

Frequency-to-Voltage Converter

The internal frequency-to-voltage converter (f/V-

converter) generates a DC signal on Pin 10 which is

proportional to the rotational speed using an AC signal

from a tacho generator or a light beam whose frequency

is in turn dependent on the rotational speed. The high-

impedance input Pin 8 compares the tacho voltage to a

switch-on threshold of typ. –100 mV. The switch-off

threshold is given with –50 mV. The hysteresis

guarantees very reliable operation even when relatively

simple tacho generators are used. The tacho frequency is

given by:

monitor if V ≥ –1.25 V. After cycling through the

18

switching point hysteresis, the output is released when

V

18

≤ –1.5 V followed by a soft start such as that after

turn-on.

Monitoring of the rotation can be carried out by

connecting an RC network to Pin 18. In the event of a

short or open circuit, the triac triggering pulses are cut off

by the time delay which is determined by R and C. The

capacitor C is discharged via an internal resistance

R = 2 kW with each charge transfer process of the f/V

i

converter. If there are no more charge transfer processes,

C is charged up via R until the switch-off threshold is

exceeded and the triac triggering pulses are cut off. For

operation without trigger pulse blocking or monitoring of

the rotation, Pins 18 and 16 must be connected together.

n

60

f +

p (Hz)

where:

n = revolutions per minute

p = number of pulses per revolution

Rev. A4, 11-Jan-01

5 (21)

U211B

exceeds an internally set threshold of approximately

7.3 V (reference voltage Pin 16), a latch is set and the load

limiting is turned on. A current source (sink) controlled

by the control voltage on Pin 15 now draws current from

Pin 12 and lowers the control voltage on Pin 12 so that the

C = 1 m F

10 V

18

17

16

15

phase angle a is increased to a

.

max

The simultaneous reduction of the phase angle during

which current flows causes firstly: a reduction of the

rotational speed of the motor which can even drop to zero

if the angular momentum of the motor is excessively

R = 1 MW

large, and secondly: a reduction of the potential on C

9

which in turn reduces the influence of the current sink on

Pin 12. The control voltage can then increase again and

bring down the phase angle. This cycle of action sets up

a “balanced condition” between the “current integral” on

Pin 15 and the control voltage on Pin 12.

1

2

3

4

Figure 7. Operation delay

Apart from the amplitude of the load current and the time

during which current flows, the potential on Pin 12 and

hence the rotational speed also affects the function of the

load limiting. A current proportional to the potential on

Control Amplifier (Figure 2)

The integrated control amplifier with differential input

compares the set value (Pin 11) with the instantaneous

value on Pin 10 and generates a regulating voltage on the

output Pin 12 (together with the external circuitry on

Pin 12) which always tries to hold the actual voltage at the

value of the set voltages. The amplifier has a

transmittance of typically 1000 m A/V and a bipolar

current source output on Pin 12 which operates with

typically ±110 m A. The amplification and frequency

Pin 10 gives rise to a voltage drop across R , via Pin 14,

10

so that the current measured on Pin 14 is smaller than the

actual current through R .

8

This means that higher rotational speeds and higher

current amplitudes lead to the same current integral.

Therefore, at higher speeds, the power dissipation must

be greater than that at lower speeds before the internal

threshold voltage on Pin 15 is exceeded. The effect of

speed on the maximum power is determined by the

response are determined by R , C , C and R (can be left

7

8

11

out). For open-loop operation, C , C , R , R , C , C and

4

5

6

7

8

resistor R and can therefore be adjusted to suit each

10

R

can be omitted. Pin 10 should be connected with

11

individual application.

Pin 12 and Pin 8 with Pin 2. The phase angle of the

triggering pulse can be adjusted using the voltage on

Pin 11. An internal limitation circuit prevents the voltage

If, after the load limiting has been turned on, the

momentum of the load sinks below the “o-momentum”

on Pin 12 from becoming more negative than V + 1 V.

16

set using R , then V will be reduced. V can then in-

10

15

12

crease again so that the phase angle is reduced. A smaller

phase angel corresponds to a larger momentum of the mo-

tor and hence the motor runs up - as long as this is allowed

by the load momentum. For an already rotating machine,

the effect of rotation on the measured “current integral”

ensures that the power dissipation is able to increase with

the rotational speed. The result is a current-controlled

accelleration run-up which ends in a small peak of accel-

leraton when the set point is reached. The latch of the load

limiting is simultaneously reset. The speed of the motor

is then again under control and is capable of carrying its

full load. The above mentioned peak of acceleration

depends upon the ripple of actual speed voltage. A large

amount of ripple also leads to a large peak of acceleration.

Load Limitation

The load limitation, with standard circuitry, provides

absolute protection against overloading of the motor. The

function of the load limiting takes account of the fact that

motors operating at higher speeds can safely withstand

larger power dissipations than at lower speeds due to the

increased action of the cooling fan. Similarly, consider-

ations have been made for short–term overloads for the

motor which are, in practice, often required. These

behavior are not damaging and can be tolerated.

In each positive half-cycle, the circuit measures via R

the load current on Pin 14 as a potential drop across R

and produces a current proportional to the voltage on

Pin 14. This current is available on Pin 15 and is The measuring resistor R should have a value which

10

8

integrated by C . If, following high-current amplitudes or ensures that the amplitude of the voltage across it does not

9

a large phase angle for current flow, the voltage on C

exceed 600 mV.

9

6 (21)

Rev. A4, 11-Jan-01

U211B

Design Hints

Practical trials are normally needed for the exact following table shows the effect of the circuitry on the

determination of the values of the relevant components in important parameters of the load limiting and summa-

the load limiting. To make this evaluation easier, the rizes the general tendencies.

Parameters

Component

R Increasing

R

10

Increasing

C Increasing

9

P

increases

n.e.

decreases

n.e.

max

decreases

n.e.

min

/

max min

t

increases

d

n.e.

r

P

– maximum continuous power dissipation

– power dissipation with no rotation

– operation delay time

P = f n 0 0

1 (n)

max

min

P = f n = 0

1

(n)

t

d

– recovery time

r

n.e

– no effect

Pulse-Output Stage

General Hints and Explanation of Terms

To ensure safe and trouble-free operation, the following

points should be taken into consideration when circuits

are being constructed or in the design of printed circuit

boards.

The pulse-output stage is short-circuit protected and can

typically deliver currents of 125 mA. For the design of

smaller triggering currents, the function I = f(R ) can

GT

be taken from figure 20.

–

The connecting lines from C to Pin 7 and Pin 2

should be as short as possible. The connection to Pin 2

should not carry any additional high current such as

2

Automatic Retriggering

The variable automatic retriggering prevents half cycles

without current flow, even if the triac is turned off earlier,

e.g., due to a collector which is not exactly centered

(brush lifter) or in the event of unsuccessful triggering. If

necessary, another triggering pulse is generated after a

time lapse which is determined by the repetition rate set

the load current. When selecting C , a low

2

temperature coefficient is desirable.

The common (earth) connections of the set-point

generator, the tacho generator and the final

interference suppression capacitor C of the f/V

4

by resistance between Pin 5 and Pin 3 (R ). With the

converter should not carry load current.

5-3

maximum repetition rate (Pin 5 directly connected to

Pin 3), the next attempt to trigger comes after a pause of

–

The tacho generator should be mounted without

influence by strong stray fields from the motor.

4.5 t and this is repeated until either the triac fires or the

p

The connections from R and C should be as short

10

5

half cycle finishes. If Pin 5 is connected, then only one

trigger pulse per half cycle is generated. Because the

as possible.

To achieve a high noise immunity, a maximum ramp

voltage of 6 V should be used.

value of R determines the charging current of C , any

5-3

2

repetition rate set using R is only valid for a fixed value

5-3

of C .

The typical resistance R can be calculated from I as

2

ö

follows:

T(ms) 1.13(V) 10³

C(nF) 6(V)

R_ö(kW) +

T = Period duration for mains frequency

(10 ms at 50 Hz)

C = Ramp capacitor, max. ramp voltage 6 V

ö

and constant voltage drop at R = 1.13 V.

ö

A 10% lower value of R (under worst case conditions)

ö

is recommended.

Rev. A4, 11-Jan-01

7 (21)

U211B

V

Mains

Supply

p /2

p

3/2p

2p

V

GT

Trigger

Pulse

t

p

t

pp

= 4.5 t

p

V

L

Load

Voltage

I

ö

L

Load

Current

F

Figure 8. Explanation of terms in phase relationship

Design Calculations for Mains Supply

The following equations can be used for the evaluation of the series resistor R for worst case conditions:

1

V

_Mmin– V_Smax

2 I_tot

V_M– V_Smin

2 I_Smax

R_1max+ 0.85

R_1min+

2

(V_Mmax– V_Smin

2 R₁

)

P_(R1max)

where:

+

V

V_S

= Mains voltage

= Supply voltage on Pin 3

= Total DC current requirement of the circuit

= I + I + I

M

I

tot

S

p

x

I

= Current requirement of the IC in mA

= Average current requirement of the triggering pulse

= Current requirement of other peripheral components

Smax

p

x

R can be easily evaluated from the figures 22 to 24.

1

8 (21)

Rev. A4, 11-Jan-01

U211B

Absolute Maximum Ratings

Reference point Pin 2, unless otherwise specified

Parameters

Symbol

Value

Unit

Current requirement

Pin 3

–I

30

mA

S

s

–i

100

mA

t ≤ 10 m s

Synchronization current

Pin 1

Pin 17

Pin 1

Pin 17

Pin 8

I

5

35

mA

syncI

I

syncV

t t 10 m s

±i

I

f/V converter

Input current

I

3

mA

I

±i

13

t t 10 m s

Load limiting

I

Pin 14

Limiting current, negative half wave

I

5

35

1

mA

I

t t 10 m s

I

Input voltage

Pin 14

Pin 15

±V

–V

V

i

V

to 0

I

16

Phase control

Input voltage

Input current

Pin 12

Pin 6

–V

0 to 7

500

1

V

m A

mA

I

±I

I

–I

I

Soft start

Input voltage

Pulse output

Reverse voltage

Pulse blocking

Input voltage

Amplifier

Pin 13

Pin 4

–V

V

to 0

V

I

16

V

R

V to 5

S

Pin 18

–V

V

16

to 0

I

Input voltage

Pin 9 open

Pin 11

Pin 10

V

I

0 to V

V

S

to 0

–V

V

16

Reference voltage source

Output current

Storage temperature range

Junction temperature

Pin 16

I

7.5

–40 to +125

125

mA

°C

o

T

stg

T

j

Ambient temperature range

T

–10 to +100

amb

Thermal Resistance

Parameters

Symbol

Maximum

Unit

Junction ambient

DIP18

SO16 on p.c.

SO16 on ceramic

R

120

180

100

K/W

thJA

Rev. A4, 11-Jan-01

9 (21)

U211B

Electrical Characteristics

–V = 13.0 V, T

= 25°C, reference point Pin 2, unless otherwise specified

S

amb

Parameters

Supply voltage for mains

operation

Test Conditions / Pins

Pin 3

Symbol

Min.

13.0

Typ.

Max.

Unit

V

–V

V

Limit

S

Supply voltage limitation

–I = 4 mA

–I = 30 mA

S

Pin 3

–V

14.6

14.7

16.6

16.8

V

S

DC current requirement

Reference voltage source

–V = 13.0 V

Pin 3

Pin 16

I

–V

1.2

8.6

8.3

2.5

8.9

3.0

9.2

9.1

mA

V

S

–I = 10 m A

L

Ref

–I = 5 mA

L

Temperature coefficient

Voltage monitoring

Turn-on threshold

Pin 16 –TC

0.5

mV/K

VRef

Pin 3 –V

11.2

9.9

13.0

10.9

V

SON

Turn-off threshold

Pin 3 –V

SOFF

Phase-control currents

Synchronization current

Pin 1 "I

0.35

1.4

2.0

1.8

mA

V

syncI

"I

Pin 17

"I = 5 mA Pins 1 and 17

syncV

Voltage limitation

"V

1.6

L

I

Reference ramp, see figure 9

Charge current

I = f (R );

7

6

R = 50 k to 1 MW

Pin 7

I

1

1.06

20

1.13

0.5

m A

V

mV/K

6

7

R -reference voltage

a

ꢀ

≥

ꢀ

1

8

0

°

C

Pins 6 and 3

V

1.18

Ref

ö

Temperature coefficient

Pulse output, see figure 20

Output pulse current

Reverse current

Output pulse width

Amplifier

Pin 6 TC

V Ref

ö

Pin 4

= 0, V = 1.2 V

R

I

o

100

155

0.01

80

190

3.0

mA

m A

m s

GT

I

or

Cϕ = 10 nF

t

p

Common-mode signal range

Input bias current

Input offset voltage

Output current

Pins 10 and 11

Pin 11

Pins 10 and 11

Pin 12

V ,

V

–1

1

V

m A

mV

m A

10 11

16

I

0.01

10

110

120

IO

V

10

–I

O

+I

O

75

88

145

165

Short circuit forward,

transmittance

Pulse blocking, tacho monitoring

See figure 16

I

= f(V

)

Pin 12

Pin 18

Y

f

1000

m

A

/

V

12

10 -11

Logic-on

Logic-off

Input current

–V

3.7

1.5

1.25

0.3

V

m A

TON

–V

1.0

1

TOFF

V

18

V

18

= V

= 1.25 V

I

R

TOFF

16

I

14.5

1.5

Output resistance

6

10

kW

O

10 (21)

Rev. A4, 11-Jan-01

U211B

Electrical Characteristics (continued)

–V = 13.0 V, T

= 25°C, reference point Pin 2, unless otherwise specified

S

amb

Parameters

Frequency-to-voltage converter

Input bias current

Test Conditions / Pins

Pin 8

Symbol

Min.

Typ.

Max.

Unit

I

0.6

2

m A

IB

Input voltage limitation

See figure 15

I = –1 mA

–V

+V

660

7.25

750

8.05

150

mV

V

mV

I

I = +1 mA

I

Turn-on threshold

Turn-off threshold

Charge amplifier

Discharge current

–V

100

50

TON

–V

I

20

mV

TOFF

See figure 2, C = 1 nF,

0.5

mA

V

5

dis

Pin 9

Charge transfer voltage

Charge transfer gain

Conversion factor

Pins 9 to 16

Pins 9 and 10

See figure 2

C = 1 nF, R = 100 kW

V

ch

6.50

7.5

6.70

8.3

6.90

9.0

I /I

G

i

10

9

K

5.5

0-6

ꢀ1

mV/Hz

5

6

Output operating range

Linearity

Pins 10 to 16

V

O

V

%

Soft start, see figures 10, 12, f/v-converter non-active

Starting current

Final current

V

13

V

13

= V V = V Pin 13

I

20

50

45

85

55

130

m A

16,

8

2

O

= 0.5

Pin 13

O

f/v-converter active, see figures 11, 13, 14

Starting current

Final current

Discharge current

V

= V

= 0.5

Pin 13

I

2

30

0.5

4

55

3

7

80

10

m A

mA

13

16

O

Restart pulse

Pin 13

Pin 5

Automatic retriggering, see figure 21

Repetition rate

R

= 0

= 15 kW

t

3

4.5

20

6

t

5-3

pp

p

Load limiting, see figures 17, 18, 19

Pin 14

Operating voltage range

Offset current

Pin 14

V

–1.0

5

1.0

12

1.0

V

m A

I

V

= V

= V via 1 kW

I

10

14

16

O

0.1

90

2

Pin 15–16

Input current

Output current

Overload ON

V

= 4.5 V

Pin 14

= 300 mV Pin 15–16

Pin 15–16

I

60

110

7.05

120

140

7.7

m A

V

10

I

14

O

V

TON

7.4

Rev. A4, 11-Jan-01

11 (21)

U211B

240

10

8

Reference Point Pin 2

2.2nF

200

10nF 4.7nF

160

6

120

80

0

4

2

0

C _ö=1.5nF

/t

Reference Point Pin 16

1.0

0

0.2

0.4

0.6

0.8

R ( MW )

ö

t=f

(C3)

Figure 9. Ramp control

Figure 12. Soft-start voltage (f/V-converter non-active)

10

100

80

8

Reference Point Pin 16

60

6

40

20

0

4

2

0

Reference Point Pin 16

10

0

2

4

6

8

V

13

( V )

t=f

(C3)

Figure 10. Soft-start charge current (f/V-converter non-active)

100

Figure 13. Soft-start voltage (f/V-converter active)

10

8

80

Reference Point Pin 16

6

60

4

2

0

40

20

0

t=f

(C3)

Motor Standstill ( Dead Time )

Motor in Action

10

0

2

4

6

8

V

13

( V )

Figure 11. Soft-start charge current (f/V-converter active)

Figure 14. Soft-start function

12 (21)

Rev. A4, 11-Jan-01

U211B

500

250

200

150

Reference Point Pin 2

0

100

–250

–500

50

0

4

300

8

–10 –8

–6

–4

–2

0

2

0

2

4

6

V ( V )

V

(V)

8

10–16

Figure 15. f/V-converter voltage limitation

Figure 18. Load limit control f/V dependency

250

100

200

150

100

50

0

–50

–100

I

15

=f ( V

)

Shunt

50

0

V

=V

10

16

Reference Point

for I = –4V

12

700

–300 –200 –100

0

100

( V )

200

0

100 200 300 400 500 600

( mV )

V

10–11

V

14–2

Figure 16. Amplifier output characteristic

Figure 19. Load current detection

200

100

80

150

100

60

40

20

0

1.4V

V

GT

=0.8V

50

0

1000

0

2

4

6

0

200

400

600

( W )

800

V

15–16

( V )

R

GT

Figure 17. Load limit control

Figure 20. Pulse output

Rev. A4, 11-Jan-01

13 (21)

U211B

20

6

5

4

3

2

Mains Supply

230 V

15

10

5

1

0

30

40

6

12

18

24

0

10

20

R ( kW )

30

t

pp

/t

p

1

Figure 21. Automatic retriggering repetition rate

50

Figure 23. Power dissipation of R₁

6

5

40

Mains Supply

230 V

Mains Supply

4

3

2

230 V

30

20

10

0

1

0

16

15

0

4

8

12

0

3

6

9

12

I

tot

( mA )

I

tot

( mA )

Figure 22. Determination of R₁

Figure 24. Power dissipation of R₁

according to current consumption

14 (21)

Rev. A4, 11-Jan-01

U211B

Figure 25. Speed control, automatic retriggering, load switch-off, soft start

The switch-off level at maximum load shows in principle This function is effected by the thyristor (formed by T

1

the same speed dependency as the original version (see and T which ignites when the voltage at Pin 15 reaches

2)

figure 2), but when reaching the maximum load, the typ. 7.4 V (reference point Pin 16). The circuit is thereby

motor is switched off completely.

switched in the “stand-by mode” over the release Pin 18.

Rev. A4, 11-Jan-01

15 (21)

U211B

Figure 26. Speed control, automatic retriggering, load switch-off, soft start

The maximum load regulation shows the principle in the at Pin 15 is lifted and kept by R over the internally

14

same speed dependency as the original version (see operating threshold whereby the maximum load

figure 2). When reaching the maximum load, the control regulation starts and adjusts the control unit constantly to

unit is turned to a , adjustable with R . Then only I

a

(I ), inspite of a reduced load current. The motor

max O

max

2

O

flows. This function is effected by the thyristor, formed shows that the circuit is still in operation in the matter of

by T and T which ignites as soon as the voltage at Pin 15 a quiet buzzing sound.

1

2

reaches ca. 6.8 V (reference point Pin 16). The potential

16 (21)

Rev. A4, 11-Jan-01

U211B

Figure 28. Speed control with reflective opto coupler CNY70 as emitter

18 (21)

Rev. A4, 11-Jan-01

U211B

Figure 29. Speed control, max. load control with reflective opto coupler CNY70 as emitter

Rev. A4, 11-Jan-01

19 (21)

U211B

The circuit is designed as a speed control based on the Instructions for adjusting:

reflection-coupled principle with 4 periods per revolution

D In the initial adjustment of the phase-control circuit,

and a max. speed of 30.000 rpm. The separation of the

coupler from the rotating aperture should be about 1 mm

approximately. In this experimental circuit, the power

supply for the coupler was provided externally because of

the relatively high current consumption.

R should be adjusted so that when R = 0 and R are

2

14

31

in min. position, the motor just turns.

D The speed can now be adjusted as desired by means of

R

between the limits determined by R and R .

13 14

31

D The switch-off power of the limiting-load control can

be set by R . The lower R , the higher the switch-off

9

power.

Package Information

Package DIP18

7.77

7.47

23.3 max

Dimensions in mm

4.8 max

6.4 max

0.36 max

3.3

0.5 min

1.64

1.44

0.58

0.48

9.8

8.2

2.54

20.32

18

10

technical drawings

according to DIN

specifications

1

9

5.2

4.8

Package SO16

Dimensions in mm

10.0

9.85

3.7

1.4

0.2

0.25

0.10

0.4

1.27

3.8

6.15

5.85

8.89

16

9

technical drawings

according to DIN

specifications

1

8

20 (21)

Rev. A4, 11-Jan-01

U211B

Ozone Depleting Substances Policy Statement

It is the policy of Atmel Germany GmbH to

1. Meet all present and future national and international statutory requirements.

2. Regularly and continuously improve the performance of our products, processes, distribution and operating systems

with respect to their impact on the health and safety of our employees and the public, as well as their impact on

the environment.

It is particular concern to control or eliminate releases of those substances into the atmosphere which are known as

ozone depleting substances (ODSs).

The Montreal Protocol (1987) and its London Amendments (1990) intend to severely restrict the use of ODSs and forbid

their use within the next ten years. Various national and international initiatives are pressing for an earlier ban on these

substances.

Atmel Germany GmbH has been able to use its policy of continuous improvements to eliminate the use of ODSs listed

in the following documents.

1. Annex A, B and list of transitional substances of the Montreal Protocol and the London Amendments respectively

2. Class I and II ozone depleting substances in the Clean Air Act Amendments of 1990 by the Environmental

Protection Agency (EPA) in the USA

3. Council Decision 88/540/EEC and 91/690/EEC Annex A, B and C (transitional substances) respectively.

Atmel Germany GmbH can certify that our semiconductors are not manufactured with ozone depleting substances

and do not contain such substances.

We reserve the right to make changes to improve technical design and may do so without further notice.

Parameters can vary in different applications. All operating parameters must be validated for each customer

application by the customer. Should the buyer use Atmel Wireless & Microcontrollers products for any unintended

or unauthorized application, the buyer shall indemnify Atmel Wireless & Microcontrollers against all claims,

costs, damages, and expenses, arising out of, directly or indirectly, any claim of personal damage, injury or death

associated with such unintended or unauthorized use.

Data sheets can also be retrieved from the Internet:

http://www.atmel–wm.com

Atmel Germany GmbH, P.O.B. 3535, D-74025 Heilbronn, Germany

Telephone: 49 (0)7131 67 2594, Fax number: 49 (0)7131 67 2423

Rev. A4, 11-Jan-01

21 (21)


型号：	U211B-X
厂家：	TEMIC SEMICONDUCTORS
描述：	Analog Circuit, 1 Func, BIPolar, PDIP18, DIP-18 ATM 异步传输模式光电二极管
文件：	总21页 (文件大小：170K)
中文：	中文翻译
下载：	下载PDF数据表文档文件

U211B-X [TEMIC]

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