AD8039ART-REEL7 [ADI]
Low Power 350 MHz Voltage Feedback Amplifiers; 低功耗350 MHz电压反馈放大器
| 型号： | AD8039ART-REEL7 |
| 厂家： | 
ADI |
| 描述： | Low Power 350 MHz Voltage Feedback Amplifiers |
| 文件： | 总12页 (文件大小：340K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
Low Power 350 MHz
a
Voltage Feedback Amplifiers
AD8038/AD8039
FEATURES
CONNECTION DIAGRAMS
Low Power
1 mA Supply Current/Amp
High Speed
350 MHz, –3 dB Bandwidth (G = +1)
425 V/s Slew Rate
Low Cost
SC70-5 (KS)
SOIC-8 (R)
AD8038
AD8038
V
1
2
3
4
8
1
2
5 +V
DISABLE
NC
–IN
+IN
OUT
S
7
6
5
+V
S
–V
S
+ –
V
OUT
Low Noise
+IN
3
4
–IN
–V
NC
S
8 nV/√Hz @ 100 kHz
600 fA/√Hz @ 100 kHz
Low Input Bias Current: 750 nA Max
Low Distortion
NC = NO CONNECT
SOIC-8 (R) and SOT23-8 (RT)*
–90 dB SFDR @ 1 MHz
–65 dB SFDR @ 5 MHz
Wide Supply Range: 3 V to 12 V
Small Packaging: SOT23-8, SC70-5, and SOIC-8
AD8039
V
1
2
3
4
8
7
6
5
+V
OUT1
S
–IN1
+IN1
V
OUT2
APPLICATIONS
Battery-Powered Instrumentation
Filters
–IN2
+IN2
–V
S
A/D Driver
Level Shifting
Buffering
High Density PC Boards
Photo Multiplier
PRODUCT DESCRIPTION
The AD8039 amplifier is the only dual low power, high speed
amplifier available in a tiny SOT23-8 package, and the single
AD8038 is available in both a SOIC-8 and a SC70-5 package.
These amps are rated to work over the industrial temperature
range of –40°C to +85°C.
The AD8038 (single) and AD8039 (dual) amplifiers are high
speed (350 MHz) voltage feedback amplifiers with an exceptionally
low quiescent current of 1.0 mA/amplifier typical (1.5 mA max).
The AD8038 single amplifier in the SOIC-8 package has a
disable feature. Despite being low power and low cost, the
amplifier provides excellent overall performance. Additionally,
it offers a high slew rate of 425 V/µs and low input offset volt-
age of 3 mV max.
24
G = +10
G = +5
21
18
ADI’s proprietary XFCB process allows low noise operation
(8 nV/√Hz and 600 fA/√Hz) at extremely low quiescent currents.
Given a wide supply voltage range (3 V to 12 V), wide bandwidth,
and small packaging, the AD8038 and AD8039 amplifiers are
designed to work in a variety of applications where power and space
are at a premium.
15
12
9
6
3
G = +2
G = +1
The AD8038 and AD8039 amplifiers have a wide input common-
mode range of 1 V from either rail and will swing within 1 V of
each rail on the output. These amplifiers are optimized for
driving capacitive loads up to 15 pF. If driving larger capaci-
tive loads, a small series resistor is needed to avoid excessive
peaking or overshoot.
0
–3
–6
0.1
1
10
100
1000
FREQUENCY – MHz
*Not yet released
Figure 1. Small Signal Frequency Response for
Various Gains, VOUT = 500 mV p-p, VS = 5 V
REV. B
Information furnished by Analog Devices is believed to be accurate and
reliable. However, no responsibility is assumed by Analog Devices for its
use, norforanyinfringementsofpatentsorotherrightsofthirdpartiesthat
may result from its use. No license is granted by implication or otherwise
under any patent or patent rights of Analog Devices.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781/329-4700
Fax: 781/326-8703
www.analog.com
© Analog Devices, Inc., 2002
AD8038/AD8039–SPECIFICATIONS (TA = 25؇C, VS = ؎5 V, RL = 2 k⍀, Gain = +1, unless otherwise noted.)
Parameter
Conditions
Min
Typ
Max
Unit
DYNAMIC PERFORMANCE
–3 dB Bandwidth
G = 1, VO = 0.5 V p-p
G = 2, VO = 0.5 V p-p
G = 1, VO = 2 V p-p
G = 2, VO = 0.2 V p-p
G = 1, VO = 2 V Step, RL = 2 kΩ
G = 2, 1 V Overdrive
G = 2, VO = 2 V Step
300
350
175
100
45
425
50
MHz
MHz
MHz
MHz
V/µs
ns
Bandwidth for 0.1 dB Flatness
Slew Rate
Overdrive Recovery Time
Settling Time to 0.1%
400
18
ns
NOISE/HARMONIC PERFORMANCE
SFDR
Second Harmonic
Third Harmonic
Second Harmonic
Third Harmonic
Crosstalk, Output-to-Output (AD8039)
Input Voltage Noise
Input Current Noise
fC = 1 MHz, VO = 2 V p-p, RL = 2 kΩ
fC = 1 MHz, VO = 2 V p-p, RL = 2 kΩ
fC = 5 MHz, VO = 2 V p-p, RL = 2 kΩ
fC = 5 MHz, VO = 2 V p-p, RL = 2 kΩ
f = 5 MHz, G = 2
–90
–92
–65
–70
–70
8
dBc
dBc
dBc
dBc
dB
nV/√Hz
fA/√Hz
f = 100 kHz
f = 100 kHz
600
DC PERFORMANCE
Input Offset Voltage
Input Offset Voltage Drift
Input Bias Current
Input Bias Current Drift
Input Offset Current
Open-Loop Gain
0.5
4.5
400
3
25
70
3
mV
µV/°C
nA
nA/°C
nA
dB
750
VO = 2.5 V
INPUT CHARACTERISTICS
Input Resistance
Input Capacitance
Input Common-Mode Voltage Range
Common-Mode Rejection Ratio
10
2
4
MΩ
pF
V
RL = 1 kΩ
VCM
=
2.5 V
61
67
dB
OUTPUT CHARACTERISTICS
DC Output Voltage Swing
Capacitive Load Drive
RL = 2 kΩ, Saturated Output
30% Overshoot, G = +2
4
20
V
pF
POWER SUPPLY
Operating Range
Quiescent Current per Amplifier
Power Supply Rejection Ratio
3.0
12
1.5
V
1.0
–77
–70
mA
dB
dB
– Supply
+ Supply
–71
–64
POWER-DOWN DISABLE*
Turn-On Time
Turn-Off Time
Disable Voltage – Part is OFF
Disable Voltage – Part is ON
Disabled Quiescent Current
Disabled In/Out Isolation
180
700
+VS – 4.5
+VS – 2.5
0.2
ns
ns
V
V
mA
dB
f = 1 MHz
–60
*Only available in AD8038 SOIC-8 package.
Specifications subject to change without notice.
–2–
REV. B
AD8038/AD8039
SPECIFICATIONS (TA = 25؇C, VS = 5 V, RL = 2 k⍀ to VS/2, Gain = +1, unless otherwise noted.)
Parameter
Conditions
Min
Typ
Max
Unit
DYNAMIC PERFORMANCE
–3 dB Bandwidth
G = 1, VO = 0.2 V p-p
G = 2, VO = 0.2 V p-p
G = 1, VO = 2 V p-p
G = 2, VO = 0.2 V p-p
G = 1, VO = 2 V Step, RL = 2 kΩ
G = 2, 1 V Overdrive
G = 2, VO = 2 V Step
275
300
150
30
45
365
50
MHz
MHz
MHz
MHz
V/µs
ns
Bandwidth for 0.1 dB Flatness
Slew Rate
Overdrive Recovery Time
Settling Time to 0.1%
340
18
ns
NOISE/HARMONIC PERFORMANCE
SFDR
Second Harmonic
Third Harmonic
Second Harmonic
Third Harmonic
Crosstalk, Output-to-Output
Input Voltage Noise
Input Current Noise
fC = 1 MHz, VO = 2 V p-p, RL = 2 kΩ
fC = 1 MHz, VO = 2 V p-p, RL = 2 kΩ
fC = 5 MHz, VO = 2 V p-p, RL = 2 kΩ
fC = 5 MHz, VO = 2 V p-p, RL = 2 kΩ
f = 5 MHz, G = 2
–82
–79
–60
–67
–70
8
dBc
dBc
dBc
dBc
dB
nV/√Hz
fA/√Hz
f = 100 kHz
f = 100 kHz
600
DC PERFORMANCE
Input Offset Voltage
Input Offset Voltage Drift
Input Bias Current
Input Bias Current Drift
Input Offset Current
Open-Loop Gain
0.8
3
400
3
30
70
3
mV
µV/°C
nA
nA/°C
nA
dB
750
VO = 2.5 V
INPUT CHARACTERISTICS
Input Resistance
Input Capacitance
Input Common-Mode Voltage Range
Common-Mode Rejection Ratio
10
2
1.0–4.0
65
MΩ
pF
V
RL = 1 kΩ
VCM
=
1 V
59
dB
OUTPUT CHARACTERISTICS
DC Output Voltage Swing
Capacitive Load Drive
RL = 2 kΩ, Saturated Output
30% Overshoot
0.9–4.1
20
V
pF
POWER SUPPLY
Operating Range
3
12
V
Quiescent Current per Amplifier
Power Supply Rejection Ratio
0.9
–71
1.5
mA
dB
–65
POWER-DOWN DISABLE*
Turn-On Time
Turn-Off Time
Disable Voltage – Part is OFF
Disable Voltage – Part is ON
Disabled Quiescent Current
Disabled In/Out Isolation
210
700
+VS – 4.5
+VS – 2.5
0.2
ns
ns
V
V
mA
dB
f = 1 MHz
–60
*Only available in AD8038 SOIC-8 package.
Specifications subject to change without notice.
REV. B
–3–
AD8038/AD8039
ABSOLUTE MAXIMUM RATINGS*
2.0
1.5
1.0
0.5
0
Supply Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 12.6 V
Power Dissipation . . . . . . . . . . . . . . . . . . . . . . . . See Figure 2
Common-Mode Input Voltage . . . . . . . . . . . . . . . . . . . . . VS
Differential Input Voltage . . . . . . . . . . . . . . . . . . . . . . . . 4 V
Storage Temperature . . . . . . . . . . . . . . . . . . –65°C to +125°C
Operating Temperature Range . . . . . . . . . . . –40°C to +85°C
Lead Temperature Range (Soldering 10 sec) . . . . . . . . . 300°C
*Stresses above those listed under Absolute Maximum Ratings may cause perma-
nent damage to the device. This is a stress rating only; functional operation of the
device at these or any other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute maximum rating
conditions for extended periods may affect device reliability.
SOIC-8
SOT23-8
SC70-5
–55
–25
5
35
65
95
125
MAXIMUM POWER DISSIPATION
AMBIENT TEMPERATURE – ؇C
The maximum safe power dissipation in the AD8038/AD8039
package is limited by the associated rise in junction temperature (TJ)
on the die. The plastic encapsulating the die will locally reach the
junction temperature. At approximately 150°C, which is the glass
transition temperature, the plastic will change its properties. Even
temporarily exceeding this temperature limit may change the stresses
that the package exerts on the die, permanently shifting the parametric
performance of the AD8038/AD8039. Exceeding a junction tempera-
ture of 175°C for an extended period of time can result in changes
in the silicon devices, potentially causing failure.
Figure 2. Maximum Power Dissipation vs.
Temperature for a Four-Layer Board
RMS output voltages should be considered. If RL is referenced to
VS–, as in single-supply operation, then the total drive power is
VS ꢁ IOUT
.
If the RMS signal levels are indeterminate, then consider the
worst case, when VOUT = VS / 4 for RL to midsupply:
2
The still-air thermal properties of the package and PCB (ꢀJA), ambient
temperature (TA), and total power dissipated in the package (PD)
determine the junction temperature of the die. The junction
temperature can be calculated as follows:
PD = V × I + V / 4 / RL
(
)
(
)
S
S
S
In single-supply operation with RL referenced to VS–, worst case is
VOUT = VS / 2.
Airflow will increase heat dissipation effectively reducing ꢀJA. Also,
more metal directly in contact with the package leads from metal traces,
through holes, ground, and power planes, will reduce the ꢀJA. Care
must be taken to minimize parasitic capacitances at the input leads
of high speed op amps as discussed in the board layout section.
T = T + P × θ
(
)
J
A
D
JA
The power dissipated in the package (PD) is the sum of the quiescent
power dissipation and the power dissipated in the package due to the
load drive for all outputs. The quiescent power is the voltage between
the supply pins (VS) multiplied by the quiescent current (IS). Assuming
the load (RL) is referenced to midsupply, then the total drive power is
VS / 2 × IOUT, some of which is dissipated in the package and some
in the load (VOUT × IOUT). The difference between the total drive
power and the load power is the drive power dissipated in the package.
Figure 2 shows the maximum safe power dissipation in the package
versus the ambient temperature for the SOIC-8 (125°C/W), SC70-5
(210°C/W), and SOT23-8 (160°C/W) package on a JEDEC standard
four-layer board. ꢀJA values are approximations.
OUTPUT SHORT CIRCUIT
Shorting the output to ground or drawing excessive current from
the AD8038/AD8039 will likely cause a catastrophic failure.
PD = quiescent power + (total drive power – load power)
2
PD = V × I + V / 2 × V
/ RL – V
/ RL
(
)
(
)
]
[
[
]
[
S
S
S
OUT
OUT
]
ORDERING GUIDE
Model
AD8038AR
Temperature Range
Package Description Package Outline
Branding Information
–40°C to +85°C
–40°C to +85°C
–40°C to +85°C
–40°C to +85°C
–40°C to +85°C
–40°C to +85°C
–40°C to +85°C
–40°C to +85°C
–40°C to +85°C
8-Lead SOIC
8-Lead SOIC
8-Lead SOIC
5-Lead SC70
5-Lead SC70
8-Lead SOIC
8-Lead SOIC
8-Lead SOIC
8-Lead SOT23
8-Lead SOT23
SO-8
SO-8
SO-8
KS-5
KS-5
SO-8
SO-8
SO-8
RT-8
RT-8
AD8038AR-REEL
AD8038AR-REEL7
AD8038AKS-REEL
AD8038AKS-REEL7
AD8039AR
AD8039AR-REEL
AD8039AR-REEL7
AD8039ART-REEL*
HUA
HUA
HYA
HYA
AD8039ART-REEL7* –40°C to +85°C
*Under development.
CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily
accumulate on the human body and test equipment and can discharge without detection.
Although the AD8038/AD8039 features proprietary ESD protection circuitry, permanent damage
may occur on devices subjected to high energy electrostatic discharges. Therefore, proper ESD
precautions are recommended to avoid performance degradation or loss of functionality.
WARNING!
ESD SENSITIVE DEVICE
–4–
REV. B
Typical Performance Characteristics–AD8038/AD8039
(Default Conditions: ؎5 V, CL = 5 pF, G = +2, RG = RF = 1 kΩ, RL = 2 kΩ, VO = 2 V p-p, Frequency = 1 MHz, TA = 25؇C.)
24
21
18
15
12
9
7
6
5
4
3
2
1
0
7
6
5
4
3
2
1
0
V
= ؎1.5V
G = +10
G = +5
S
R
= 2k⍀
L
V
= ؎2.5V
S
V
= ؎5V
S
G = +2
G = +1
6
R
= 500⍀
L
3
R
= 1k⍀
L
0
–3
–6
0.1
1
10
100
1000
0.1
1
10
100
1000
0.1
1
10
100
1000
FREQUENCY – MHz
FREQUENCY – MHz
FREQUENCY – MHz
TPC 1. Small Signal Frequency
Response for Various Gains,
TPC 2. Small Signal Frequency
Response for Various Supplies,
TPC 3. Small Signal Frequency
Response for Various RLOAD
,
V
OUT = 500 mV p-p
V
OUT = 500 mV p-p
VS = 5 V, VOUT = 500 mV p-p
7
8
8
R
= 2k⍀
R = 2k⍀
L
R
= 2k⍀
L
L
7
6
5
4
3
2
1
7
6
5
4
3
2
1
6
5
4
3
2
1
0
R
= 500⍀
R
= 500⍀
R = 500⍀
L
L
L
R
= 1k⍀
L
R
= 1k⍀
R
= 1k⍀
L
L
0
0.1
0
0.1
0.1
1
10
100
1000
1
10
100
1
10
100
FREQUENCY – MHz
FREQUENCY – MHz
FREQUENCY – MHz
TPC 4. Small Signal Frequency
Response for Various RLOAD
VS = 5 V, VOUT = 500 mV p-p
TPC 5. Large Signal Frequency
TPC 6. Large Signal Frequency
,
Response for Various RLOAD
VOUT = 3 V p-p, VS = 5 V
,
Response for Various RLOAD
VOUT = 4 V p-p, VS = 5 V
,
5
7
2
C
= 15pF
L
V
= 200mV
= 1V
OUT
C
= 15pF
L
4
3
1
V
OUT
5
3
1
C
= 10pF
L
0
–1
–2
–3
–4
–5
–6
2
1
C
= 10pF
L
0
V
= 500mV
= 2V
OUT
–1
–2
–3
–4
–5
C
= 5pF
L
–1
C
= 5pF
L
V
OUT
–3
–5
1
10
100
1000
1
10
100
1000
0.1
1
10
100
1000
FREQUENCY – MHz
FREQUENCY – MHz
FREQUENCY – MHz
TPC 7. Small Signal Frequency
Response for Various CLOAD
VOUT = 500 mV p-p, VS = 5 V,
G = +1
TPC 8. Small Signal Frequency
Response for Various CLOAD
VOUT = 500 mV p-p, VS = 5 V, G
+1
TPC 9. Frequency Response for
Various Output Voltage Levels
,
,
=
REV. B
–5–
AD8038/AD8039
(Default Conditions: ؎5 V, CL = 5 pF, G = +2, RG = RF = 1 kΩ, RL = 2 kΩ, VO = 2 V p-p, Frequency = 1 MHz, TA = 25؇C.)
9
6
3
80
70
60
50
40
30
20
10
0
180
135
90
–50
–55
R
= 500⍀ HD2
L
R
= 500⍀ HD3
L
–60
–65
–70
–75
–80
–85
–90
–40؇C
+25؇C
PHASE
GAIN
45
R
= 2k⍀ HD3
L
R
3
= 2k⍀ HD2
+85؇C
L
0
0
–10
–20
–3
0.1
–45
1000
1
2
4
5
6
7
8
9
10
1
10
100
1000
0.01
0.1
1
10
100
FREQUENCY – MHz
FREQUENCY – MHz
FREQUENCY – MHz
TPC 12. Harmonic Distortion vs.
Frequency for Various Loads,
VS = 5 V, VOUT = 2 V p-p, G = +2
TPC 11. Frequency Response
vs. Temperature, Gain = +2, VS
TPC 10. Open-Loop Gain and
Phase, VS = 5 V
=
–50
–60
–70
–80
–90
–100
5 V, VOUT = 2V p-p
–45
–50
G = +1 HD2
G = +1 HD2
G = +2 HD2
R
= 500⍀ HD2
L
–50
–55
–60
–65
–70
G = +2 HD2
–60
R
= 500⍀ HD3
L
–70
G = +2 HD3
G = +2 HD3
–80
R
= 2k⍀ HD3
L
–75
–80
–85
–90
R
3
= 2k⍀ HD2
L
G = +1 HD3
–90
G = +1 HD3
–100
1
2
3
4
5
6
7
8
9
10
1
2
3
4
5
6
7
8
9
10
1
2
4
5
6
7
8
9
10
FREQUENCY – MHz
FREQUENCY – MHz
FREQUENCY – MHz
TPC 13. Harmonic Distortion vs.
Frequency for Various Loads,
VS = 5 V, VOUT = 2 V p-p, G = +2
TPC 14. Harmonic Distortion vs.
Frequency for Various Gains,
VS = 5 V, VOUT = 2 V p-p
TPC 15. Harmonic Distortion vs.
Frequency for Various Gains,
VS = 5 V, VOUT = 2 V p-p
1000
100
10
–45
–40
10MHz HD2
10MHz HD2
–50
–55
10MHz HD3
5MHz HD2
5MHz HD3
5MHz HD2
5MHz HD3
10MHz HD3
–60
–70
–65
–75
1MHz HD3
1MHz HD2
1MHz HD3
–80
1MHz HD2
2.0
–85
–95
–90
1
–100
1.0
1.5
2.5
3.0
1
2
3
4
10
100
1k
10k 100k 1M 10M 100M
AMPLITUDE – V p-p
AMPLITUDE – V p-p
FREQUENCY – Hz
TPC 17. Harmonic Distortion vs.
Amplitude for Various Frequencies,
VS = 5 V, G = +2
TPC 16. Harmonic Distortion vs.
VOUT Amplitude for Various
Frequencies, VS = 5 V, G = +2
TPC 18. Input Voltage Noise vs.
Frequency
–6–
REV. B
AD8038/AD8039
(Default Conditions: ؎5 V, CL = 5 pF, G = +2, RG = RF = 1 kΩ, RL = 2 kΩ, VO = 2 V p-p, Frequency = 1 MHz, TA = 25؇C.)
100000
10000
1000
R
= 2k⍀
R
= 500⍀
L
L
R
= 500⍀
L
R
= 2k⍀
L
50mV/DIV
5ns/DIV
50mV/DIV
5ns/DIV
100
10
100
1000
10000 100000
1M
FREQUENCY – Hz
TPC 20. Small Signal Transient
TPC 21. Small Signal Transient
TPC 19. Input Current Noise vs.
Frequency
Response for Various RLOAD
VS = 5 V
,
Response for Various RLOAD
VS = 5 V
,
C
= 25pF WITH
L
R
= 500⍀
R = 2k⍀
L
C
= 25pF WITH
L
L
R
= 19.6⍀
SNUB
R
= 19.6⍀
SNUB
2.5V
C
= 5pF
C
= 5pF
L
L
C
= 10pF
L
C
= 10pF
L
500mV/DIV
5ns/DIV
50mV/DIV
5ns/DIV
50mV/DIV
5ns/DIV
TPC 23. Small Signal Transient
Response for Various Capacitive
Loads, VS = 5 V
TPC 24. Large Signal Transient
TPC 22. Small Signal Transient
Response for Various Capacitive
Loads, VS = 5 V
Response for Various RLOAD
VS = 5 V
,
C
= 10pF
L
R
= 2k⍀
C
= 25pF
R
= 500⍀
L
L
L
C
= 5pF
L
C
= 5pF
L
2.5V
1V/DIV
5ns/DIV
500mV/DIV
5ns/DIV
500mV/DIV
5ns/DIV
TPC 26. Large Signal Transient
Response for Various Capacitive
Loads, VS = 5 V
TPC 27. Large Signal Transient
Response for Various Capacitive
Loads, VS = 5 V
TPC 25. Large Signal Transient
Response for Various RLOAD
VS = 5 V
,
REV. B
–7–
AD8038/AD8039
(Default Conditions: ؎5 V, CL = 5 pF, G = +2, RG = RF = 1 kΩ, RL = 2 kΩ, VO = 2 V p-p, Frequency = 1 MHz, TA = 25؇C.)
V
= ؎5V
S
2mV/DIV
G = +2
= 2V p-p
IN
OUT
V
IN
OUT
ERROR
VOLTAGE
+0.1%
0
t = 0
OUT
–0.1%
V
IN
INPUT 1V/DIV
OUTPUT 2V/DIV
0.5V/DIV
5ns/DIV
50ns/DIV
2V/DIV
50ns/DIV
TPC 28. Input Overdrive
Recovery, Gain = +1
TPC 29. Output Overdrive
Recovery, Gain = +2
TPC 30. 0.1% Settling Time
VOUT = 2 V p-p
–10
–20
–30
–40
–50
–60
–70
–10
–20
–30
–40
–50
–60
–70
–80
1000
100
10
V
= +5V
S
SIDE B
V
= ؎5V
S
SIDE A
1
–80
–90
V
= ؎5V
S
V
= +5V
S
0.1
0.01
–100
1
10
100
1000
0.1
1
10
FREQUENCY – MHz
1000
100
0.1
1
10
100
1000
FREQUENCY – MHz
FREQUENCY – MHz
TPC 31. AD8039 Crosstalk,
VIN = 1 V p-p, Gain = +1
TPC 32. CMRR vs. Frequency,
VIN = 1 V p-p
TPC 33. Output Impedance vs.
Frequency
10
0
9
8
1.25
1.00
0.75
0.50
0.25
V
= ؎5V
S
–10
7
6
–20
–30
–40
–50
–60
–70
–80
–90
–PSRR
5
4
3
2
1
0
+PSRR
V
= +5V
S
0
0
0.001
0.01
1
10
100
1000
2
4
6
8
10
12
0
100
200
300
– ⍀
400
500
SUPPLYVOLTAGE –V
FREQUENCY – MHz
R
LOAD
TPC 35. Output Swing vs. Load
Resistance
TPC 34. PSRR vs. Frequency
TPC 36. AD8038 Supply Current vs.
Supply Voltage
–8–
REV. B
AD8038/AD8039
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
Input Capacitance
Along with bypassing and ground, high speed amplifiers can be
sensitive to parasitic capacitance between the inputs and ground. A
few pF of capacitance will reduce the input impedance at high
frequencies, in turn increasing the amplifiers’ gain, causing peaking
of the frequency response, or even oscillations if severe enough.
It is recommended that the external passive components that
are connected to the input pins be placed as close as possible to
the inputs to avoid parasitic capacitance. The ground and power
planes must be kept at a distance of at least 0.05 mm from the
input pins on all layers of the board.
Output Capacitance
0.1
1.0
10
100
1000
To a lesser extent, parasitic capacitances on the output can cause
peaking of the frequency response. There are two methods to
minimize this effect.
FREQUENCY – MHz
TPC 37. AD8038 Input-Output Isolation (G = +2,
RL = 2 kΩ, VS = 5V
1. Put a small value resistor in series with the output to isolate
the load capacitor from the amp’s output stage; see TPCs 7,
8, 22, and 23.
LAYOUT, GROUNDING, AND BYPASSING
CONSIDERATIONS
2. Increase the phase margin with higher noise gains or add a pole
with a parallel resistor and capacitor from –IN to the output.
Disable
The AD8038 in the SOIC-8 package provides a disable feature.
This feature disables the input from the output (see TPC 37 for
input-output isolation) and reduces the quiescent current from
typically 1 mA to 0.2 mA. When the DISABLE node is pulled
below 4.5 V from the positive supply rail, the part becomes
disabled. In order to enable the part, the DISABLE node needs
to be pulled up to above 2.5 V below the positive rail.
Input-to-Output Coupling
The input and output signal traces should not be parallel to
minimize capacitive coupling between the inputs and outputs,
avoiding any positive feedback.
APPLICATIONS
Low Power ADC Driver
Power Supply Bypassing
Power supply pins are actually inputs, and care must be taken
so that a noise-free stable dc voltage is applied. The purpose
of bypass capacitors is to create low impedances from the sup-
ply to ground at all frequencies, thereby shunting or filtering a
majority of the noise.
1k⍀
2.5V
+5V
8
0.1F
50⍀
10F
3V
0.1F
10F
1k⍀
1k⍀
1k⍀
REF
VINA
3
2
Decoupling schemes are designed to minimize the bypassing
impedance at all frequencies with a parallel combination of
capacitors. 0.01 µF or 0.001 µF (X7R or NPO) chip capacitors
are critical and should be as close as possible to the amplifier
package. Larger chip capacitors, such as the 0.1 µF capacitor,
can be shared among a few closely spaced active components in
the same signal path. A 10 µF tantalum capacitor is less critical
for high frequency bypassing and, in most cases, only one per
board is needed at the supply inputs.
1
V
IN
0V
1k⍀
AD9203
AD8039
1k⍀
6
5
7
VINB
50⍀
4
1k⍀
10F
0.1F
Grounding
A ground plane layer is important in densely packed PC boards
to spread the current minimizing parasitic inductances.
However, an understanding of where the current flows in a circuit
is critical to implementing effective high speed circuit design.
The length of the current path is directly proportional to the
magnitude of parasitic inductances, and thus the high frequency
impedance of the path. High speed currents in an inductive
ground return will create an unwanted voltage noise.
–5V
1k⍀
Figure 3. Schematic to Drive AD9203 with the AD8039
Differential A/D Driver
The AD9203 is a low power (125 mW on a 5 V supply) 40 MSPS
10-bit converter. This represents a breakthrough in power/speed
for ADCs. As such, the low power, high performance AD8039
is an appropriate choice of amplifier to drive it.
The length of the high frequency bypass capacitor leads are most
critical. A parasitic inductance in the bypass grounding will
work against the low impedance created by the bypass capacitor.
Place the ground leads of the bypass capacitors at the same
physical location. Because load currents flow from the supplies
as well, the ground for the load impedance should be at the
same physical location as the bypass capacitor grounds. For the
larger value capacitors, which are intended to be effective at
lower frequencies, the current return path distance is less critical.
In low supply voltage applications, differential analog inputs are
needed to increase the dynamic range of the ADC inputs.
Differential driving can also reduce second and other even-order
distortion products. The AD8039 can be used to make a
dc-coupled, single-ended-to-differential driver for one of these
ADCs. Figure 3 is a schematic of such a circuit for driving an
AD9203, a 10-bit, 40 MSPS ADC.
REV. B
–9–
AD8038/AD8039
The AD9203 works best when the common-mode voltage at the
input is at the midsupply or 2.5 V. The output stage design of
the AD8039 makes it ideal for driving these types of ADCs.
R
1k⍀
F
680pF
+2.5V
In this circuit, one of the op amps is configured in the inverting
mode, while the other is in the noninverting mode. However, to
provide better bandwidth matching, each op amp is configured
for a noise gain of +2. The inverting op amp is configured for a
gain of –1, while the noninverting op amp is configured for a
gain of +2. Each has a very similar ac response. The input signal
to the noninverting op amp is divided by 2 to normalize its
voltage level and make it equal to the inverting output.
10F
0.1F
R1
R2
R3
V
AD8038
OUT
200k⍀
499k⍀ 49.9k⍀
R5
V
IN
49.9k⍀
C1
100pF
C3
33pF
R4
49.9k⍀
10F
0.1F
–2.5V
Figure 4. Low-Pass Filter for Video
The outputs of the op amps are centered at 2.5 V, which is the
midsupply level of the ADC. This is accomplished by first taking
the 2.5 V reference output of the ADC and dividing it by 2 with a
pair of 1 kΩ resistors. The resulting 1.25 V is applied to each op
amp’s positive input. This voltage is then multiplied by the gain of
the op amps to provide a 2.5 V level at each output.
Figure 5 shows the frequency response of this filter. The response
is down 3 dB at 6 MHz, so it passes the video band with little
attenuation. The rejection at 27 MHz is 45 dB, which provides
more than a factor of 100 in suppression of the clock components
at this frequency.
10
Low Power Active Video Filter
Some composite video signals derived from a digital source
contain clock feedthrough that can limit picture quality. Active
filters made from op amps can be used in this application, but
they will consume 25 mW to 30 mW for each channel. In
power-sensitive applications, this can be too much, requiring the
use of passive filters that can create impedance matching prob-
lems when driving any significant load.
0
–10
–20
–30
–40
–50
–60
The AD8038 can be used to make an effective low-pass active
filter that consumes one-fifth of the power consumed by an
active filter made from an op amp. Figure 4 shows a circuit that
uses an AD8038 to create a single 2.5 V supply, three-pole
Sallen-Key filter. This circuit uses a single RC pole in front
of a standard two-pole active section.
0.1
1
10
FREQUENCY – MHz
100
Figure 5. Video Filter Response
–10–
REV. B
AD8038/AD8039
OUTLINE DIMENSIONS
Dimensions shown in inches and (mm)
Dimensions shown in inches and (mm)
5-Lead SC70
(KS-5)
8-Lead Plastic Surface Mount
(RT-8)*
0.087 (2.20)
0.071 (1.80)
0.122 (3.10)
0.110 (2.80)
4
3
5
1
8
7
2
6
3
5
4
0.053 (1.35)
0.045 (1.15)
0.094 (2.40)
0.071 (1.80)
0.071 (1.80)
0.059 (1.50)
0.112 (2.80)
2
PIN 1
0.016 (0.40)
0.004 (0.10)
PIN 1
0.026 (0.65) BSC
0.026
(0.65) BSC
0.039 (1.00)
0.031 (0.80)
0.043 (1.10)
0.031 (0.80)
0.077
(1.95)
BSC
0.012 (0.30)
0.006 (0.15)
0.012 (0.30)
0.004 (0.10)
0.007 (0.18)
0.004 (0.10)
0.004 (0.10)
0.000 (0.00)
SEATING
PLANE
0.051 (1.30)
0.035 (0.90)
0.057 (1.45)
0.035 (0.90)
10؇
0؇
0.022 (0.55)
0.014 (0.35)
0.009 (0.23)
0.003 (0.08)
0.006 (0.15)
0.000 (0.00)
0.015 (0.38)
0.009 (0.22)
SEATING
PLANE
*Not yet released.
Dimensions shown in millimeters and (inches)
8-Lead Plastic SOIC
(R-8)
5.00 (0.1968)
4.80 (0.1890)
8
1
5
4
6.20 (0.2440)
5.80 (0.2284)
4.00 (0.1574)
3.80 (0.1497)
PIN 1
0.50 (0.0196)
0.25 (0.0099)
1.27 (0.0500)
BSC
؋
45؇ 1.75 (0.0688)
1.35 (0.0532)
COPLANARITY
0.25 (0.0098)
0.10 (0.0040)
8؇
0؇ 1.27 (0.0500)
0.51 (0.0201)
0.33 (0.0130)
0.25 (0.0098)
0.19 (0.0075)
SEATING
PLANE
0.40 (0.0157)
CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS
(IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR
REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN
COMPLIANT TO JEDEC STANDARDS MS-012 AA
REV. B
–11–
AD8038/AD8039
Revision History
Location
Page
5/02–Data Sheet changed from REV. A to REV. B.
Add part number AD8038 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . UNIVERSAL
Changes to Product Title . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1
Changes to FEATURES . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1
Changes to PRODUCT DESCRIPTION . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1
Changes to CONNECTION DIAGRAM . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1
Update to SPECIFICATIONS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2
Update to MAXIMUM POWER DISSIPATION . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4
Update to OUTPUT SHORT CIRCUIT . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4
Update to ORDERING GUIDE . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4
Change to FIGURE 2 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4
Change to TPC 2 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 5
Change to TPC 18 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 6
Change to TPC 27 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 7
Change to TPC 29 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 8
Change to TPC 30 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 8
Change to TPC 31 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 8
Added TPC 36 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 8
Added TPC 37 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 9
Edits to Low Power Active Video Filter . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 10
Change to Figure 4 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 10
Data Sheet changed from REV. 0 to REV. A.
Changes to FEATURES . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1
Update SPECIFICATIONS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2, 3
Edits to TPC 19 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 7
–12–
REV. B
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