TS1102-200EG5TP [TOUCHSTONE]
A 1μA, 200μVOS SOT23 Precision Current-Sense Amplifier; 一个1μA ， 200μVOS SOT23高精度电流检测放大器
| 型号： | TS1102-200EG5TP |
| 厂家： | 
TOUCHSTONE SEMICONDUCTOR INC |
| 描述： | A 1μA, 200μVOS SOT23 Precision Current-Sense Amplifier |
| 文件： | 总11页 (文件大小：787K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
TS1102
A 1µA, 200µVOS SOT23 Precision Current-Sense Amplifier
FEATURES
DESCRIPTION
♦ Improved Electrical Performance over the
MAX9938 and the MAX9634
♦ Ultra-Low Supply Current: 1μA
♦ Wide Input Common Mode Range: +2V to +25V
♦ Low Input Offset Voltage: 200μV (max)
♦ Low Gain Error: 0.5% (max)
♦ Voltage Output
The voltage-output TS1102 current-sense amplifiers
are form-factor identical and electrical improvements
to the MAX9938 and the MAX9634 current-sense
amplifiers. The TS1102 is the latest addition to the
TS1100
family
of
current-sense
amplifiers.
Consuming a very low 1μA supply current, the
TS1102 high-side current-sense amplifiers combine a
200-µV (max) VOS and a 0.5% (max) gain error for
cost-sensitive applications. For all high-side current-
sensing applications, the TS1102 features a wide
input common-mode voltage range from 2V to 25V.
♦ Four Gain Options Available:
TS1102-25: Gain = 25V/V
TS1102-50: Gain = 50V/V
TS1102-100: Gain = 100V/V
TS1102-200: Gain = 200V/V
♦ 5-Pin SOT23 Packaging
The SOT23 package makes the TS1102 an ideal
choice for pcb-area-critical, low-current, high-
accuracy current-sense applications in all battery-
powered, remote or hand-held portable instruments.
APPLICATIONS
Notebook Computers
Current-Shunt Measurement
Power Management Systems
Battery Monitoring
All TS1102s are specified for operation over the
-40°C to +105°C extended temperature range.
Motor Control
Load Protection
Smart Battery Packs/Chargers
TYPICAL APPLICATION CIRCUIT
Input Offset Voltage Histogram
35
30
25
20
15
10
5
0
10
20
30
40
0
50
INPUT OFFSET VOLTAGE - µV
PART
GAIN OPTION
25 V/V
TS1102-25
TS1102-50
TS1102-100
TS1102-200
50 V/V
100 V/V
200 V/V
The Touchstone Semiconductor logo is a registered
trademark of Touchstone Semiconductor, Incorporated.
Page 1
© 2011 Touchstone Semiconductor, Inc. All rights reserved.
TS1102
ABSOLUTE MAXIMUM RATINGS
RS+, RS- to GND..............................................-0.3V to +27V
OUT to GND........................................................-0.3V to +6V
RS+ to RS-..................................................................... ±27V
Short-Circuit Duration: OUT to GND .................... Continuous
Continuous Input Current (Any Pin) ............................ ±20mA
Continuous Power Dissipation (TA = +70°C)
Operating Temperature Range .................... -40°C to +105°C
Junction Temperature ................................................ +150°C
Storage Temperature Range ....................... -65°C to +150°C
Lead Temperature (Soldering, 10s) ........................... +300°C
Soldering Temperature (Reflow) ............................ +260°C
5-Pin SOT23 (Derate at 3.9mW/°C above +70°C).. 312mW
Electrical and thermal stresses beyond those listed under “Absolute Maximum Ratings” may cause permanent damage to the device. These
are stress ratings only and functional operation of the device at these or any other condition beyond those indicated in the operational sections
of the specifications is not implied. Exposure to any absolute maximum rating conditions for extended periods may affect device reliability and
lifetime.
PACKAGE/ORDERING INFORMATION
ORDER NUMBER PART MARKING CARRIER QUANTITY
TS1102-25EG5TP
TS1102-25EG5T
TS1102-50EG5TP
TS1102-50EG5T
TS1102-100EG5TP
TS1102-100EG5T
TS1102-200EG5TP
TS1102-200EG5T
Tape & Reel
Tape & Reel 3000
Tape & Reel -----
Tape & Reel 3000
Tape & Reel -----
Tape & Reel 3000
Tape & Reel -----
Tape & Reel 3000
-----
TADS
TADT
TADU
TADV
Lead-free Program: Touchstone Semiconductor supplies only lead-free packaging.
Consult Touchstone Semiconductor for products specified with wider operating temperature ranges.
Page 2
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TS1102
ELECTRICAL CHARACTERISTICS
VRS+ = VRS- = 3.6V; VSENSE = (VRS+ - VRS-) = 0V; COUT = 47nF; TA = -40°C to +105°C, unless otherwise noted.
Typical values are at TA = +25°C. See Note 1
PARAMETER
SYMBOL
CONDITIONS
TA = +25°C
MIN
TYP
0.68
MAX
0.85
1.0
1.0
1.2
UNITS
Supply Current (Note 2)
ICC
μA
TA = +25°C
VRS+ = 25V
Common-Mode Input Range
Common-Mode Rejection
Ratio
VCM
Guaranteed by CMRR
2V < VRS+ < 25V
TA = +25°C
2
25
V
CMRR
120
150
±30
dB
±200
±300
Input Offset Voltage (Note 3)
VOS
G
μV
TS1102-25
TS1102-50
TS1102-100
TS1102-200
TA = +25°C
25
50
100
200
±0.1
Gain
V/V
%
±0.5
±0.6
13.2
26.4
5
Gain Error (Note 4)
GE
TS1102-25/50/100
TS1102-200
7.0
14.0
10
20
Output Resistance (Note 5)
ROUT
kΩ
Gain = 25
Gain = 50
Gain = 100
10
20
OUT Low Voltage
VOL
mV
Gain = 200
40
OUT High Voltage (Note 6)
Output Settling Time
VOH
tS
VOH = VRS- - VOUT
TS1102-25/50/100
TS1102-200
0.05
2.2
4.3
0.2
V
ms
ms
1% final value, VOUT = 3V
Note 1: All devices are 100% production tested at TA = +25°C. All temperature limits are guaranteed by product
characterization.
Note 2: Extrapolated to VOUT = 0. ICC is the total current into the RS+ and the RS- pins.
Note 3: Input offset voltage VOS is extrapolated from VOUT with VSENSE set to 1mV.
Note 4: Gain error is calculated by applying two values for VSENSE and then calculating the error of the actual slope vs. the
ideal transfer characteristic:
For GAIN = 25, the applied VSENSE is 20mV and 120mV.
For GAIN = 50, the applied VSENSE is 10mV and 60mV.
For GAIN = 100, the applied VSENSE is 5mV and 30mV.
For GAIN = 200, the applied VSENSE is 2.5mV and 15mV.
Note 5: The device is stable for any capacitive load at VOUT
.
Note 6: VOH is the voltage from VRS- to VOUT with VSENSE = 3.6V/GAIN.
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TS1102
TYPICAL PERFORMANCE CHARACTERISTICS
VRS+ = VRS- = 3.6V; TA = +25°C, unless otherwise noted.
Gain Error Histogram
Input Offset Voltage Histogram
35
30
30
25
20
15
10
25
20
15
10
5
5
0
0
-0.4
-0.2
0
0.2
0.4
10
20
30
40
50
0
GAIN ERROR - %
INPUT OFFSET VOLTAGE - µV
Input Offset Voltage vs Common-Mode Voltage
Supply Current vs Temperature
40
1
0.8
0.6
0.4
0.2
0
35
30
25
20
25V
2V
3.6V
-40 -15
10
35
60
85
20
25
30
110
0
5
10
15
TEMPERATURE - °C
SUPPLY VOLTAGE - Volt
Supply Current vs Common-Mode Voltage
Input Offset Voltage vs Temperature
80
60
40
20
0
1
0.8
0.6
0.4
0.2
0
-20
-40
10
110
0
5
10
20
25
30
-40 -15
35
60
85
15
SUPPLY VOLTAGE - Volt
TEMPERATURE - °C
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TS1102
TYPICAL PERFORMANCE CHARACTERISTICS
VRS+ = VRS- = 3.6V; TA = +25°C, unless otherwise noted.
Gain Error vs Common-Mode Voltage
Gain Error vs. Temperature
0.5
0.4
0.3
0.2
0.1
0
0.3
0.2
0.1
0
-0.1
110
-40 -15
10
35
60
85
0
5
10
15
25
30
20
SUPPLY VOLTAGE - Volt
TEMPERATURE - °C
VOUT vs VSENSE @ Supply = 2V
VOUT vs VSENSE @ Supply = 3.6V
2
4
3.5
3
G = 100
1.8
1.6
1.4
1.2
G = 50
G = 100
G = 50
2.5
2
G = 25
1.0
0.8
0.6
0.4
0.2
0
G = 25
1.5
1
0.5
0
0
20
60
80
0
50
100
VSENSE- mV
150
40
100
VSENSE- mV
Common-Mode Rejection vs Frequency
Small-Signal Gain vs Frequency
5
0
0
-20
G = 50
G = 50, 100
-5
-40
-60
G = 100
G = 25
-10
-15
-20
-25
G = 25
-80
-100
-120
-140
-30
-35
0.001 0.01 0.1
1
10
100 1000
0.001 0.01 0.1
10
100 1000
1
FREQUENCY - kHz
FREQUENCY - kHz
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TS1102
TYPICAL PERFORMANCE CHARACTERISTICS
VRS+ = VRS- = 3.6V; TA = +25°C, unless otherwise noted.
Large-Signal Pulse Response, Gain = 50
Small-Signal Pulse Response, Gain = 50
200µs/DIV
200µs/DIV
Large-Signal Pulse Response, Gain = 25
Small-Signal Pulse Response, Gain = 25
200µs/DIV
200µs/DIV
Small-Signal Pulse Response, Gain = 100
Large-Signal Pulse Response, Gain = 100
200µs/DIV
200µs/DIV
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TS1102
PIN FUNCTIONS
PIN
SOT23
LABEL
FUNCTION
5
4
1, 2
3
RS+
RS-
GND
OUT
External Sense Resistor Power-Side Connection
External Sense Resistor Load-Side Connection
Ground. Connect these pins to analog ground.
Output Voltage. VOUT is proportional to VSENSE = VRS+ - VRS-
BLOCK DIAGRAM
DESCRIPTION OF OPERATION
The internal configuration of the TS1102 – a
unidirectional high-side, current-sense amplifier - is
based on a commonly-used operational amplifier (op
amp) circuit for measuring load currents (in one
direction) in the presence of high-common-mode
voltages. In the general case, a current-sense
amplifier monitors the voltage caused by a load
current through an external sense resistor and
generates an output voltage as a function of that load
current. Referring to the typical application circuit on
Page 1, the inputs of the op-amp-based circuit are
connected across an external RSENSE resistor that
is used to measure load current. At the non-inverting
input of the TS1102 (the RS+ terminal), the applied
voltage is ILOAD x RSENSE. Since the RS- terminal is
the non-inverting input of the internal op amp, op-amp
feedback action forces the inverting input of the
internal
op
amp
to
the
same
potential
(ILOAD x RSENSE). Therefore, the voltage drop across
RSENSE (VSENSE) and the voltage drop across RGAIN
(at the RS+ terminal) are equal. To minimize any
additional error because of op-amp input bias current
mismatch, both RGAINs are the same value.
Since the internal p-channel FET’s source is
connected to the inverting input of the internal op
amp and since the voltage drop across RGAIN is the
same as the external VSENSE, op amp feedback action
drives the gate of the FET such that the FET’s drain-
source current is equal to:
VSEꢃSE
ꢀꢁS
ꢂ
RꢄAꢀꢃ
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TS1102
or
Table 1: Internal Gain Setting Resistors (Typical
Values)
ꢀLꢅAꢁ x RSEꢃSE
ꢀꢁS
ꢂ
RꢄAꢀꢃ
GAIN (V/V) RGAIN (Ω) ROUT (Ω) Part Number
25
50
100
200
400
200
100
100
10k
10k
10k
20k
TS1102-25
TS1102-50
TS1102-100
TS1102-200
Since the FET’s drain terminal is connected to ROUT
the output voltage of the TS1102 at the OUT
terminal is, therefore;
,
RꢅꢆT
VꢅꢆT ꢂ ꢀLꢅAꢁ x RSEꢃSE
x
To achieve its very-low input offset voltage
performance over temperature, VSENSE voltage,
and power supply voltage, the design of the
RꢄAꢀꢃ
The current-sense amplifier’s gain accuracy is
therefore the ratio match of ROUT to RGAIN. For each
of the four gain options available, Table 1 lists the
values for ROUT and RGAIN. The TS1102’s output
stage is protected against input overdrive by use of
an output current-limiting circuit of 3mA (typical) and
a 7V internal clamp protection circuit.
TS1102’s amplifier is chopper-stabilized,
a
commonly-used technique to reduce significantly the
input offset voltage of amplifiers. This method,
however, does employ the use of sampling
techniques and therefore residue of the TS1102’s
10kHz internal clock is contained in the TS1102’s
output voltage spectrum.
APPLICATIONS INFORMATION
Therefore,
Choosing the Sense Resistor
VOUT(max) = VRS+(min) - VSENSE(max) – VOH(max)
Selecting the optimal value for the external RSENSE
is based on the following criteria and for each
commentary follows:
and
VꢅꢆT ꢀmaxꢁ
RSEꢃSE
ꢂ
1) RSENSE Voltage Loss
2) VOUT Swing vs. Applied Input Voltage at VRS+
and Desired VSENSE
ꢄAꢀꢃ ꢇ ꢀLꢅAꢁꢀmaxꢁ
where the full-scale VSENSE should be less than
VOUT(MAX)/ꢄAꢀꢃ at the application’s minimum RS+
terminal voltage. For best performance with a 3.6V
power supply, RSENSE should be chosen to
generate a VSENSE of: a) 120mV (for the 25V/V GAIN
option), b) 60mV (for the 50V/V GAIN option), c)
30mV (for the 100V/V GAIN option), or d) 15mV (for
the 200V/V GAIN option) at the full-scale ILOAD(MAX)
current in each application. For the case where the
minimum power supply voltage is higher than 3.6V,
each of the four full-scale VSENSEs above can be
increased.
3) Total ILOAD Accuracy
4) Circuit Efficiency and Power Dissipation
5) RSENSE Kelvin Connections
6) Sense Resistor Composition
1) RSENSE Voltage Loss
For lowest IR voltage loss in RSENSE, the smallest
usable value for RSENSE should be selected.
2) VOUT Swing vs. Applied Input Voltage at VRS+
and Desired VSENSE
3) Total ILOAD Accuracy
As there is no separate power supply pin for the
TS1102, the circuit draws its power from the applied
voltage at both its RS+ and RS- terminals.
Therefore, the signal voltage at the OUT terminal is
bounded by the minimum supply voltage applied to
the TS1102.
In
the
TS1102’s
linear
region
where
VOUT < VOUT(MAX), there are two specifications related
to the circuit’s accuracy: a) the TS1102’s input offset
voltage (VOS = 200μV, max) and b) its gain error
(GE(max) = 0.5%).
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TS1102
An expression for the TS1102’s total output voltage
6) RSENSE Composition
(+ error) is given by:
Current-shunt resistors are made available in metal
film, metal strip, and wire-wound constructions.
Wire-wound current-shunt resistors are constructed
with wire spirally wound onto a core. As a result,
these types of current shunt resistors exhibit the
largest self inductance. In applications where the
load current contains high-frequency transients,
metal film or metal strip current sense resistors are
recommended.
VOUT = [GAIN x (1 ± GE) x VSENSE] ± (GAIN x VOS)
A large value for RSENSE permits the use of smaller
load currents to be measured more accurately
because the effects of offset voltages are less
significant when compared to larger VSENSE
voltages. Due care though should be exercised as
previously mentioned with large values of RSENSE.
4) Circuit Efficiency and Power Dissipation
Internal Noise Filter
IR losses in RSENSE can be large especially at high
load currents. It is important to select the smallest,
usable RSENSE value to minimize power dissipation
and to keep the physical size of RSENSE small. If
the external RSENSE is allowed to dissipate
significant power, then its inherent temperature
coefficient may alter its design center value, thereby
reducing load current measurement accuracy.
Precisely because the TS1102’s input stage was
designed to exhibit a very low input offset voltage,
small RSENSE values can be used to reduce power
dissipation and minimize local hot spots on the pcb.
In power management and motor control
applications, current-sense amplifiers are required to
measure load currents accurately in the presence of
both externally-generated differential and common-
mode noise. An example of differential-mode noise
that can appear at the inputs of a current-sense
amplifier is high-frequency ripple. High-frequency
ripple – whether injected into the circuit inductively
or capacitively - can produce a differential-mode
voltage drop across the external current-shunt
resistor (RSENSE). An example of externally-
generated, common-mode noise is the high-
frequency output ripple of a switching regulator that
can result in common-mode noise injection into both
inputs of a current-sense amplifier.
5) RSENSE Kelvin Connections
For optimal VSENSE accuracy in the presence of large
load currents, parasitic pcb track resistance should
be minimized. Kelvin-sense pcb connections
Even though the load current signal bandwidth is
DC, the input stage of any current-sense amplifier
can rectify unwanted, out-of-band noise that can
result in an apparent error voltage at its output. This
rectification of noise signals occurs because all
amplifier input stages are constructed with
transistors that can behave as high-frequency signal
detectors in the same way pn-junction diodes were
used as RF envelope detectors in early radio
designs. Against common-mode injected noise, the
amplifier’s internal common-mode rejection is
usually sufficient.
Figure 1: Making PCB Connections to the Sense
To counter the effects of externally-injected noise, it
has always been good engineering practice to add
external low-pass filters in series with the inputs of a
current-sense amplifier. In the design of discrete
current-sense amplifiers, resistors used in the
external low-pass filters were incorporated into the
circuit’s overall design so errors because of any
input-bias current-generated offset voltage errors
and gain errors were compensated.
Resistor.
between RSENSE and the TS1102’s RS+ and RS-
terminals are strongly recommended. The drawing in
Figure 1 illustrates the connections between the
current-sense amplifier and the current-sense
resistor. The pcb layout should be balanced and
symmetrical to minimize wiring-induced errors. In
addition, the pcb layout for RSENSE should include
good thermal management techniques for optimal
RSENSE power dissipation.
With the advent of monolithic current-sense
amplifiers, like the TS1102, the addition of external
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TS1102
low-pass filters in series with the current-sense
amplifier’s inputs only introduces additional offset
voltage and gain errors. To minimize or eliminate
altogether the need for external low-pass filters and
to maintain low input offset voltage and gain errors,
the TS1102 incorporates a 50-kHz (typ), 2nd-order
differential low-pass filter as shown in the TS1102’s
Block Diagram.
the RS+ and the RS- input terminals of the TS1102
should be short and symmetric. Also recommended
are a ground plane and surface mount resistors and
capacitors.
Using the TS1102 in Bidirectional Load Current
Applications
In many battery-powered systems, it is oftentimes
necessary to monitor a battery’s discharge and
Optional Output Filter Capacitor
charge currents. To perform this function,
a
bidirectional current-sense amplifier is required. The
circuit illustrated in Figure 2 shows how two
TS1102s can be configured as a bidirectional
current-sense amplifier. As shown in the figure, the
RS+/RS- input pair of TS1102 #2 is wired opposite
in polarity with respect to the RS+/RS- connections
of TS1102 #1. Current-sense amplifier #1 therefore
measures the discharge current and current-sense
amplifier #2 measures the charge current. Note that
both output voltages are measured with respect to
GND. When the discharge current is being
measured, VOUT1 is active and VOUT2 is zero; for the
case where charge current is being measured, VOUT1
is zero, and VOUT2 is active.
If the TS1102 is part of a signal acquisition system
where its OUT terminal is connected to the input of
an ADC with an internal, switched-capacitor track-
and-hold circuit, the internal track-and-hold’s
sampling capacitor can cause voltage droop at VOUT
.
A 22nF to 100nF good-quality ceramic capacitor
from the OUT terminal to GND forms a low-pass
filters with the TS1102’s ROUT and should be used to
minimize voltage droop (holding VOUT constant
during the sample interval. Using a capacitor on the
OUT terminal will also reduce the TS1102’s small-
signal bandwidth as well as band-limiting amplifier
noise.
PC Board Layout and Power-Supply Bypassing
For optimal circuit performance, the TS1102 should
be in very close proximity to the external current-
sense resistor and the pcb tracks from RSENSE to
Figure 2: Using Two TS1102s for Bidirectional Load Current Detection
Page 10
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TS1102
PACKAGE OUTLINE DRAWING
5-Pin SOT23 Package Outline Drawing
(N.B., Drawings are not to scale)
NOTES:
1. Dimensions and tolerances are as per ANSI Y14.5M, 1982.
2. Package surface to be matte finish VDI 11~13.
5
2.80 - 3.00
3. Die is facing up mold and facing down for trim/form,
ie, reverse trim/form.
0.950
0.95
TYP
TYP
4. The foot length measuring is based on the gauge plane method.
5.Dimensions are exclusive of mold flash and gate burr.
6. Dimensions are exclusive of solder plating.
7. All dimensions are in mm.
8. This part is compliant with EIAJ spec. and JEDEC MO-178 AA
0.30 - 0.50
9. Lead span/stand off height/coplanarity are considered as special
characteristic.
1.90 Max
10º TYP
1.50 – 1.75
10º TYP
0.09 – 1.45
0.60 – 0.80
0.90 - 1.30
0º- 8º
0.25
0.00 - 0.15
0.09 - 0.20
5
0.30 - 0.55
Gauge Plane
10º TYP
10º TYP
0.10 Max
0.50 – 0.70
0.50 Max
0.30 Min
0.20 Max
0.09 Min
Information furnished by Touchstone Semiconductor is believed to be accurate and reliable. However, Touchstone Semiconductor does not
assume any responsibility for its use nor for any infringements of patents or other rights of third parties that may result from its use, and all
information provided by Touchstone Semiconductor and its suppliers is provided on an AS IS basis, WITHOUT WARRANTY OF ANY KIND.
Touchstone Semiconductor reserves the right to change product specifications and product descriptions at any time without any advance
notice. No license is granted by implication or otherwise under any patent or patent rights of Touchstone Semiconductor. Touchstone
Semiconductor assumes no liability for applications assistance or customer product design. Customers are responsible for their products and
applications using Touchstone Semiconductor components. To minimize the risk associated with customer products and applications,
customers should provide adequate design and operating safeguards. Trademarks and registered trademarks are the property of their
respective owners.
Touchstone Semiconductor, Inc.
Page 11
630 Alder Drive, Milpitas, CA 95035
+1 (408) 215 - 1220 ▪ www.touchstonesemi.com
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