TDA7360 [STMICROELECTRONICS]
22W BRIDGE / STEREO AUDIO AMPLIFIER WITH CLIPPING DETECTOR; 22W BRIDGE /立体声音频剪报检测放大器型号: | TDA7360 |
厂家: | ST |
描述: | 22W BRIDGE / STEREO AUDIO AMPLIFIER WITH CLIPPING DETECTOR |
文件: | 总22页 (文件大小:228K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
TDA7360
22W BRIDGE / STEREO AUDIO AMPLIFIER
WITH CLIPPING DETECTOR
VERYFEW EXTERNAL COMPONENTS
NO BOUCHEROT CELLS
NO BOOSTRAPCAPACITORS
HIGH OUTPUT POWER
NO SWITCH ON/OFF NOISE
VERYLOW STAND-BY CURRENT
FIXED GAIN (20dB STEREO)
PROGRAMMABLE TURN-ON DELAY
CLIPPING DETECTOR
MULTIWATT11V
MULTIWATT11H
ORDERING NUMBERS:
Protections:
TDA7360
TDA7360HS
OUTPUT AC-DC SHORT CIRCUIT TO
GROUND AND TO SUPPLY VOLTAGE
VERYINDUCTIVE LOADS
LOUDSPEAKER PROTECTION
OVERRATING CHIP TEMPERATURE
LOAD DUMP VOLTAGE
FORTUITOUS OPEN GROUND
ESD
Thanks to the fully complementary PNP/NPN out-
put configuration the high power performance of
the TDA7360 is obtained without bootstrap ca-
pacitors.
A delayed turn-on mute circuit eliminates audible
on/off noise, and a novel short circuit protection
system prevents spurious intervention with highly
inductive loads.
The device provides a circuit for the detection of
clipping in the output stages. The output, an open
collector, is able to drive systems with automatic
volume control.
DESCRIPTION
The TDA7360 is a new technology class AB
Audio Power Amplifier in the Multiwatt package
designed for car radio applications.
APPLICATION CIRCUIT (BRIDGE)
October 1998
1/22
This is advanced information on a new product now in development or undergoing evaluation. Details are subject to change without notice.
TDA7360
PIN CONNECTION (Top view)
ABSOLUTE MAXIMUM RATINGS
Symbol
Parameter
Test Conditions
Unit
V
VS
VS
Operating Supply Voltage
DC Supply Voltage
18
28
V
VS
Peak Supply Voltage (for t = 50ms)
Output Peak Current (non rep. for t = 100µs)
Output Peak Current (rep. freq. > 10Hz)
Power Dissipation at Tcase = 85°C
50
V
Io
5
A
Io
4
36
A
Ptot
Tstg,TJ
W
Storage and Junction Temperature
-40 to 150
C
°
THERMAL DATA
Symbol
Description
Value
1.8
Unit
Rth j-case Thermal Resistance Junction-case
Max
°C/W
2/22
TDA7360
ELECTRICAL CHARACTERISTICS
otherwise specified)
(Refer to the test circuits, Tamb = 25°C, VS = 14.4V, f = 1KHz unless
Symbol
VS
Parameter
Supply Voltage Range
Total Quiescent Drain Current
Stand-by attenuation
Test Condition
Min.
Typ.
Max.
18
Unit
V
8
Id
stereo configuration
120
mA
dB
ASB
ISB
60
80
Stand-by Current
100
A
µ
ICO
Clip Detector Average Current
Pin 2 pull up to 5V
with 10KΩ
d = 1%
d = 5%
70
µA
µA
130
STEREO
PO
Output Power (each channel)
d = 10%
RL = 1.6Ω
12
11
8
W
W
W
W
R = 2
Ω
L
RL = 3.2Ω
RL = 4Ω
7
6.5
d
Distortion
P
O = 0.1 to 4W RL = 3.2Ω
0.05
0.5
%
SVR
Supply Voltage Rejection
R = 10K
f = 100Hz
C3 = 22 F
C3 = 100µF
45
45
dB
dB
Ω
µ
g
62
CT
Crosstalk
f = 1KHz
f = 10KHz
dB
dB
55
50
20
RI
GV
GV
EIN
Input Resistance
Voltage Gain
K
Ω
dB
dB
Voltage Gain Match
Input Noise Voltage
1
22 Hz to 22KHz Rg = 50Ω
Rg = 10KΩ
2.5
3
5
7
µV
µV
R =
g
3.5
∞
BRIDGE
VOS
Po
Output Offset Voltage
Output Power
250
1
mV
d = 10%; RL = 4Ω
d = 10%; RL = 3.2
20
22
W
W
Ω
16
45
d
Distortion
Po = 0.1 to 10W; RL = 3.2Ω
0.05
%
SVR
Supply Voltage Rejection
R = 10K
C3 = 22 F
C3 = 100µF
dB
dB
Ω
µ
g
f = 100Hz
62
50
26
RI
GV
EIN
Input Resistance
Voltage Gain
KΩ
dB
µV
Input Noise Voltage
22Hz to 22KHz Rg = 50Ω
R = 10K
3.5
4
V
µ
Ω
g
3/22
TDA7360
Figure 1: STEREOTest and AppicationCircuit
1000µF
1000µF
Figure 2:
P.C. Board and Component Layout (STEREO) of the circuit of fig. 1 (1:1 scale)
4/22
TDA7360
Figure 3: BRIDGETest and Appication Circuit
Figure 4:
P.C. Board and Layout (BRIDGE) of the circuit of fig. 3 (1:1 scale)
5/22
TDA7360
RECOMMENDED VALUES OF THE EXTERNAL COMPONENTS
tion Circuit)
(ref to the Stereo Test and Applica-
Recommended
Value
Larger than the Recomm.
Smaller than the Recomm.
Value
Component
Purpose
Input
Decoupling
(CH1)
Value
C1
0.22µF
0.22µF
100µF
—
—
—
C2
C3
Input
Decoupling
(CH2)
—
Supply Voltage Longer Turn-On Delay Time
- WorseSupply VoltageRejection.
- Shorter Turn-On Delay Time
- Danger of Noise (POP)
Rejection
Filtering
Capacitor
C4
22µF
Stand-By
ON/OFF
Delay
Delayed Turn-Off by Stand-By
Switch
Danger of Noise (POP)
C5
C6
C7
220µF (min)
100nF (min)
2200µF
Supply By-Pass
Supply By-Pass
Danger of Oscillations
Danger of Oscillations
Output
Decoupling
CH2
-Decrease ofLow Frequency CutOff - Increase of Low Frequency Cut Off
- Longer Turn On Delay
- ShorterTurnOnDelay
Figure 5: Output Power vs. Supply Voltage
Figure 6:
Output Power vs. Supply Voltage
(Stereo)
(Stereo)
Figure 7:
Output Power vs. Supply Voltage
(Stereo)
Figure 8: Output Power vs. Supply Voltage
(Bridge)
6/22
TDA7360
Figure 9: Output Power vs. Supply Voltage
Figure 10: Drain Current vs SupplyVoltage
(Bridge)
(Stereo)
Figure 11:
Distortionvs OutputPower(Stereo)
Figure 12:
Distortion vs Output Power (Stereo)
Figure 13:
Figure 14:
Distortionvs OutputPower (Bridge)
Distortionvs OutputPower(Stereo)
7/22
TDA7360
Figure 15:
Distortion vs. Output Power
Figure 16: SVR vs. Frequency& C3 (Stereo)
Rg
Figure 17:
SVR vs. Frequency& C3 (Bridge)
Figure 18:
Crosstalk vs. Frequency(Stereo)
Rg
Rg
Figure 19:
Figure 20:
PowerDissipation & Efficiency vs.
OutputPower (Stereo)
Power Dissipation & Efficiency vs.
Output Power (Stereo)
8/22
TDA7360
TO MINIMIZE THE OUTPUT NOISE AND OP-
TIMIZE SVR
SILENT MUTE/ST-BY FUNCTION FEATUR-
ING ABSENCE OF POP ON/OFF NOISE
Figure 21:
PowerDissipation & Efficiency vs.
OutputPower (Bridge)
HIGH SVR
STEREO/BRIDGE OPERATION WITHOUT
ADDITION OF EXTERNAL COMPONENT
AC/DC SHORT CIRCUIT PROTECTION (TO
GND, TO VS, ACROSSTHE LOAD)
LOUDSPEAKER PROTECTION
DUMP PROTECTION
ESD PROTECTION
BLOCK DESCRIPTION
Polarization
The device is organized with the gain resistors di-
rectly connected to the signal ground pin i.e. with-
out gain capacitors(fig. 23).
The non inverting inputs of the amplifiers are con-
nected to the SVR pin by means of resistor divid-
ers, equal to the feedback networks. This allows
the outputs to track the SVR pin which is suffi-
ciently slow to avoid audible turn-on and turn-off
transients.
Figure 22: Power Dissipation & Efficiency vs.
OutputPower (Bridge)
SVR
The voltage ripple on the outputs is equal to the
one on SVR pin: with appropriate selection of
CSVR, more than 60dB of ripple rejection can be
obtained.
Delayed Turn-on (muting)
The CSVR sets a signal turn-on delay too. A circuit
is included which mutes the device until the volt-
age on SVR pin reaches ~2.5V typ. (fig. 25). The
mute function is obtained by duplicating the input
differential pair (fig. 24): it can be switched to the
signal source or to an internal mute input. This
feature is necessary to prevent transients at the
inputs reaching the loudspeaker(s) immediately
after power-on).
Fig. 25 represents the detailed turn-on transient
with reference to the stereo configuration.
At the power-on the output decoupling capacitors
are charged through an internal path but the de-
vice itself remains switched off (phase 1 of the
represented diagram).
When the outputs reach the voltage level of about
1V (this means that there is no presence of short
circuits) the device switches on, the SVR capaci-
tor starts charging itself and the output tracks ex-
actly the SVRpin.
During this phase the device is muted until the
SVR reaches the ”Play” threshold (~2.5V typ.), af-
ter that the music signal starts being played.
AMPLIFIER ORGANIZATION
The TDA7360 has been developed taking care of
the key concepts of the modern power audio am-
plifier for car radio such as: space and costs sav-
ing due to the minimized external count, excellent
electrical performances, flexibility in use, superior
reliability thanks to a built-in array of protections.
As a result the following performances has been
achieved:
NO NEED OF BOOTSTRAP CAPACITORS
EVEN AT THE HIGHEST OUTPUT POWER
LEVELS
ABSOLUTE STABILITY WITHOUT EXTER-
NAL COMPENSATION THANKS TO THE IN-
NOVATIVE OUT STAGE CONFIGURATION,
ALSO ALLOWING INTERNALLY FIXED
CLOSED LOOP LOWER THAN COMPETI-
TORS
LOW GAIN (20dB STEREO FIXED WITHOUT
ANY EXTERNAL COMPONENTS) IN ORDER
9/22
TDA7360
tion, so that a low current, and hence low cost
switch, can be used for turn on/off.
Stereo/Bridge Switching
There is also no need for external componentsfor
changing from stereo to bridge configuration(figg.
23-26). A simple short circuit between two pins al-
lows phase reversal at one output, yet maintain-
ing the quiescent output voltage.
Stability
The device is provided with an internal compen-
sation wich allows to reach low values of closed
loop gain.
In this way better performances on S/N ratio and
SVR can be obtained.
Stand-by
The device is also equipped with a stand-by func-
Figure 23:
BlockDiagram; Stereo Configuration
Figure 24:
MuteFunction Diagram
10/22
TDA7360
Figure 25: Turn-on Delay Circuit
11/22
TDA7360
Figure 26:
BlockDiagram; Bridge Configuration
out. (pin2) when a certain distortion level is
reached at each output. This particular function
allows compression facility whenever the amplifier
is overdriven, so obtaining high quality sound at
all listening levels.
CLIP DETECTOR
The TDA7360 is equipped with an internal circuit
able to detect the output stage saturation provid-
ing a proper current sinking into an open collector
Figure 27: Dual Channel Distortion Detector
Figure 28:
Output at Clipping Detector Pin vs.
Signal Distortion
12/22
TDA7360
OUTPUT STAGE
Figure 29:
ICV - PNP Gain vs. IC
Poor current capability and low cutoff frequency
are well known limits of the standard lateral PNP.
Composite PNP-NPN power output stages have
been widely used, regardless their high saturation
drop. This drop can be overcome only at the ex-
pense of external components, namely, the boot-
strap capacitors. The availability of 4A isolated
collector PNP (ICV PNP) adds versatility to the
design. The performance of this component, in
terms of gain, VCEsat and cut-off frequency, is
shown in fig. 29, 30, 31 respectively. It is realized
in a new bipolar technology, characterized by top-
bottom isolation techniques, allowing the imple-
mentation of low leakage diodes, too. It guaran-
tees BVCEO > 20V and BVCBO > 50V both for
NPN and PNP transistors. Basically, the connec-
tion shown in fig. 32 has been chosen. First of all
because its voltage swing is rail-to-rail, limited
only by the VCEsat of the output transistors,
which are in the range of 0.3Ω each. Then, the
gain VOUT/VIN is greater than unity, approxi-
mately 1+R2/R1. (VCC/2 is fixed by an auxiliary
amplifier common to both channel). It is possible,
controlling the amount of this local feedback, to
force the loop gain (A * β) to less than unity at fre-
quencies for which the phase shift is 180°. This
means that the output buffer is intrinsically stable
and not prone to oscillation.
Figure 30: ICV - PNP VCE(sat) vs. IC
Figure 32: The New Output Stage
Figure 31: ICV - PNP cut-off frequencyvs. IC
In contrast, with the circuit of fig. 33, the solution
adopted to reduce the gain at high frequencies is
the use of an external RC network.
AMPLIFIER BLOCK DIAGRAM
The block diagram of each voltage amplifier is
shown in fig. 34. Regardless of production
spread, the current in each final stage is kept low,
with enough margin on the minimum, below which
cross-over distortion would appear.
13/22
TDA7360
Figure 33: A Classical Output Stage
Figure 34:
Amplifier Block Diagram
below a given limit.
BUILT-IN PROTECTION SYSTEMS
The signal sets a flip-flop which forces the amplifier
outputsinto a high impedancestate.
Short Circuit Protection
The maximum current the device can deliver can
be calculated by considering the voltage that may
be present at the terminals of a car radio amplifier
and the minimum load impedance.
In case of DC short circuit when the short circuit
is removed the flip-flop is reset and restarts the
circuit (fig. 39). In case of AC short circuit or load
shorted in Bridge configuration, the device is con-
tinuously switched in ON/OFF conditions and the
current is limited.
Apart from consideration concerning the area of
the power transistors it is not difficult to achieve
peak currents of this magnitude (5 A peak).
However, it becomes more complicated if AC and
DC short circuit protection is also required.In par-
ticular, with a protection circuit which limits the
output current following the SOA curve of the out-
put transistors it is possible that in some condi-
tions (highly reactive loads, for example) the pro-
tection circuit may intervene during normal
operation. For this reason each amplifier has
been equipped with a protection circuit that inter-
venes when the output current exceeds 4A
Figure 35: Circuitry for Short Circuit Detection
Fig 35 shows the protection circuit for an NPN
power transistor (a symmetrical circuit applies to
PNP).The VBE of the power is monitored and
gives out a signal,availablethrough a cascode.
This cascode is used to avoid the intervention of
the short circuit protection when the saturation is
14/22
TDA7360
ing winter if two batteries are series connected to
crank the engine.
Load Dump Voltage Surge
The TDA 7360 has a circuit which enables it to
withstanda voltage pulse train on pin 9, of the type
shownin fig. 37.
Thermal Shut-down
The presence of a thermal limiting circuit offers
the following advantages:
1)an overload on the output (even if it is perma-
nent), or an excessive ambient temperature
can be easily withstood.
If the supply voltage peaks to more than 50V, then
an LC filter must be inserted between the supply
and pin 9, in order to assure that the pulses at pin9
will be held withinthe limits shown.
A suggestedLC networkis shownin fig. 36.
With this network, a train of pulseswith amplitude up
to 120Vand width of 2ms can be appliedat point A.
Thistypeof protectionis ON when thesupplyvoltage
(pulse or DC) exceeds18V. Forthis reason the maxi-
mumoperatingsupplyvoltageis18V.
2)the heatsink can have a smaller factorof safety
compared with that of a conventional circuit.
There is no device damage in the case of ex-
cessive junction temperature: all happens is
thatPo (andthereforePtot) and Id arereduced.
Figure 36
Figure 37
The maximum allowable power dissipation de-
pends upon the size of the external heatsink (i.e.
its thermal resistance); Fig. 38 shows the dissi-
pable power as a function of ambient temperature
for different thermal resistance.
Figure 38: Maximum Allowable Power
Dissipation vs. Ambient Temperature
Polarity Inversion
Loudspeaker Protection
High current (up to 10A) can be handled by the de-
vice with no damage for a longer period than the
blow-out time of a quick 2A fuse (normally connected
in series with the supply). This features is added to
avoiddestruction,if during fittingto thecar, a mistake
on theconnectionofthe supplyismade.
The TDA7360 guarantees safe operations even
for the loudspeaker in case of accidental shortcir-
cuit.
Whenever a single OUT to GND, OUT to VS short
circuit occurs both the outputs are switched OFF
so limiting dangerous DC current flowing through
the loudspeaker.
Open Ground
When the radio is in the ON condition and the
ground is accidentally opened, a standard audio
amplifier will be damaged. On the TDA7360 pro-
tection diodes are included to avoid any damage.
Figure 39:
RestartCircuit
DC Voltage
The maximum operating DC voltage for the
TDA7360 is 18V.
However the device can withstand a DC voltage
up to 28V with no damage. This could occur dur-
15/22
TDA7360
APPLICATION HINTS
Figure 40:
a) Csvr = 22 µF
This section explains briefly how to get the best
from the TDA7360 and presentssome application
circuits with suggestionsfor the value of the com-
ponents.These values can change depending on
the characteristics that the designer of the car ra-
dio wants to obtain,or other parts of the car radio
that are connected to the audio block.
To optimize the performance of the audio part it is
useful (or indispensable)to analyze also the parts
outside this block that can have an interconnec-
tion with the amplifier.
This method can provide componentsand system
cost saving.
Reducing Turn On-Off Pop
The TDA7360 has been designed in a way that
the turn on(off) transients are controlled through
the charge(discharge)of the Csvr capacitor.
b) Csvr = 47 µF
As a result of it, the turn on(off) transient spec-
trum contents is limited only to the subsonic
range.The following section gives some brief
notes to get the best from this design feature(it
will refer mainly to the stereo application which
appears to be in most cases the more critical from
the pop viewpoint.The bridge connection in
fact,due to the common mode waveform at the
outputs,does not give pop effect).
TURN-ON
Fig 40 shows the output waveform (before and
after the ”A” weighting filter) compared to the
value of Csvr.
Better pop-on performance is obtained with
higher Csvr values (the recommended range is
from 22uF to 220uF).
The turn-on delay (during which the amplifier is in
mute condition) is a function essentially of : Cout ,
c) Csvr = 100 µF
Csvr
.
Being:
T1 ≈ 120 • Cout
T2 ≈ 1200 • Csvr
The turn-on delay is given by:
T1+T2 STEREO
T2 BRIDGE
The best performance is obtained by driving the
st-by pin with a ramp having a slope slower than
2V/ms
16/22
TDA7360
perior, in particular the st-by pin can go low faster.
TURN-OFF
A turn-off pop can occur if the st-by pin goes low
with a short time constant (this can occur if other
car radio sections, preamplifiers,radio.. are sup-
plied through the same st-by switch).
GLOBAL APPROACH TO SOLVING POP
PROBLEM BY USING THE MUTING/TURN ON
DELAY FUNCTION
This pop is due to the fast switch-off of the inter-
nal current generatorof the amplifier.
In the real case turn-on and turn-off pop problems
are generated not only by the power amplifier,but
also (very often) by preamplifiers,tone controls,ra-
dios etc. and transmitted by the power amplifier to
the loudspeaker.
A simple approach to solving these problems is to
use the mute characteristicsof the TDA7360.
If the voltage present across the load becomes
rapidly zero (due to the fast switch off) a small
pop occurs, dependingalso on Cout,Rload.
The parameters that set the switch off time con-
stant of the st-by pin are:
♦ the st-by capacitor (Cst-by)
♦ the SVR capacitor (Csvr)
♦ resistors connected from st-by pin to ground
(Rext)
If the SVR pin is at a voltage below 1.5 V, the
mute attenuation (typ) is 30dB .The amplifier is in
play mode when Vsvr overcomes3.5 V.
With the circuit of fig 43 we can mute the amplifier
for a time Ton after switch-on and for a time Toff
after switch-off.During this period the circuitry that
precedes the power amplifier can produce spuri-
ous spikes that are not transmitted to the loud-
speaker. This can give back a very simple design
of this circuitry from the pop point of view.
The time constant is given by :
T ≈ Csvr • 2000Ω //Rext + Cst-by • 2500Ω //Rext
The suggestedtime constantsare :
T > 120ms with Cout=1000µF,RL = 4ohm,stereo
T > 170ms with Cout=2200µF,RL = 4ohm,stereo
If Rext is too low the Csvr can become too high
and a different approach may be useful (see next
section).
Figg 41, 42 show some types of electronic
switches (µP compatible) suitable for supplying
the st-by pin (it is important that Qsw is able to
saturate with VCE ≤ 150mV).
A timing diagram of this circuit is illustrated in fig
44. Other advantagesof this circuit are:
- A reduced time constant allowance of stand-by
pin turn off.Consequentlyit is possible to drive all
the car-radio with the signal that drives this pin.
-A better turn-off noise with signal on the output.
To drive two stereo amplifiers with this circuit it is
possible to use the circuit of fig 45.
Also for turn off pop the bridge configuration is su-
Figure 41
Figure 42
17/22
TDA7360
Figure 43
Figure 44
18/22
TDA7360
bridge configuration, a signal present on both the
input capacitors is amplified by the same amount
and it is present in phase at the outputs,so this
signal does not produce effects on the load.The
typical value of CMRR is 46 dB.
Figure 45
Looking at fig 46, we can see that a noise signal
from the ground of the power amplifier to the
ground of the hypothetical preamplifier is ampli-
fied of a factor equal to the gain of the amplifier
(2 * Gv).
Using a configuration of fig. 47 the same ground
noise is present at the output multiplied by the
factor 2 * Gv/200.
This means less distortion,less noise (e.g. motor
cassette noise ) and/or a simplification of the lay-
out of PC board.
The only limitation of this balanced input is the
maximum amplitude of common mode signals
(few tens of millivolt) to avoid a loss of output
power due to the common mode signal on the
output, but in a large number of cases this signal
is within this range.
BALANCED INPUTIN BRIDGE CONFIGURATION
A helpful characteristic of the TDA7360 is that,in
Figure 46
Figure 47
19/22
TDA7360
mm
inch
DIM.
OUTLINE AND
MIN. TYP. MAX. MIN. TYP. MAX.
MECHANICAL DATA
A
B
5
0.197
0.104
0.063
2.65
1.6
C
D
1
0.039
E
0.49
0.88
1.45
16.75
19.6
0.55 0.019
0.95 0.035
0.022
0.037
F
G
1.7
17
1.95 0.057 0.067 0.077
17.25 0.659 0.669 0.679
0.772
G1
H1
H2
L
20.2
0.795
21.9
21.7
17.4
22.2
22.1
22.5 0.862 0.874 0.886
22.5 0.854 0.87 0.886
L1
L2
L3
L4
L7
M
18.1 0.685
0.713
17.25 17.5 17.75 0.679 0.689 0.699
10.3
2.65
4.25
4.73
1.9
10.7
10.9 0.406 0.421 0.429
2.9 0.104 0.114
4.55
5.08
4.85 0.167 0.179 0.191
5.43 0.186 0.200 0.214
M1
S
2.6
2.6
0.075
0.075
0.102
0.102
0.152
S1
Dia1
1.9
Multiwatt11 V
3.65
3.85 0.144
20/22
TDA7360
mm
MIN. TYP. MAX. MIN. TYP. MAX.
4.373 4.5 4.627 0.172 0.177 0.182
inch
DIM.
OUTLINE AND
MECHANICAL DATA
A
B
C
2.65
1.6
0.104
0.063
E
E1
F
0.49 0.515 0.55 0.019 0.020 0.022
1.007 1.037 1.07 0.040 0.041 0.042
0.88
1.5
0.9
1.7
0.95 0.035 0.035 0.037
1.9 0.059 0.067 0.075
G
G.1
G2
G3
G4
G5
H1
H2
L1
L2
L3
L4
16.82 17.02 17.22 0.662 0.670 0.678
6.61 6.807 7.01 0.260 0.268 0.276
13.41 13.61 13.81 0.528 0.536 13.810
3.2
10.01 10.21 10.41 0.394 0.402 0.410
19.6 0.77
3.4
3.6
0.126 0.134 0.142
2
20.2
19.28 19.58 19.88 0.759 0.771 0.783
3.61 3.81 4.01 0.142 0.150 0.158
17.25 17.5 17.75 0.679 0.689 0.699
0.795
10.3
10.6
10.9 0.406 0.417 0.429
L5
(Inner)
3.4
3.75
4
0.134 0.148 0.157
L5
3.6
3.9
1
4.2
2.9
0.142 0.154 4.200
(Outer)
L7
R
S
S1
Dia1
2.65
0.75
1.9
1.9
3.65
0.104
0.114
1.25 0.030 0.039 0.049
2.6
2.6
0.075
0.075
0.102
0.102
0.152
Multiwatt11 H (Short leads)
3.85 0.144
V
V
V
G5
G4
R
R
A
B
C
L5
V
L1
E
X
L2
L3
G1
H2
L4
N
L7
F
E1
E
G
DETAIL X
G2
F
H2
G3
H1
0.25min
0.50max
Dia.1
S1
S
P
MULT11LHM
R1
60 to 90
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TDA7360
Information furnished is believed to be accurate and reliable. However, STMicroelectronics assumes no responsibility for the consequences
of use of such information nor for any infringement of patents or other rights of third parties which may result from its use. No license is
granted by implication or otherwise under any patent or patent rights of STMicroelectronics. Specification mentioned in this publication are
subject to change without notice. This publication supersedes and replaces all information previously supplied. STMicroelectronics products
are not authorized for use as critical components in life support devices or systems without express written approval of STMicroelectronics.
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MULTIWATT is a Registered Trademark of the STMicroelectronics
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