LMH6609MA [NSC]
900MHz Voltage Feedback Op Amp; 900MHz的电压反馈运算放大器
| 型号： | LMH6609MA |
| 厂家： | 
National Semiconductor |
| 描述： | 900MHz Voltage Feedback Op Amp |
| 文件： | 总15页 (文件大小：639K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
August 2003
LMH6609
900MHz Voltage Feedback Op Amp
General Description
Features
n 900MHz −3dB bandwidth (AV = 1)
The LMH6609 is an ultra wideband, unity gain stable, low
power, voltage feedback op amp that offers 900MHz band-
width at a gain of 1, 1400V/µs slew rate and 90mA of linear
output current.
n Large signal bandwidth and slew rate 100% tested
n 280MHz −3dB bandwidth (AV = +2, VOUT = 2VPP
n 90mA linear output current
n 1400V/µs slew rate
)
The LMH6609 is designed with voltage feedback architec-
ture for maximum flexibility especially for active filters and
integrators. The LMH6609 has balanced, symmetrical inputs
with well-matched bias currents and minimal offset voltage.
n Unity gain stable
<
n
1mV input Offset voltage
n 7mA Supply current (no load)
n 6V to 12V supply voltage range
n .01/ .026 differential gain/phase PAL
With Differential Gain of .01 and Differential Phase of .026
the LMH6609 is suited for video applications. The 90mA of
linear output current makes the LMH6609 suitable for mul-
tiple video loads and cable driving applications as well.
n 3.1nV/
voltage noise
n Improved replacement for CLC440, 420, 426
The recommended supply voltage range of 6V to 12V and is
specified at 6.6 and 10V. A low supply current of 7mA (at 10V
supply) makes the LMH6609 useful in a wide variety of
platforms, including portable or remote equipment that must
run from battery power.
Applications
n Test equipment
n IF/RF amplifier
n A/D Input driver
n Active filter
n Integrator
n DAC output buffer
n Transimpedance amplifier
The LMH6609 is available in the industry standard 8-pin
SOIC package and in the space-saving 5-pin SOT package.
The LMH6609 is specified for operation over the -40˚C to
+85˚C temperature range. The LMH6609 is manufactured in
National Semiconductor’s state-of-the-art VIP10 technol-
ogy for high performance.
™
Typical Application
20079037
20079038
Sallen Key Low Pass Filter
© 2003 National Semiconductor Corporation
DS200790
www.national.com
Absolute Maximum Ratings (Note 1)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales Office/
Distributors for availability and specifications.
Machine Model
200V
Operating Ratings (Note 3)
Thermal Resistance
VS (V+ - V−)
6.6V
(Note 3)
Package
(θJC
)
(θJA)
IOUT
8-Pin SOIC
65˚C/W
120˚C/W
−40˚C
145˚C/W
187˚C/W
+85˚C
6V
Common Mode Input Voltage
Maximum Junction Temperature
Storage Temperature Range
Lead Temperature Range
ESD Tolerance (Note 4)
Human Body Model
V+ to V−
5-Pin SOT23
+150˚C
Operating Temperature
Nominal Supply Voltage
(Note 6)
−65˚C to +150˚C
+300˚C
3.3V
2000V
5V Electrical Characteristics
Unless specified, AV = +2, RF = 250Ω: VS
=
5V, RL = 100Ω; unless otherwise specified. Boldface limits apply over tempera-
ture Range. (Note 2)
Symbol
Parameter
Conditions
Min
Typ
Max
Units
Frequency Domain Response
SSBW
LSBW
−3dB Bandwidth
−3dB Bandwidth
VOUT = 0.5VPP
260
170
MHz
MHz
MHz
MHz
%
VOUT = 4.0VPP
150
SSBWG1 −3dB Bandwidth AV = 1
VOUT = 0.25VPP
900
GFP
DG
DP
.1dB Bandwidth
Differential Gain
Differential Phase
Gain is Flat to .1dB
RL = 150Ω, 4.43MHz
RL = 150Ω, 4.43MHz
130
0.01
0.026
deg
Time Domain Response
TRS
TRL
ts
Rise and Fall Time
1V Step
1.6
2.6
ns
ns
4V Step
Settling Time to 0.05%
Slew Rate
2V Step
15
ns
SR
4V Step (Note 5)
1200
1400
V/µs
Distortion and Noise Response
HD2
HD3
2nd Harmonic Distortion
3rd Harmonic Distortion
Equivalent Input Noise
Voltage Noise
2VPP, 20MHz
2VPP, 20MHz
−63
−57
dBc
dBc
>
>
VN
CN
1MHz
1MHz
3.1
1.6
nV/
pA/
Current Noise
Static, DC Performance
VIO
Input Offset Voltage
0.8
−2
.1
2.5
3.5
5
mV
IBN
Input Bias Current
µA
µA
dB
dB
mA
8
IBI
Input Offset Current
1.5
3
PSRR
CMRR
ICC
Power Supply Rejection Ratio
Common Mode Rejection Ratio
Supply Current
DC, 1V Step
DC, 2V Step
67
65
67
65
73
73
7.0
∞
RL
=
7.8
8.5
Miscellaneous Performance
RIN
Input Resistance
Input Capacitance
Output Resistance
1
MΩ
pF
Ω
CIN
1.2
0.3
ROUT
Closed Loop
2
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5V Electrical Characteristics (Continued)
Unless specified, AV = +2, RF = 250Ω: VS
ture Range. (Note 2)
=
5V, RL = 100Ω; unless otherwise specified. Boldface limits apply over tempera-
Symbol
VO
Parameter
Conditions
Min
3.6
3.3
3.2
3.0
2.8
2.5
60
Typ
Max
Units
∞
Output Voltage Range
RL
=
3.9
V
VOL
CMIR
IO
RL = 100Ω
3.5
3.0
90
V
V
>
Input Voltage Range
Linear Output Current
Common Mode, CMRR 60dB
VOUT
mA
50
3.3V Electrical Characteristics
Unless specified, AV = +2, RF = 250Ω: VS
perature Range. (Note 2)
=
3.3V, RL = 100Ω; unless otherwise specified. Boldface limits apply over tem-
Symbol
Parameter
Conditions
Min
Typ
Max
Units
Frequency Domain Response
SSBW
LSBW
−3dB Bandwidth
−3dB Bandwidth
VOUT = 0.5VPP
180
110
450
40
MHz
MHz
MHz
MHz
%
VOUT = 3.0VPP
SSBWG1 −3dB Bandwidth AV = 1
VOUT = 0.25VPP
VOUT = 1VPP
GFP
DG
DP
.1dB Bandwidth
Differential Gain
Differential Phase
RL = 150Ω, 4.43MHz
RL = 150Ω, 4.43MHz
.01
.06
deg
Time Domain Response
TRL
1V Step
2.2
ns
SR
Slew Rate
2V Step (Note 5)
800
V/µs
Distortion and Noise Response
HD2
HD3
2nd Harmonic Distortion
3rd Harmonic Distortion
Equivalent Input Noise
Voltage Noise
2VPP, 20MHz
2VPP, 20MHz
−63
−43
dBc
dBc
>
>
VN
CN
1MHz
1MHz
3.7
1.1
nV/
pA/
Current Noise
Static, DC Performance
VIO
IBN
IBI
Input Offset Voltage
0.8
−1
0
2.5
3.5
3
mV
Input Bias Current
Input Offset Current
µA
µA
6
1.5
3
PSRR
CMRR
ICC
Power Supply Rejection Ratio
Common Mode Rejection Ratio
Supply Current
DC, .5V Step
DC, 1V Step
67
67
73
75
dB
dB
∞
RL
=
3.6
5
mA
6
Miscellaneous Performance
ROUT
VO
Input Resistance
Close Loop
.05
2.3
2.0
1.3
45
Ω
V
∞
Output Voltage Range
RL
=
2.1
1.9
VOL
CMIR
IO
RL = 100Ω
Common Mode
VOUT
V
Input Voltage Range
Linear Output Current
V
30
mA
3
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3.3V Electrical Characteristics (Continued)
Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is
intended to be functional, but specific performance is not guaranteed. For guaranteed specifications, see the Electrical Characteristics tables.
Note 2: Electrical Table values apply only for factory testing conditions at the temperature indicated. Factory testing conditions result in very limited self-heating of
>
the device such that T = T . No guarantee of parametric performance is indicated in the electrical tables under conditions of internal self heating where T
T .
J
A
J
A
See Applications Section for information on temperature derating of this device. Min/Max ratings are based on product characterization and simulation. Individual
parameters are tested as noted.
Note 3: The maximum output current (I
) is determined by device power dissipation limitations. See the Power Dissipation section of the Application Section for
OUT
more details.
Note 4: Human body model, 1.5kΩ in series with 100pF. Machine model, 0Ω In series with 200pF.
Note 5: rate is Average of Rising and Falling 40-60% slew rates.
Note 6: Nominal Supply voltage range is for supplies with regulation of 10% or better.
Connection Diagrams
5-Pin SOT23
8-Pin SOIC
20079039
20079040
Top View
Top View
Ordering Information
Package
Part Number
LMH6609MA
LMH6609MAX
LMH6609MF
LMH6609MFX
Package Marking
Transport Media
NSC Drawing
95 Units/Rails
8-Pin SOIC
LMH6609MA
M08A
2.5k Units Tape and Reel
1k Units Tape and Reel
2.5k Units Tape and Reel
5-SOT23
A89A
MF05A
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4
Typical Performance Characteristics
Small Signal Non-Inverting Frequency Response
Large Signal Non-Inverting Frequency Response
20079004
20079003
Small Signal Inverting Frequency Response
Large Signal Inverting Frequency Response
20079002
20079010
Frequency Response vs. VOUT AV = 2
Frequency Response vs. VOUT AV = 2
20079009
20079001
5
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Typical Performance Characteristics (Continued)
Frequency Response vs. VOUT AV = 1
Frequency Response vs. VOUT AV = −1
20079007
20079008
Frequency Response vs. VOUT AV = −1
Frequency Response vs. Cap Load
20079042
20079006
Frequency Response vs. Cap Load
Suggested ROUT vs. Cap Load
20079043
20079041
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6
Typical Performance Characteristics (Continued)
CMRR vs. Frequency
PSRR vs. Frequency
20079011
20079012
PSRR vs. Frequency
Pulse Response
20079013
20079016
Pulse Response
Large Signal Pulse Response
20079014
20079015
7
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Typical Performance Characteristics (Continued)
Noise vs. Frequency
HD2 vs. VOUT
20079025
20079018
HD3 vs. VOUT
HD2 vs. VOUT
20079020
20079017
HD3 vs. VOUT
HD2 & HD3 vs. Frequency
20079021
20079019
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8
Typical Performance Characteristics (Continued)
HD2 & HD3 vs. Frequency
Differential Gain & Phase
20079022
20079046
Differential Gain & Phase
Open Loop Gain & Phase
20079044
20079047
Open Loop Gain & Phase
Closed Loop Output Resistance
20079045
20079023
9
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Application Section
GENERAL DESIGN EQUATION
The LMH6609 is a unity gain stable voltage feedback ampli-
fier. The matched input bias currents track well over tem-
perature. This allows the DC offset to be minimized by
matching the impedance seen by both inputs.
GAIN
The non-inverting and inverting gain equations for the
LMH6609 are as follows:
20079028
FIGURE 2. Typical Inverting Application
20079027
FIGURE 1. Typical Non-Inverting Application
20079029
FIGURE 3. Single Supply Inverting
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10
time. Refer to the Driving Capacitive Loads section for guid-
ance on selecting an output resistor for driving capacitive
loads.
Application Section (Continued)
EVALUATION BOARDS
National Semiconductor provides the following evaluation
boards as a guide for high frequency layout and as an aid in
device testing and characterization. Many of the datasheet
plots were measured with these boards.
#
Device
LMH6609MA
LMH6609MF
Package
SOIC
SOT-23
Board Part
CLC730227
CLC730216
A free evaluation board is automatically shipped when a
sample request is placed with National Semiconductor.
CIRCUIT LAYOUT CONSIDERATION
A proper printed circuit layout is essential for achieving high
frequency performance. National provides evaluation boards
for the LMH6609 as shown above. These boards were laid
out for optimum, high-speed performance. The ground plane
was removed near the input and output pins to reduce
parasitic capacitance. Also, all trace lengths were minimized
to reduce series inductances.
20079030
Supply bypassing is required for the amplifiers performance.
The bypass capacitors provide a low impedance return cur-
rent path at the supply pins. They also provide high fre-
quency filtering on the power supply traces. 10µF tantalum
and .01µF capacitors are recommended on both supplies
(from supply to ground). In addition a .1µF ceramic capacitor
can be added from V+ to V− to aid in second harmonic
suppression.
FIGURE 4. AC Coupled Non-Inverting
GAIN BANDWIDTH PRODUCT
The LMH6609 is a voltage feedback amplifier, whose
closed-loop bandwidth is approximately equal to the gain-
bandwidth product (GBP) divided by the gain (AV). For gains
greater than 5, AV sets the closed-loop bandwidth of the
LMH6609.
20079033
20079031
FIGURE 5. Driving Capacitive Loads with ROUT for
Improved Stability
For Gains less than 5, refer to the frequency response plots
to determine maximum bandwidth. For large signal band-
width the slew rate is a more accurate predictor of band-
width.
DRIVING CAPACITIVE LOADS
Capacitive output loading applications will benefit from the
use of a series output resistor ROUT. Figure 5 shows the use
of a series output resistor, ROUT as it might be applied when
driving an analog to digital converter. The charts "Suggested
RO vs. Cap Load" in the Typical Performance Section give a
recommended value for mitigating capacitive loads. The val-
ues suggested in the charts are selected for .5dB or less of
peaking in the frequency response. This gives a good com-
promise between settling time and bandwidth. For applica-
tions where maximum frequency response is needed and
some peaking is tolerable, the value of RO can be reduced
slightly from the recommended values. There will be ampli-
tude lost in the series resistor unless the gain is adjusted to
compensate; this effect is most noticeable with heavy resis-
tive loads.
20079032
Where fMAX = bandwidth, SR = Slew rate and VP = peak
amplitude.
OUTPUT DRIVE AND SETTLING TIME PERFORMANCE
The LMH6609 has large output current capability. The
100mA of output current makes the LMH6609 an excellent
choice for applications such as:
•
•
Video Line Drivers
Distribution Amplifiers
When driving a capacitive load or coaxial cable, include a
series resistance ROUT to back match or improve settling
11
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quency content of the signal. Performance degrades as the
loading is increased, therefore best performance will be
obtained with back-terminated loads. The back termination
reduces reflections from the transmission line and effectively
masks transmission line and other parasitic capacitances
from the amplifier output stage. This means that the device
should be configured for a gain of 2 in order to have a net
gain of 1 after the terminating resistor. (See Figure 6)
Application Section (Continued)
COMPONENT SELECTION AND FEEDBACK RESISTOR
Surface mount components are highly recommended for the
LMH6609. Leaded components will introduce unpredictable
parasitic loading that will interfere with proper device opera-
tion. Do not use wire wound resistors.
The LMH6609 operates best with a feedback resistor of
approximately 250Ω for all gains of +2 and greater and for −1
and less. With lower gains in particular, large value feedback
resistors will exaggerate the effects of parasitic capacitances
and may lead to ringing on the pulse response and fre-
quency response peaking. Large value resistors also add
undesirable thermal noise. Feedback resistors that are much
below 100Ω will load the output stage, which will reduce
voltage output swing, increase device power dissipation,
increase distortion and reduce current available for driving
the load.
In the buffer configuration the output should be shorted
directly to the inverting input. This feedback does not load
the output stage because the inverting input is a high imped-
ance point and there is no gain set resistor to ground.
OPTIMIZING DC ACCURACY
The LMH6609 offers excellent DC accuracy. The well-
matched inputs of this amplifier allows even better perfor-
mance if care is taken to balance the impedances seen by
the two inputs. The parallel combination of the gain setting
RG and feedback RF resistors should be equal to RSEQ, the
resistance of the source driving the op amp in parallel with
any terminating Resistor (See Figure 1). Combining this with
the non inverting gain equation gives the following param-
eters:
20079034
FIGURE 6. Typical Video Application
ESD PROTECTION
RF = AVRSEQ
The LMH6609 is protected against electrostatic discharge
(ESD) on all pins. The LMH6609 will survive 2000V Human
Body model or 200V Machine model events.
RG = RF/(AV−1)
For Inverting gains the bias current cancellation is accom-
plished by placing a resistor RB on the non-inverting input
equal in value to the resistance seen by the inverting input
(See Figure 2). RB = RF || (RG + RS)
Under closed loop operation the ESD diodes have no effect
on circuit performance. There are occasions, however, when
the ESD diodes may be evident. For instance, if the amplifier
is powered down and a large input signal is applied the ESD
diodes will conduct.
The additional noise contribution of RB can be minimized by
the use of a shunt capacitor (not shown).
POWER DISSIPATION
TRANSIMPEDANCE AMPLIFIER
The LMH6609 has the ability to drive large currents into low
impedance loads. Some combinations of ambient tempera-
ture and device loading could result in device overheating.
For most conditions peak power values are not as important
as RMS powers. To determine the maximum allowable
power dissipation for the LMH6609 use the following for-
mula:
The low input current noise and unity gain stability of the
LMH6609 make it an excellent choice for transimpedance
applications. Figure 7 illustrates a low noise transimpedance
amplifier that is commonly implemented with photo diodes.
RF sets the transimpedance gain. The photo diode current
multiplied by RF determines the output voltage.
PMAX = (150o - TAMB)/θJA
Where TAMB = Ambient temperature (˚C) and θJA = Thermal
resistance, from junction to ambient, for a given package
(˚C/W). For the SOIC package θJA is 148˚C/W, for the SOT
it is 250˚C/W. 150oC is the absolute maximum limit for the
internal temperature of the device.
Either forced air cooling or a heat sink can greatly increase
the power handling capability for the LMH6609.
VIDEO PERFORMANCE
The LMH6609 has been designed to provide good perfor-
mance with both PAL and NTSC composite video signals.
The LMH6609 is specified for PAL signals. NTSC perfor-
mance is typically marginally better due to the lower fre-
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12
Rectifier
Application Section (Continued)
The large bandwidth of the LMH6609 allows for high-speed
rectification. A common rectifier topology is shown in Figure
8. R1 and R2 set the gain of the rectifier.
20079035
FIGURE 7. Transimpedance Amplifier
20079036
The capacitances are defined as:
FIGURE 8. Rectifier Topology
•
•
CD = Equivalent Diode Capacitance
CF = Feedback Capacitance
The feedback capacitor is used to give optimum flatness and
stability. As a starting point the feedback capacitance should
1
be chosen as ⁄
2
of the Diode capacitance. Lower feedback
capacitors will peak frequency response.
13
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Physical Dimensions inches (millimeters)
unless otherwise noted
8-Pin SOIC
NS Product Number M08A
5-Pin SOT23
NS Product Number MF05A
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14
Notes
LIFE SUPPORT POLICY
NATIONAL’S PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT
DEVICES OR SYSTEMS WITHOUT THE EXPRESS WRITTEN APPROVAL OF THE PRESIDENT AND GENERAL
COUNSEL OF NATIONAL SEMICONDUCTOR CORPORATION. As used herein:
1. Life support devices or systems are devices or
systems which, (a) are intended for surgical implant
into the body, or (b) support or sustain life, and
whose failure to perform when properly used in
accordance with instructions for use provided in the
labeling, can be reasonably expected to result in a
significant injury to the user.
2. A critical component is any component of a life
support device or system whose failure to perform
can be reasonably expected to cause the failure of
the life support device or system, or to affect its
safety or effectiveness.
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