LM6171 [NSC]
High Speed Low Power Low Distortion Voltage Feedback Amplifier; 高速低功耗低失真电压反馈放大器
| 型号： | LM6171 |
| 厂家： | 
National Semiconductor |
| 描述： | High Speed Low Power Low Distortion Voltage Feedback Amplifier |
| 文件： | 总17页 (文件大小：710K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
May 1998
LM6171
High Speed Low Power Low Distortion Voltage Feedback
Amplifier
General Description
Features
The LM6171 is a high speed unity-gain stable voltage feed-
back amplifier. It offers a high slew rate of 3600V/µs and a
unity-gain bandwidth of 100 MHz while consuming only 2.5
mA of supply current. The LM6171 has very impressive AC
and DC performance which is a great benefit for high speed
signal processing and video applications.
(Typical Unless Otherwise Noted)
n Easy-To-Use Voltage Feedback Topology
n Very High Slew Rate: 3600V/µs
n Wide Unity-Gain-Bandwidth Product: 100 MHz
n −3 dB Frequency AV +2: 62 MHz
n Low Supply Current: 2.5 mA
n High CMRR: 110 dB
=
@
±
The 15V power supplies allow for large signal swings and
give greater dynamic range and signal-to-noise ratio. The
LM6171 has high output current drive, low SFDR and THD,
ideal for ADC/DAC systems. The LM6171 is specified for
n High Open Loop Gain: 90 dB
n Specified for 15V and 5V Operation
±
±
±
5V operation for portable applications.
Applications
n Multimedia Broadcast Systems
n Line Drivers, Switchers
n Video Amplifiers
™
The LM6171 is built on National’s advanced VIP III (Verti-
cally Integrated PNP) complementary bipolar process.
n NTSC, PAL® and SECAM Systems
n ADC/DAC Buffers
n HDTV Amplifiers
n Pulse Amplifiers and Peak Detectors
n Instrumentation Amplifier
n Active Filters
Typical Performance Characteristics
Closed Loop Frequency Response
Large Signal
=
vs Supply Voltage (AV +1)
Pulse Response
=
=
±
AV +1, VS
15
DS012336-9
DS012336-5
™
VIP is a trademark of National Semiconductor Corporation.
PAL® is a registered trademark of and used under licence from Advanced Micro Devices, Inc.
© 1999 National Semiconductor Corporation
DS012336
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Connection Diagram
8-Pin DIP/SO
DS012336-1
Top View
Ordering Information
Package
Temperature Range
Transport
Media
NSC
Drawing
Industrial
−40˚C to +85˚C
8-Pin
LM6171AIN
Rails
N08E
Molded DIP
8-Pin
LM6171BIN
LM6171AIM, LM6171BIM
LM6171AIMX, LM6171BIMX
Rails
M08A
Small Outline
Tape and Reel
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2
Absolute Maximum Ratings (Note 1)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales Office/
Distributors for availability and specifications.
Storage Temperature Range
Maximum Junction Temperature
(Note 4)
−65˚C to +150˚C
150˚C
Operating Ratings (Note 1)
ESD Tolerance (Note 2)
Supply Voltage (V+–V−)
Differential Input Voltage
(Note 11)
2.5 kV
36V
Supply Voltage
2.75V ≤ V+ ≤ 18V
Junction Temperature Range
LM6171AI, LM6171BI
±
10V
−40˚C ≤ TJ ≤ +85˚C
Common-Mode
Thermal Resistance (θJA
)
Voltage Range
V+ −1.4V to V− + 1.4V
Continuous
N Package, 8-Pin Molded DIP
108˚C/W
172˚C/W
Output Short Circuit to Ground
(Note 3)
M Package, 8-Pin Surface Mount
±
15V DC Electrical Characteristics
+
−
=
=
= = =
−15V, VCM 0V, and RL 1 kΩ. Boldface
Unless otherwise specified, all limits guaranteed for TJ 25˚C, V
limits apply at the temperature extremes
+15V, V
Typ
LM6171AI
LM6171BI
Symbol
Parameter
Input Offset Voltage
Conditions
(Note 5)
Limit
Limit
Units
(Note 6)
(Note 6)
VOS
1.5
3
6
mV
max
µV/˚C
µA
5
8
TC VOS
IB
Input Offset Voltage Average Drift
Input Bias Current
6
1
3
4
2
3
3
4
2
3
max
µA
IOS
Input Offset Current
Input Resistance
0.03
max
MΩ
RIN
Common Mode
40
4.9
14
Differential Mode
RO
Open Loop
Ω
Output Resistance
Common Mode
Rejection Ratio
Power Supply
=
±
CMRR
PSRR
VCM
AV
VCM
10V
110
95
80
75
85
80
75
70
80
75
dB
min
dB
min
V
=
±
±
15V to 5V
VS
Rejection Ratio
Input Common-Mode
Voltage Range
Large Signal Voltage
Gain (Note 7)
±
CMRR ≥ 60 dB
13.5
90
=
RL 1 kΩ
80
70
80
70
dB
min
dB
=
RL 100Ω
83
70
70
60
60
min
V
=
VO
Output Swing
RL 1 kΩ
13.3
−13.3
11.6
−10.5
116
12.5
12
12.5
12
min
V
−12.5
−12
9
−12.5
−12
9
max
V
=
RL 100Ω
8.5
−9
8.5
−9
min
V
−8.5
90
−8.5
90
max
mA
min
mA
max
=
Sourcing, RL 100Ω
Continuous Output Current
(Open Loop) (Note 8)
85
85
=
Sinking, RL 100Ω
105
90
90
85
85
3
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±
15V DC Electrical Characteristics (Continued)
+
−
=
=
= = =
−15V, VCM 0V, and RL 1 kΩ. Boldface
Unless otherwise specified, all limits guaranteed for TJ 25˚C, V
limits apply at the temperature extremes
+15V, V
Typ
LM6171AI
Limit
LM6171BI
Limit
Symbol
Parameter
Conditions
(Note 5)
Units
(Note 6)
(Note 6)
=
Continuous Output Current
(in Linear Region)
Output Short
Sourcing, RL 10Ω
100
80
mA
mA
mA
mA
mA
max
=
Sinking, RL 10Ω
ISC
Sourcing
Sinking
135
135
2.5
Circuit Current
IS
Supply Current
4
4
4.5
4.5
±
15V AC Electrical Characteristics
+
−
=
=
= = =
−15V, VCM 0V, and RL 1 kΩ. Boldface
Unless otherwise specified, all limits guaranteed for TJ 25˚C, V
limits apply at the temperature extremes
+15V, V
Typ
LM6171AI
Limit
LM6171BI
Limit
Symbol
SR
Parameter
Conditions
(Note 5)
Units
(Note 6)
(Note 6)
=
=
Slew Rate (Note 9)
AV +2, VIN 13 VPP
3600
3000
100
160
62
V/µs
=
=
AV +2, VIN 10 VPP
GBW
Unity Gain-Bandwidth Product
−3 dB Frequency
MHz
MHz
MHz
deg
ns
=
AV +1
=
AV +2
φm
Phase Margin
40
=
=
=
±
ts
Settling Time (0.1%)
AV −1, VOUT
5V
48
=
RL 500Ω
=
±
Propagation Delay
VIN
5V, RL 500Ω,
6
ns
=
AV −2
AD
φD
en
Differential Gain (Note 10)
Differential Phase (Note 10)
Input-Referred
0.03
0.5
12
%
deg
=
=
f
f
1 kHz
Voltage Noise
in
Input-Referred
1 kHz
1
Current Noise
±
5V DC Electrical Characteristics
+
−
=
=
= = =
−5V, VCM 0V, and RL 1 kΩ. Boldface
Unless otherwise specified, all limits guaranteed for TJ 25˚C, V
limits apply at the temperature extremes
+5V, V
Typ
LM6171AI
LM6171BI
Symbol
VOS
Parameter
Conditions
(Note 5)
Limit
Limit
Units
(Note 6)
(Note 6)
Input Offset Voltage
1.2
4
3
6
mV
max
5
8
TC VOS
Input Offset Voltage
Average Drift
µV/˚C
IB
Input Bias Current
1
2.5
3.5
1.5
2.2
2.5
3.5
1.5
2.2
µA
max
µA
IOS
Input Offset Current
0.03
max
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4
±
5V DC Electrical Characteristics (Continued)
+
−
=
=
= = =
−5V, VCM 0V, and RL 1 kΩ. Boldface
Unless otherwise specified, all limits guaranteed for TJ 25˚C, V
limits apply at the temperature extremes
+5V, V
Typ
LM6171AI
Limit
LM6171BI
Limit
Symbol
RIN
Parameter
Input Resistance
Conditions
(Note 5)
Units
MΩ
Ω
(Note 6)
(Note 6)
Common Mode
40
4.9
14
Differential Mode
RO
Open Loop
Output Resistance
Common Mode
Rejection Ratio
Power Supply
=
±
CMRR
PSRR
VCM
VCM
2.5V
105
95
80
75
85
80
75
70
80
75
dB
min
dB
min
V
=
±
±
15V to 5V
VS
Rejection Ratio
Input Common-Mode
Voltage Range
Large Signal Voltage
Gain (Note 7)
±
CMRR ≥ 60 dB
3.7
=
AV
RL 1 kΩ
84
80
75
65
75
65
dB
min
dB
=
RL 100Ω
70
70
60
60
min
V
=
VO
Output Swing
RL 1 kΩ
3.5
−3.4
3.2
−3.0
32
3.2
3
3.2
3
min
V
−3.2
−3
−3.2
−3
max
V
=
RL 100Ω
2.8
2.5
−2.8
−2.5
28
2.8
2.5
−2.8
−2.5
28
min
V
max
mA
min
mA
max
mA
mA
mA
max
=
Sourcing, RL 100Ω
Continuous Output Current
(Open Loop) (Note 8)
25
25
=
Sinking, RL 100Ω
30
28
28
25
25
ISC
Output Short
Sourcing
Sinking
130
100
2.3
Circuit Current
Supply Current
IS
3
3
3.5
3.5
±
5V AC Electrical Characteristics
+
−
=
=
=
=
=
Unless otherwise specified, all limits guaranteed for TJ 25˚C, V
limits apply at the temperature extremes
+5V, V
−5V, VCM 0V, and RL 1 kΩ. Boldface
Typ LM6171AI LM6171BI
Symbol
Parameter
Conditions
(Note 5)
Limit
Limit
Units
(Note 6)
(Note 6)
=
=
SR
Slew Rate (Note 9)
Unity Gain-Bandwidth
Product
AV +2, VIN 3.5 VPP
750
70
V/µs
MHz
GBW
=
−3 dB Frequency
AV +1
130
45
MHz
=
AV +2
φm
Phase Margin
57
deg
ns
=
=
ts
Settling Time (0.1%)
AV −1, VOUT +1V,
60
=
RL 500Ω
=
=
±
Propagation Delay
VIN
1V, RL 500Ω,
8
ns
5
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±
5V AC Electrical Characteristics (Continued)
+
−
=
=
=
=
=
Unless otherwise specified, all limits guaranteed for TJ 25˚C, V
limits apply at the temperature extremes
+5V, V
−5V, VCM 0V, and RL 1 kΩ. Boldface
Typ LM6171AI LM6171BI
Symbol
Parameter
Conditions
(Note 5)
Limit
Limit
Units
(Note 6)
(Note 6)
=
AV −2
AD
φD
en
Differential Gain (Note 10)
Differential Phase (Note 10)
Input-Referred
0.04
0.7
11
%
deg
=
=
f
f
1 kHz
1 kHz
Voltage Noise
in
Input-Referred
1
Current Noise
Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is in-
tended to be functional, but specific performance is not guaranteed. For guaranteed specifications and the test conditions, see the Electrical Characteristics.
Note 2: Human body model, 1.5 kΩ in series with 100 pF.
Note 3: Continuous short circuit operation at elevated ambient temperature can result in exceeding the maximum allowed junction temperature of 150˚C.
=
, θ , and T . The maximum allowable power dissipation at any ambient temperature is P
A D
Note 4: The maximum power dissipation is a function of T
J(max) JA
(T
−
T
)/θ . All numbers apply for packages soldered directly into a PC board.
J(max)
A JA
Note 5: Typical Values represent the most likely parametric norm.
Note 6: All limits are guaranteed by testing or statistical analysis.
=
=
=
5V. For V +5V,
S
±
±
Note 7: Large signal voltage gain is the total output swing divided by the input signal required to produce that swing. For V
15V, V
OUT
S
=
±
V
1V.
OUT
Note 8: The open loop output current is the output swing with the 100Ω load resistor divided by that resistor.
Note 9: Slew rate is the average of the rising and falling slew rates.
=
=
1 V at 3.58 MHz and both input and output 75Ω terminated.
Note 10: Differential gain and phase are measured with A
+2, V
IN
V
PP
=
±
Note 11: Differential input voltage is measured at V
15V.
S
=
Typical Performance Characteristics Unless otherwise noted, TA 25˚C
Supply Current vs
Supply Voltage
Supply Current vs
Temperature
Input Offset Voltage vs
Temperature
DS012336-22
DS012336-20
DS012336-21
Input Bias Current
vs Temperature
Input Offset Voltage vs
Common Mode Voltage
Short Circuit Current
vs Temperature (Sourcing)
DS012336-25
DS012336-23
DS012336-24
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=
Typical Performance Characteristics Unless otherwise noted, TA 25˚C (Continued)
Short Circuit Current
Output Voltage
Output Voltage
vs Temperature (Sinking)
vs Output Current
vs Output Current
DS012336-26
DS012336-27
DS012336-28
CMRR vs Frequency
PSRR vs Frequency
PSRR vs Frequency
DS012336-29
DS012336-30
DS012336-31
Open Loop
Frequency Response
Open Loop
Frequency Response
Gain Bandwidth Product
vs Supply Voltage
DS012336-32
DS012336-33
DS012336-34
7
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=
Typical Performance Characteristics Unless otherwise noted, TA 25˚C (Continued)
Gain Bandwidth
Large Signal
Large Signal
Product vs
Load Capacitance
Voltage Gain
vs Load
Voltage Gain
vs Load
DS012336-35
DS012336-36
DS012336-37
Input Voltage Noise
vs Frequency
Input Voltage Noise
vs Frequency
Input Current Noise
vs Frequency
DS012336-38
DS012336-39
DS012336-40
Input Current Noise
vs Frequency
Slew Rate vs
Supply Voltage
Slew Rate vs
Input Voltage
DS012336-42
DS012336-41
DS012336-43
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=
Typical Performance Characteristics Unless otherwise noted, TA 25˚C (Continued)
Slew Rate vs
Open Loop Output
Open Loop Output
Load Capacitance
Impedance vs Frequency
Impedance vs Frequency
DS012336-44
DS012336-45
DS012336-46
Large Signal
Pulse Response
Large Signal
Pulse Response
Large Signal
Pulse Response
=
=
±
AV −1, VS
15V
=
=
±
AV −1, VS
5V
=
=
±
AV +1, VS
15V
DS012336-47
DS012336-48
DS012336-49
Large Signal
Pulse Response
Large Signal
Pulse Response
Large Signal
Pulse Response
=
=
±
AV +1, VS
5V
=
=
±
AV +2, VS
15V
=
=
±
AV +2, VS
5V
DS012336-50
DS012336-51
DS012336-52
9
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=
Typical Performance Characteristics Unless otherwise noted, TA 25˚C (Continued)
Small Signal
Pulse Response
Small Signal
Pulse Response
Small Signal
Pulse Response
=
=
±
AV −1, VS
15V
=
=
±
AV −1, VS
5V
=
=
±
AV +1, VS
15V
DS012336-53
DS012336-54
DS012336-55
Small Signal
Pulse Response
Small Signal
Pulse Response
Small Signal
Pulse Response
=
=
±
AV +1, VS
5V
=
=
±
AV +2, VS
15V
=
=
±
AV +2, VS
5V
DS012336-56
DS012336-57
DS012336-58
Closed Loop Frequency
Response vs Supply
Closed Loop Frequency
Response vs Supply
Closed Loop Frequency
Response vs Capacitive
=
Voltage (AV +1)
=
Voltage (AV +2)
=
Load (AV +1)
DS012336-59
DS012336-60
DS012336-61
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=
Typical Performance Characteristics Unless otherwise noted, TA 25˚C (Continued)
Closed Loop Frequency
Response vs Capacitive
Closed Loop Frequency
Response vs Capacitive
Closed Loop Frequency
Response vs Capacitive
=
Load (AV +1)
=
Load (AV +2)
=
Load (AV +2)
DS012336-62
DS012336-63
DS012336-64
DS012336-67
DS012336-70
Total Harmonic Distortion
vs Frequency
Total Harmonic Distortion
vs Frequency
Total Harmonic Distortion
vs Frequency
DS012336-65
DS012336-66
Total Harmonic Distortion
vs Frequency
Undistorted Output Swing
vs Frequency
Undistorted Output Swing
vs Frequency
DS012336-68
DS012336-69
11
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=
Typical Performance Characteristics Unless otherwise noted, TA 25˚C (Continued)
Undistorted Output Swing
vs Frequency
Undistorted Output Swing
vs Frequency
Total Power
Dissipation vs
Ambient Temperature
DS012336-71
DS012336-72
DS012336-73
LM6171 Simplified Schematic
DS012336-10
Application Information
LM6171 Performance Discussion
LM6171 Circuit Operation
The LM6171 is a high speed, unity-gain stable voltage feed-
back amplifier. It consumes only 2.5 mA supply current while
providing a gain-bandwidth product of 100 MHz and a slew
rate of 3600V/µs. It also has other great features such as low
differential gain and phase and high output current. The
LM6171 is a good choice in high speed circuits.
The class AB input stage in LM6171 is fully symmetrical and
has a similar slewing characteristic to the current feedback
amplifiers. In the LM6171 Simplfied Schematic, Q1 through
Q4 form the equivalent of the current feedback input buffer,
R
E the equivalent of the feedback resistor, and stage A buff-
ers the inverting input. The triple-buffered output stage iso-
lates the gain stage from the load to provide low output im-
pedance.
The LM6171 is a true voltage feedback amplifier. Unlike cur-
rent feedback amplifiers (CFAs) with a low inverting input im-
pedance and a high non-inverting input impedance, both in-
puts of voltage feedback amplifiers (VFAs) have high
impedance nodes. The low impedance inverting input in
CFAs will couple with feedback capacitor and cause oscilla-
tion. As a result, CFAs cannot be used in traditional op amp
circuits such as photodiode amplifiers, I-to-V converters and
integrators.
LM6171 Slew Rate Characteristic
The slew rate of LM6171 is determined by the current avail-
able to charge and discharge an internal high impedance
node capacitor. The current is the differential input voltage
divided by the total degeneration resistor RE. Therefore, the
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12
Application Information (Continued)
slew rate is proportional to the input voltage level, and the
higher slew rates are achievable in the lower gain configura-
tions.
When a very fast large signal pulse is applied to the input of
an amplifier, some overshoot or undershoot occurs. By plac-
ing an external series resistor such as 1 kΩ to the input of
LM6171, the bandwidth is reduced to help lower the over-
shoot.
DS012336-11
Layout Consideration
FIGURE 1. Compensating for Input Capacitance
PRINTED CIRCUIT BOARDS AND HIGH SPEED OP
AMPS
Power Supply Bypassing
There are many things to consider when designing PC
boards for high speed op amps. Without proper caution, it is
very easy and frustrating to have excessive ringing, oscilla-
tion and other degraded AC performance in high speed cir-
cuits. As a rule, the signal traces should be short and wide to
provide low inductance and low impedance paths. Any un-
used board space needs to be grounded to reduce stray sig-
nal pickup. Critical components should also be grounded at
a common point to eliminate voltage drop. Sockets add ca-
pacitance to the board and can affect frequency perfor-
mance. It is better to solder the amplifier directly into the PC
board without using any socket.
Bypassing the power supply is necessary to maintain low
power supply impedance across frequency. Both positive
and negative power supplies should be bypassed individu-
ally by placing 0.01 µF ceramic capacitors directly to power
supply pins and 2.2 µF tantalum capacitors close to the
power supply pins.
USING PROBES
Active (FET) probes are ideal for taking high frequency mea-
surements because they have wide bandwidth, high input
impedance and low input capacitance. However, the probe
ground leads provide a long ground loop that will produce er-
rors in measurement. Instead, the probes can be grounded
directly by removing the ground leads and probe jackets and
using scope probe jacks.
COMPONENTS SELECTION AND FEEDBACK
RESISTOR
DS012336-12
FIGURE 2. Power Supply Bypassing
It is important in high speed applications to keep all compo-
nent leads short because wires are inductive at high fre-
quency. For discrete components, choose carbon
composition-type resistors and mica-type capacitors. Sur-
face mount components are preferred over discrete compo-
nents for minimum inductive effect.
Termination
In high frequency applications, reflections occur if signals
are not properly terminated. Figure 3 shows a properly termi-
nated signal while Figure 4 shows an improperly terminated
signal.
Large values of feedback resistors can couple with parasitic
capacitance and cause undesirable effects such as ringing
or oscillation in high speed amplifiers. For LM6171, a feed-
back resistor of 510Ω gives optimal performance.
Compensation for Input
Capacitance
The combination of an amplifier’s input capacitance with the
gain setting resistors adds a pole that can cause peaking or
oscillation. To solve this problem, a feedback capacitor with
a value
>
CF (RG x CIN)/RF
can be used to cancel that pole. For LM6171, a feedback ca-
pacitor of 2 pF is recommended. Figure 1 illustrates the com-
pensation circuit.
DS012336-14
FIGURE 3. Properly Terminated Signal
13
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Application Information (Continued)
DS012336-13
FIGURE 5. Isolation Resistor Used
to Drive Capacitive Load
DS012336-15
FIGURE 4. Improperly Terminated Signal
To minimize reflection, coaxial cable with matching charac-
teristic impedance to the signal source should be used. The
other end of the cable should be terminated with the same
value terminator or resistor. For the commonly used cables,
RG59 has 75Ω characteristic impedance, and RG58 has
50Ω characteristic impedance.
DS012336-16
Driving Capacitive Loads
Amplifiers driving capacitive loads can oscillate or have ring-
ing at the output. To eliminate oscillation or reduce ringing,
an isolation resistor can be placed as shown below in Figure
5. The combination of the isolation resistor and the load ca-
pacitor forms a pole to increase stablility by adding more
phase margin to the overall system. The desired perfor-
mance depends on the value of the isolation resistor; the big-
ger the isolation resistor, the more damped the pulse re-
sponse becomes. For LM6171, a 50Ω isolation resistor is
FIGURE 6. The LM6171 Driving a 200 pF Load
with a 50Ω Isolation Resistor
Power Dissipation
The maximum power allowed to dissipate in a device is de-
fined as:
=
PD (TJ(max) − TA)/θJA
Where PD is the power dissipation in a device
TJ(max) is the maximum junction temperature
TA is the ambient temperature
recommended for initial evaluation. Figure
6 shows the
LM6171 driving a 200 pF load with the 50Ω isolation resistor.
θJA is the thermal resistance of a particular package
For example, for the LM6171 in a SO-8 package, the maxi-
mum power dissipation at 25˚C ambient temperature is
730 mW.
Thermal resistance, θJA, depends on parameters such as
die size, package size and package material. The smaller
the die size and package, the higher θJA becomes. The 8-pin
DIP package has a lower thermal resistance (108˚C/W) than
that of 8-pin SO (172˚C/W). Therefore, for higher dissipation
capability, use an 8-pin DIP package.
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Application Information (Continued)
Multivibrator
The total power dissipated in a device can be calculated as:
=
PD PQ + PL
PQ is the quiescent power dissipated in a device with no load
connected at the output. PL is the power dissipated in the de-
vice with a load connected at the output; it is not the power
dissipated by the load.
Furthermore,
=
PQ
supply current x total supply voltage with no
load
=
PL
output current x (voltage difference between
supply voltage and output voltage of the same
supply)
For example, the total power dissipated by the LM6171 with
DS012336-18
=
±
VS
15V and output voltage of 10V into 1 kΩ load resistor
(one end tied to ground) is
=
=
=
=
PD
PQ + PL
(2.5 mA) x (30V) + (10 mA) x (15V − 10V)
75 mW + 50 mW
125 mW
Application Circuits
Pulse Width Modulator
Fast Instrumentation Amplifier
DS012336-19
Design Kit
A design kit is available for the LM6171. The design kit con-
tains:
DS012336-17
•
•
•
•
High Speed Evaluation Board
LM6171 in 8-pin DIP Package
LM6171 Datasheet
Pspice Macromodel Diskette With the LM6171 Macro-
model
•
An Amplifier Selection Guide
Pitch Pack
A pitch pack is available for the LM6171. The pitch pack con-
tains:
•
•
•
•
High Speed Evaluation Board
LM6171 in 8-pin DIP Package
LM6171 Datasheet
Pspice Macromodel Diskette With the LM6171 Macro-
model
Contact your local National Semiconductor sales office to
obtain a pitch pack.
15
www.national.com
Physical Dimensions inches (millimeters) unless otherwise noted
8-Pin Small Outline Package
NS Package Number M08A
8-Pin Molded DIP Package
NS Package Number N08E
www.national.com
16
Notes
LIFE SUPPORT POLICY
NATIONAL’S PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT
DEVICES OR SYSTEMS WITHOUT THE EXPRESS WRITTEN APPROVAL OF THE PRESIDENT OF NATIONAL
SEMICONDUCTOR CORPORATION. As used herein:
1. Life support devices or systems are devices or
systems which, (a) are intended for surgical implant
into the body, or (b) support or sustain life, and
whose failure to perform when properly used in
accordance with instructions for use provided in the
labeling, can be reasonably expected to result in a
significant injury to the user.
2. A critical component is any component of a life
support device or system whose failure to perform
can be reasonably expected to cause the failure of
the life support device or system, or to affect its
safety or effectiveness.
National Semiconductor
Corporation
Americas
Tel: 1-800-272-9959
Fax: 1-800-737-7018
Email: support@nsc.com
National Semiconductor
Europe
National Semiconductor
Asia Pacific Customer
Response Group
Tel: 65-2544466
Fax: 65-2504466
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Japan Ltd.
Tel: 81-3-5639-7560
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Fax: +49 (0) 1 80-530 85 86
Email: europe.support@nsc.com
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Email: sea.support@nsc.com
www.national.com
National does not assume any responsibility for use of any circuitry described, no circuit patent licenses are implied and National reserves the right at any time without notice to change said circuitry and specifications.
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