SK23 [MPS]
2A, 380 KHz Step-Down Converter; 2A ， 380千赫降压转换器
| 型号： | SK23 |
| 厂家： | 
MONOLITHIC POWER SYSTEMS |
| 描述： | 2A, 380 KHz Step-Down Converter |
| 文件： | 总10页 (文件大小：249K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
TM
MP1580
2A, 380 KHz
Step-Down Converter
TM
The Future of Analog IC Technology
DESCRIPTION
FEATURES
The MP1580 is a monolithic step-down switch
mode converter with a built in internal power
MOSFET. It achieves 2A continuous output
current over a wide input supply range with
excellent load and line regulation.
•
•
•
2A Output Current
0.18Ω Internal Power MOSFET Switch
Stable with Low ESR Output Ceramic
Capacitors
Up to 95% Efficiency
23µA Shutdown Mode
•
•
•
•
•
•
•
•
•
•
Current mode operation provides fast transient
response and eases loop stabilization.
Fixed 380KHz Frequency
Thermal Shutdown
Fault condition protection includes cycle-by-cycle
current limiting and thermal shutdown. In
shutdown mode the regulator draws 23µA of
supply current.
Cycle-by-Cycle Over Current Protection
Wide 4.75 to 25V Operating Input Range
Output Adjustable from 1.22V to 21V
Programmable Under Voltage Lockout
Frequency Synchronization Input
Available in an 8-Pin SO Package
The MP1580 requires a minimum number of
readily available standard external components. A
synchronization pin allows the part to be driven to
600KHz.
APPLICATIONS
•
•
•
Distributed Power Systems
Battery Chargers
Pre-Regulator for Linear Regulators
EVALUATION BOARD REFERENCE
Board Number
Dimensions
EV0007
2.3”X x 1.5”Y x 0.5”Z
“MPS” and “The Future of Analog IC Technology” are Trademarks of Monolithic
Power Systems, Inc.
TYPICAL APPLICATION
Efficiency vs
Output Current Voltage
C5
10nF
INPUT
95
V
= 5.0V
4.75V to 25V
OUT
2
1
IN
BS
90
85
80
75
70
V
= 3.3V
7
3
OUT
OUTPUT
2.5V / 2A
EN
SW
FB
OFF ON
D1
V
= 2.5V
MP1580
OUT
8
5
OPEN
NOT USED
SYNC
GND
4
COMP
6
C3
2.2nF
C6
OPEN
V
= 10V
IN
0
0.5
1
1.5
2
OUTPUT CURRENT (A)
MP1580_TAC_S01
MP1580_TAC_EC01
MP1580 Rev. 3.0
12/5/2005
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1
TM
MP1580 – 2A, 380KHz STEP-DOWN CONVERTER
PACKAGE REFERENCE
TOP VIEW
TOP VIEW
BS
IN
1
2
3
4
8
7
6
5
SYNC
EN
BS
IN
1
2
3
4
8
7
6
5
SYNC
EN
SW
GND
COMP
FB
SW
GND
COMP
FB
MP1580_PD01-SOIC8
MP1580_PD02-PDIP8
Part Number*
Package
Temperature
–40°C to +125°C
Part Number**
Package
PDIP8
Temperature
MP1580HS
SOIC8
MP1580HP
–40°C to +125°C
For Tape & Reel, add suffix –Z (eg. MP1580HS–Z)
For Lead Free, add suffix –LF (eg. MP1580HS –LF–Z)
** For Tape & Reel, add suffix –Z (eg. MP1580HP–Z)
*
For Lead Free, add suffix –LF (eg. MP1580HP –LF–Z)
ABSOLUTE MAXIMUM RATINGS (1)
Supply Voltage (VIN)..................................... 27V
Switch Voltage (VSW).................. –1V to VIN + 1V
Bootstrap Voltage (VBS) .......................VSW + 6V
Feedback Voltage (VFB) .................–0.3V to +6V
Enable/UVLO Voltage (VEN)...........–0.3V to +6V
Comp Voltage (VCOMP) ...................–0.3V to +6V
Sync Voltage (VSYNC)......................–0.3V to +6V
Junction Temperature............................ +150°C
Lead Temperature ................................. +260°C
Storage Temperature.............. –65°C to +150°C
Recommended Operating Conditions (2)
Input Voltage (VIN) ......................... 4.75V to 25V
Operating Temperature...............–40°C to +125°C
Thermal Resistance (3)
θJA
θJC
SOIC8....................................105..... 50... °C/W
PDIP8 .....................................95...... 55... °C/W
Notes:
1) Exceeding these ratings may damage the device.
2) The device is not guaranteed to function outside of its
operating conditions.
3) Measured on approximately 1” square of 1 oz copper.
ELECTRICAL CHARACTERISTICS
VIN = 12V, TA = +25°C, unless otherwise noted.
Parameter
Symbol Condition
Min
Typ
Max
Units
4.75V ≤ VIN ≤ 25V
VCOMP < 2V
Feedback Voltage
1.198
1.222
1.246
V
Upper Switch-On Resistance
Lower Switch-On Resistance
Upper Switch Leakage
Current Limit (4)
0.18
10
Ω
Ω
VEN = 0V, VSW = 0V
0
10
µA
A
2.4
3.0
3.6
Current Limit Gain.
Output Current to Comp Pin Voltage
1.95
A/V
Error Amplifier Voltage Gain
Error Amplifier Transconductance
Oscillator Frequency
400
770
380
35
V/V
µA/V
KHz
KHz
KHz
500
342
20
1100
418
54
∆IC = ±10µA
Short Circuit Frequency
Sync Frequency
VFB = 0V
Sync Drive 0V to 2.7V
445
600
MP1580 Rev. 3.0
12/5/2005
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TM
MP1580 – 2A, 380KHz STEP-DOWN CONVERTER
ELECTRICAL CHARACTERISTICS (continued)
VIN = 12V, TA = +25°C, unless otherwise noted.
Parameter
Symbol Condition
VFB = 1.0V
Min
Typ
Max
Units
%
Maximum Duty Cycle
90
Minimum Duty Cycle
VFB = 1.5V
0
%
EN Shutdown Threshold Voltage
Enable Pull-Up Current
EN UVLO Threshold Rising
EN UVLO Threshold Hysteresis
Supply Current (Shutdown)
Supply Current (Quiescent)
Thermal Shutdown
ICC > 100µA
VEN = 0V
0.7
1.0
1.46
2.495
210
23
1.3
1.8
2.62
V
1.15
2.37
µA
V
VEN Rising
mV
µA
mA
°C
36
VEN ≤ 0.4V
1.0
1.2
VEN ≥ 2.6V, VFB = 1.4V
160
Note:
4) Derate current limit 0.011A/°C.
PIN FUNCTIONS
Pin #
Name Description
Bootstrap (C5). This capacitor is needed to drive the power switch’s gate above the
supply voltage. It is connected between SW and BS pins to form a floating supply across
the power switch driver. The voltage across C5 is about 5V and is supplied by the internal
+5V supply when the SW pin voltage is low.
1
BS
Supply Voltage. The MP1580 operates from a +4.75V to +25V unregulated input. C1 is
needed to prevent large voltage spikes from appearing at the input.
2
3
IN
SW
Switch. This connects the inductor to either IN through M1 or to GND through M2.
Ground. This pin is the voltage reference for the regulated output voltage. For this reason
care must be taken in its layout. This node should be placed outside of the D1 to C1
ground path to prevent switching current spikes from inducing voltage noise into the part.
4
GND
Feedback. An external resistor divider from the output to GND, tapped to the FB pin sets
the output voltage. To prevent current limit run away during a short circuit fault condition
the frequency foldback comparator lowers the oscillator frequency when the FB voltage is
below 700mV.
5
FB
Compensation. This node is the output of the transconductance error amplifier and the
6
7
8
COMP input to the current comparator. Frequency compensation is done at this node by
connecting a series R-C to ground. See the compensation section for exact details.
Enable/UVLO. A voltage greater than 2.62V enables operation. For complete low current
shutdown the EN pin voltage needs to be less than 700mV.
EN
Synchronization Input. This pin is used to synchronize the internal oscillator frequency to
SYNC an external source. There is an internal 11kΩ pull down resistor to GND; therefore leave
SYNC unconnected if unused.
MP1580 Rev. 3.0
12/5/2005
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TM
MP1580 – 2A, 380KHz STEP-DOWN CONVERTER
OPERATION
The MP1580 is a current mode regulator; the
COMP pin voltage is proportional to the peak
inductor current. At the beginning of a cycle: the
upper transistor M1 is off; the lower transistor
M2 is on (refer to Figure 1); the COMP pin
voltage is higher than the current sense
amplifier output and the current comparator’s
output is low. The rising edge of the 380KHz
CLK signal sets the RS Flip-Flop. Its output
turns off M2 and turns on M1, thus connecting
the SW pin and inductor to the input supply.
The increasing inductor current is sensed and
amplified by the Current Sense Amplifier. Ramp
compensation is summed to Current Sense
Amplifier output and compared to the Error
Amplifier output by the Current Comparator.
When the Current Sense Amplifier plus Slope
Compensation signal exceeds the COMP pin
voltage, the RS Flip-Flop is reset and the
MP1580 reverts to its initial M1 off, M2 on,
state. If the Current Sense Amplifier plus Slope
Compensation signal does not exceed the
COMP voltage, then the falling edge of the CLK
resets the Flip-Flop.
The output of the Error Amplifier integrates the
voltage difference between the feedback and
the 1.222V bandgap reference. The polarity is
such that an FB pin voltage less than 1.222V
increases the COMP pin voltage. Since the
COMP pin voltage is proportional to the peak
inductor current, an increase in its voltage
increases the current delivered to the output.
The lower 10Ω switch ensures that the
bootstrap capacitor voltage is charged during
light load conditions. An external Schottky
Diode D1 carries the inductor current when M1
is off (see Figure 1).
2
8
IN
CURRENT
SENSE
AMPLIFIER
INTERNAL
REGULATORS
+
--
5V
OSCILLATOR
SYNC
SLOPE
COMP
1
3
BS
40/380kHz
CLK
+
--
+
S
R
Q
Q
SW
CURRENT
COMPARATOR
SHUTDOWN
COMPARATOR
--
0.7V
7
EN
LOCKOUT
COMPARATOR
--
+
1.8V
2.285V/
2.495V
+
--
4
GND
0.7V 1.222V
5
--
+
FREQUENCY
FOLDBACK
COMPARATOR
ERROR
AMPLIFIER
6
FB
COMP
MP1580_BD01
Figure 1—Functional Block Diagram
MP1580 Rev. 3.0
12/5/2005
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TM
MP1580 – 2A, 380KHz STEP-DOWN CONVERTER
APPLICATION INFORMATION
A good rule for determining the inductance is to
allow the peak-to-peak ripple current in the
inductor to be approximately 30% of the
maximum load current. Also, make sure that the
peak inductor current (the load current plus half
the peak-to-peak inductor ripple current) is
below the 2.4A minimum current limit.
COMPONENT SELECTION
Sync Pin Operation
The SYNC pin driving waveform should be a
square wave with a rise time less than 20ns.
The Minimum High voltage level is 2.7V and the
Low level is less than 0.8V. The frequency of
the external sync signal needs to be greater
than 445KHz.
The inductance value can be calculated by the
equation:
A rising edge on the SYNC pin forces a reset of
the oscillator. The upper transistor M1 is
switched off immediately if it is not already off.
250ns later M1 turns on connecting SW to VIN.
(VIN − VOUT
VIN × f × ∆I
)
L = VOUT
×
Where VIN is the input voltage, f is the oscillator
frequency and ∆I is the peak-to-peak inductor
ripple current. Table 1 lists a number of suitable
inductors from various manufacturers.
Setting the Output Voltage
The output voltage is set using a resistive
voltage divider from the output to FB (see
Figure 3). The voltage divider divides the output
voltage down by the ratio:
Table 1—Inductor Selection Guide
R2
Package
Dimensions
VFB = VOUT
R1+ R2
(mm)
Vendor/
Model
Core
Type Material
Core
Where VFB is the feedback voltage and VOUT is
the output voltage.
W
L
H
Sumida
CR75
CDH74
CDRH5D28 Shielded Ferrite
CDRH5D28 Shielded Ferrite
CDRH6D28 Shielded Ferrite
Thus the output voltage is:
Open
Open
Ferrite
Ferrite
7.0
7.3
5.5
5.5
6.7
7.8 5.5
8.0 5.2
5.7 5.5
5.7 5.5
6.7 3.0
R1+ R2
VOUT = 1.222 ×
R2
R2 can be as high as 100kꢀ, but a typical value
is 10kꢀ. Using this value, R1 is determined by:
CDRH104R Shielded Ferrite 10.1 10.0 3.0
R1 ≅ 8.18 × (VOUT − 1.222)
Toko
D53LC
Type A
D75C
Shielded Ferrite
Shielded Ferrite
5.0
7.6
5.0 3.0
7.6 5.1
For example, for a 3.3V output voltage, R2 is
10kꢀ and R1 is 17kꢀ.
Inductor
D104C
Shielded Ferrite 10.0 10.0 4.3
The inductor is required to supply constant
current to the output load while being driven by
the switched input voltage. A larger value
inductor results in less ripple current that in turn
results in lower output ripple voltage.
D10FL
Open
Ferrite
9.7 11.5 4.0
Coilcraft
DO3308
DO3316
Open
Open
Ferrite
Ferrite
9.4 13.0 3.0
9.4 13.0 5.1
However, the larger value inductor has a larger
physical size, higher series resistance and/or
lower saturation current. Choose an inductor
that does not saturate under the worst-case
load conditions.
MP1580 Rev. 3.0
12/5/2005
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TM
MP1580 – 2A, 380KHz STEP-DOWN CONVERTER
Input Capacitor
In the case of tantalum or low-ESR electrolytic
capacitors, the ESR dominates the impedance
at the oscillator frequency, therefore the output
ripple is calculated as:
The input current to the step-down converter is
discontinuous, so a capacitor is required to
supply the AC current to the step-down
converter while maintaining the DC input
voltage. A low ESR capacitor is required to
keep the noise at the IC to a minimum. Ceramic
capacitors are preferred, but tantalum or low-
ESR electrolytic capacitors will also suffice.
VRIPPLE ≅ ∆I×RESR
Where VRIPPLE is the output voltage ripple and
RESR is the equivalent series resistance of the
output capacitors.
The input capacitor value should be greater
than 10µF. The capacitor can be electrolytic,
tantalum or ceramic. However, since it absorbs
the input switching current it requires an
adequate ripple current rating. Its RMS current
rating should be greater than approximately 1/2
of the DC load current.
Output Rectifier Diode
The output rectifier diode supplies the current to
the inductor when the upper transistor M1 is off.
To reduce losses due to the diode forward
voltage and recovery times, use a Schottky
rectifier.
Table 2 provides the Schottky rectifier part
numbers based on the maximum input voltage
and current rating.
To ensure stable operation, C1 should be
placed as close to the IN pin as possible.
Alternately, a smaller high quality ceramic
0.1µF capacitor may be placed closer to the IN
pin and a larger capacitor placed further away.
If using this technique, it is recommended that
the larger capacitor be a tantalum or electrolytic
type capacitor. All ceramic capacitors should be
placed close to the MP1580.
Table 2—Schottky Rectifier Selection Guide
2A Load Current
VIN (Max)
Part Number
30BQ015
B220
Vendor
15V
20V
4
1
Output Capacitor
SK23
6
The output capacitor is required to maintain the
DC output voltage. Low ESR capacitors are
preferred to keep the output voltage ripple low.
The characteristics of the output capacitor also
affect the stability of the regulation control
system. Ceramic, tantalum or low ESR
electrolytic capacitors are recommended. In the
case of ceramic capacitors, the impedance at
the oscillator frequency is dominated by the
capacitance, so the output voltage ripple is
mostly independent of the ESR. The output
voltage ripple is estimated to be:
SR22
6
20BQ030
B230
4
1
26V
SK23
6
SR23
3, 6
2, 3
SS23
Table 3 lists some rectifier manufacturers.
Table 3—Schottky Diode Manufacturers
Vendor
Web Site
2
Diodes, Inc.
www.diodes.com
f
⎛
⎞
LC
⎜
⎜
⎟
⎟
VRIPPLE ≅ 1.4 × VIN
×
Fairchild Semiconductor www.fairchildsemi.com
General Semiconductor www.gensemi.com
f
⎝
⎠
Where VRIPPLE is the output ripple voltage, fLC is
the resonant frequency of the LC filter and f is
the oscillator frequency.
International Rectifier
On Semiconductor
Pan Jit International
www.irf.com
www.onsemi.com
www.panjit.com.tw
Choose a rectifier that has a maximum reverse
voltage rating greater than the maximum input
voltage, and a current rating greater than the
maximum load current.
MP1580 Rev. 3.0
12/5/2005
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TM
MP1580 – 2A, 380KHz STEP-DOWN CONVERTER
Compensation
In this case, the switching frequency is 380KHz,
so use a crossover frequency, fC, of 40KHz.
Lower crossover frequencies result in slower
response and worse transient load recovery.
Higher crossover frequencies can result in
instability.
The system stability is controlled through the
COMP pin. COMP is the output of the internal
transconductance error amplifier. A series
capacitor-resistor combination sets a pole-zero
combination to control the characteristics of the
control system.
Choosing the Compensation Components
The values of the compensation components
given in Table 4 yield a stable control loop for
the output voltage and capacitor given.
The DC loop gain is:
VFB
AVDC = RLOAD × GCS × AVEA
×
VOUT
Table 4—Compensation Values for Typical
Output Voltage/Capacitor Combinations
Where AVEA is the transconductance error
amplifier voltage gain, 400 V/V, GCS is the
current sense gain, (roughly the output current
divided by the voltage at COMP), 1.95 A/V and
RLOAD is the load resistance (VOUT / IOUT where
VOUT
2.5V 22µF Ceramic 7.5kꢀ 2.2nF None
3.3V 22µF Ceramic 10kꢀ 2nF None
15kꢀ 1.2nF None
33kꢀ 1nF None
200kꢀ 1nF 100pF
C2
R3
C3
C6
I
OUT is the output load current).
5V
22µF Ceramic
22µF Ceramic
The system has 2 poles of importance, one is
due to the compensation capacitor (C3), and
the other is due to the output capacitor (C2).
These are:
12V
560µF/6.3V
(30mꢀ ESR)
2.5V
3.3V
5V
560µF/6.3V
(30mꢀ ESR)
200kꢀ 1nF
250kꢀ 1nF
250kꢀ 1nF
82pF
56pF
27pF
GEA
fP1
=
2π× C3× AVEA
470µF/10V
(30mꢀ ESR)
Where P1 is the first pole and GEA is the error
amplifier transconductance (770µA/V).
220µF/25V
(30mꢀ ESR)
12V
and
To optimize the compensation components for
conditions not listed in Table 4, use the
following procedure:
1
2π × C2× RLOAD
fP2
=
Choose the compensation resistor to set the
desired crossover frequency. Determine the
value by the following equation:
The system has one zero of importance, due to
the compensation capacitor (C3) and the
compensation resistor (R3). The zero is:
2π × C2× fC VOUT
1
R3 =
×
fZ1
=
GEA × GCS
VFB
2π × C3×R3
If a large value capacitor (C2) with relatively
high equivalent-series-resistance (ESR) is
used, the zero due to the capacitance and ESR
of the output capacitor can be compensated by
a third pole set by R3 and C6. The pole is:
Putting in the known constants and setting the
crossover frequency to the desired 40KHz:
R3 ≈ 1.37 ×108 × C2× VOUT
Choose the compensation capacitor to set the
zero below ¼ of the crossover frequency.
Determine the value by the following equation:
1
fP3
=
2π × C6 × R3
0.22 × C2 × VOUT
The system crossover frequency (the frequency
where the loop gain drops to 1, or 0dB) is
important. A good rule of thumb is to set the
crossover frequency to approximately 1/10 of
the switching frequency.
C3 >
R3
MP1580 Rev. 3.0
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TM
MP1580 – 2A, 380KHz STEP-DOWN CONVERTER
Determine if the second compensation
capacitor, C6, is required. It is required if the
ESR zero of the output capacitor happens at
less than four times the crossover frequency.
Or:
Negative Output Voltage
The MP1580 can be configured as a buck-
boost regulator to supply negative output
voltage.
Because the GND pin of the IC is now
connected to the negative output voltage, the
maximum allowable input voltage is the IC input
voltage rating (25V) minus the negative output
voltage value. A typical application circuit is
shown in Figure 3.
8π × C2× RESR × fC ≥ 1
or
7.34 ×10−5 × R3 × RESR
≥ 1
VOUT
External Bootstrap Diode
If this is the case, add the second
compensation capacitor. Determine the value
by the equation:
It is recommended that an external bootstrap
diode be added when the system has a 5V
fixed input or the power supply generates a 5V
output. This helps improve the efficiency of the
regulator. The bootstrap diode can be a low
cost one such as IN4148 or BAT54.
C2 × RESR(MAX)
C6 =
R3
Where RESR(MAX) is the maximum ESR of the
output capacitor.
5V
For example:
BS
VOUT = 3.3V
10nF
MP1580
C2= 22µF Ceramic (ESR = 10mꢀ)
SW
R3 ≈ (1.37 ×108 )× (22 ×10−6 )× (3.3) = 9.9kΩ
Use the nearest standard value of 10kꢀ.
0.22 × (22 ×10−6 )× 3.3
10 ×103
Use a standard value of 2nF
2π × C2× RESR × fC = 0.014
MP1580_F02
Figure 2—External Bootstrap Diode
This diode is also recommended for high duty
VOUT
C3 >
= 1.6nF
cycle operation (when
>65%) and high
VIN
output voltage (VOUT>12V) applications.
which is less than 1, therefore no second
compensation capacitor is required.
Table 5—Recommended Components for
Standard Output Voltages
VOUT
1.22V
1.5V
1.8V
2.5V
3.3V
5.0V
R1
L1 Minimum
6.8µH
0ꢀ
2.32kꢀ
4.75kꢀ
10.5kꢀ
16.9kꢀ
30.9kꢀ
6.8µH
10µH
10µH
15µH
22µH
MP1580 Rev. 3.0
12/5/2005
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TM
MP1580 – 2A, 380KHz STEP-DOWN CONVERTER
TYPICAL APPLICATION CIRCUITS
C5
10nF
INPUT
4.75V to 25V
2
1
IN
BS
7
3
5
OUTPUT
2.5V / 2A
EN
SW
FB
OFF ON
D1
MP1580
8
OPEN
NOT USED
SYNC
GND
4
COMP
6
C3
2.2nF
C6
OPEN
MP1580_F03
Figure 3—Application Circuit for -5V Supply
C5
10nF
INPUT
4.75V to 20V
2
1
IN
BS
7
8
3
5
EN
SW
FB
OFF ON
D1
B230
MP1580
OPEN
NOT USED
SYNC
GND
4
COMP
6
C3
10nF
C6
OPEN
OUTPUT
-5V / 0.8A
MP1580_F04
Figure 4—MP1580 with Murata 22µF/10V Ceramic Output Capacitor
MP1580 Rev. 3.0
12/5/2005
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TM
MP1580 – 2A, 380KHz STEP-DOWN CONVERTER
PACKAGE INFORMATION
SOIC8
PIN 1 IDENT.
0.229(5.820)
0.244(6.200)
0.0075(0.191)
0.0098(0.249)
0.150(3.810)
0.157(4.000)
SEE DETAIL "A"
0.011(0.280)
0.020(0.508)
x 45o
0.013(0.330)
0.020(0.508)
0.050(1.270)BSC
0.189(4.800)
0.197(5.004)
0o-8o
0.016(0.410)
0.050(1.270)
DETAIL "A"
0.049(1.250)
0.060(1.524)
0.053(1.350)
0.068(1.730)
SEATING PLANE
0.001(0.030)
0.004(0.101)
NOTE:
1) Control dimension is in inches. Dimension in bracket is millimeters.
PDIP8
NOTICE: The information in this document is subject to change without notice. Please contact MPS for current specifications.
Users should warrant and guarantee that third party Intellectual Property rights are not infringed upon when integrating MPS
products into any application. MPS will not assume any legal responsibility for any said applications.
MP1580 Rev. 3.0
12/5/2005
www.MonolithicPower.com
MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.
© 2005 MPS. All Rights Reserved.
10
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