MP8712 [MPS]
High-Efficiency, 12A, 3V-18V, Synchronous Step-Down Converter with Power Good, External Soft Start and OVP;
| 型号： | MP8712 |
| 厂家： | 
MONOLITHIC POWER SYSTEMS |
| 描述： | High-Efficiency, 12A, 3V-18V, Synchronous Step-Down Converter with Power Good, External Soft Start and OVP |
| 文件： | 总26页 (文件大小：1459K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
MP8712
High-Efficiency, 12A, 3V-18V,
Synchronous Step-Down Converter with
Power Good, External Soft Start and OVP
The Future of Analog IC Technology
DESCRIPTION
FEATURES
The MP8712 is a high-frequency, synchronous,
rectified, step-down, switch-mode converter.
The MP8712 offers a fully integrated solution
that achieves 12A of continuous and 15A of
peak output current with excellent load and line
regulation over a wide input supply range.
Wide 3V to 18V Operating Input Range
12A Continuous/15A Peak Output Current
1% Internal Reference Accuracy
Output Adjustable from 0.6V
15mΩ High-Side, 4.5mΩ Low-Side RDS(ON)
for Internal Power MOSFETs
500kHz Switching Frequency
External Soft Start (SS)
Open-Drain Power Good (PG) Indication
Output Over-Voltage Protection (OVP)
Hiccup Over-Current Protection (OCP)
Thermal Shutdown
Constant-on-time (COT) control operation
provides fast transient response. An open-drain
power good pin (PG) indicates that the output
voltage is in the nominal range. Full protection
features include over-voltage protection (OVP),
over-current protection (OCP), and thermal
shutdown.
Available in
Package
a
QFN-14 (3mmx4mm)
The MP8712 is available in a QFN-14
(3mmx4mm) package.
APPLICATIONS
Solid-State Drives (SSD)
Flat-Panel Televisions and Monitors
Set-Top Boxes
Distributed Power Systems
All MPS parts are lead-free, halogen-free, and adhere to the RoHS
directive. For MPS green status, please visit the MPS website under Quality
Assurance. “MPS” and “The Future of Analog IC Technology” are registered
trademarks of Monolithic Power Systems, Inc.
TYPICAL APPLICATION
100
96
92
88
V
=4.5V
IN
84
80
76
72
68
64
60
V
=12V
IN
V
=18V
IN
0.1
1
10
OUTPUT CURRENT (A)
MP8712 Rev.1.01
3/28/2017
www.MonolithicPower.com
MPS Proprietary Information. Patent Protected. Unauthorized Photocopy and Duplication Prohibited.
© 2017 MPS. All Rights Reserved.
1
MP8712 – 18V, 12A, SYNCHRONOUS STEP-DOWN CONVERTER
ORDERING INFORMATION
Part Number*
Package
Top Marking
MP8712GL
QFN-14 (3mmx4mm)
See Below
* For Tape & Reel, add suffix –Z (e.g. MP8712GL–Z)
TOP MARKING
MP: Product code of MP8712GL
Y: Year code
W: Week code
8712: First four digits of the part number
LLL: Lot number
PACKAGE REFERENCE
TOP VIEW
QFN-14 (3mmx4mm)
MP8712 Rev.1.01
3/28/2017
www.MonolithicPower.com
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© 2017 MPS. All Rights Reserved.
2
MP8712 – 18V, 12A, SYNCHRONOUS STEP-DOWN CONVERTER
ABSOLUTE MAXIMUM RATINGS (1)
VIN..................................................-0.3V to 19V
Thermal Resistance
QFN-14 (3mmx4mm)
θJA
θJC
V
SW................................-0.6V (-7V for <10ns) to
EV8712-L-00A....................... 30........ 6.... °C/W
(4)
VIN + 0.7V (25V for <25ns)
JESD51-7 .......................... 48....... 11... °C/W
VBST ...................................................... VSW + 4V
EN ............................................................... 18V
V
NOTES:
1) Exceeding these ratings may damage the device.
2) The maximum allowable power dissipation is a function of the
maximum junction temperature TJ (MAX), the junction-to-
ambient thermal resistance θJA, and the ambient temperature
TA. The maximum allowable continuous power dissipation at
any ambient temperature is calculated by PD (MAX) = (TJ
(MAX)-TA)/θJA. Exceeding the maximum allowable power
dissipation produces an excessive die temperature, causing
the regulator to go into thermal shutdown. Internal thermal
shutdown circuitry protects the device from permanent
damage.
VOUT............................................................. 7V
All other pins.....................................-0.3V to 4V
(2)
Continuous power dissipation (TA = +25°C)
QFN-14 (3mmx4mm)................................. 2.5W
Junction temperature................................150°C
Lead temperature .....................................260°C
Storage temperature.................. -65°C to 150°C
Recommended Operating Conditions (3)
Supply voltage (VIN).......................... 3V to 18V
Output voltage (VOUT)...................0.6V to 5.5V
Operating junction temp. (TJ)... -40°C to +125°C
3) The device is not guaranteed to function outside of its
operating conditions.
4) Highly effective thermal conductivity test board for leaded
surface-mount packages.
MP8712 Rev.1.01
3/28/2017
www.MonolithicPower.com
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© 2017 MPS. All Rights Reserved.
3
MP8712 – 18V, 12A, SYNCHRONOUS STEP-DOWN CONVERTER
ELECTRICAL CHARACTERISTICS
VIN = 12V, TJ = -40°C to +125°C (5), typical value is tested at TJ = +25°C, unless otherwise noted.
Parameter
Symbol
Condition
Min
Typ
Max
Units
Supply current (shutdown)
IIN
VEN = 0V
2.1
4
μA
No switching,
FB = 105% VREF
Supply current (quiescent)
IQ
420
600
1
μA
HS switch on resistance
LS switch on resistance
HSRDS-ON VBST-SW = 3.3V
15
mΩ
mΩ
LSRDS-ON
VCC = 3.3V
4.5
VEN = 0V, VSW = 12V,
TJ = +25°C
Switch leakage
SWLKG
μA
Low-side valley current limit
Low-side negative current limit
Low-side ZCD threshold
ILIMIT L
ILIMIT LN
IZCD
14
-3
A
A
OVP state
TJ = +25°C
200
500
500
185
50
mA
kHz
kHz
ns
fSW1
VIN = 12V, VOUT = 1V
VIN = 12V, VOUT = 5V
400
400
600
600
Switching frequency
fSW2
Minimum off time (6)
Minimum on time (6)
τOFF MIN
tON MIN
VOUT = 0.6V
ns
TJ = 25°C
594
591
600
600
10
606
609
50
Reference voltage
Vref
mV
-40°C < TJ < 125°C (5)
FB current
IFB
VOUT = 620mV
nA
V
EN rising threshold
EN threshold hysteresis
EN to GND pull-down resistor
VEN RISING
VEN HYS
REN
1.1
1.2
110
1.5
1.3
mV
Mꢀ
VIN under-voltage lockout
threshold rising
INUVVth
2.7
2.8
2.92
V
VIN under-voltage lockout
threshold hysteresis
INUVHYS
300
mV
Power good UV threshold rising
power good UV threshold falling
Power good OV threshold rising
Power good OV threshold falling
Power good deglitch time
PGVth-Hi Good
PGVth-Lo Fault
PGVth-Hi Fault
PGVth-Lo Good
PGTd
0.86
0.81
1.11
1.01
0.9
0.85
1.15
1.05
30
0.94
0.89
1.19
1.09
VOUT
VOUT
VOUT
VOUT
μs
Power good sink current
capability
VPG
Sink 4mA
0.4
V
OVP rising threshold
OVP falling threshold
OVP delay
VOVP Rise
FB
121%
106%
125%
110%
3.7
129%
114%
VREF
VREF
μs
VOVP Falling FB
τOVP
Output pin absolute OV
UVP threshold
UVP delay (6)
6.0
6.5
7.0
V
VOVP2
VFB UV th
ΤUVP
Hiccup entry
55%
60%
10
65%
VREF
μs
Soft-start current
5
7
9
μA
ISS
MP8712 Rev.1.01
www.MonolithicPower.com
4
3/28/2017
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© 2017 MPS. All Rights Reserved.
MP8712 – 18V, 12A, SYNCHRONOUS STEP-DOWN CONVERTER
ELECTRICAL CHARACTERISTICS (continued)
VIN = 12V, TJ = -40°C to +125°C (5), typical value is tested at TJ = +25°C, unless otherwise noted.
Parameter
Symbol Condition
Min
Typ
Max
Units
V
VCC voltage
VCC
3.5
VCC load regulation
Thermal shutdown (6)
Thermal hysteresis (6)
NOTES:
VCC reg
TTSD
ICC = 20mA
3
%
160
20
°C
TTSD HYS
°C
5) Not tested in production, guaranteed by over-temperature correlation.
6) Guaranteed by design and characterization tests.
MP8712 Rev.1.01
3/28/2017
www.MonolithicPower.com
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© 2017 MPS. All Rights Reserved.
5
MP8712 – 18V, 12A, SYNCHRONOUS STEP-DOWN CONVERTER
TYPICAL PERFORMANCE CHARACTERISTICS
Performance waveforms are tested on the evaluation board.
VIN = 12V, VOUT = 1V, L = 1.5µH, FS = 500kHz, TA = 25°C, unless otherwise noted.
MP8712 Rev.1.01
3/28/2017
www.MonolithicPower.com
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© 2017 MPS. All Rights Reserved.
6
MP8712 – 18V, 12A, SYNCHRONOUS STEP-DOWN CONVERTER
TYPICAL PERFORMANCE CHARACTERISTICS (continued)
Performance waveforms are tested on the evaluation board.
VIN = 12V, VOUT = 1V, L = 1.5µH, FS = 500kHz, TA = 25°C, unless otherwise noted.
100
96
92
88
84
80
76
72
68
64
60
100
96
92
88
84
80
76
72
68
64
60
100
96
92
88
84
80
76
72
68
64
60
VIN=12V
VIN=5V
VIN=12V
VIN=4.5V
VIN=4.5V
VIN=12V
VIN=18V
VIN=18V
VIN=18V
0.01
0.1
1
10
100
0.01
0.1
1
10
100
0.01
0.1
1
10
100
OUTPUT CURRENT (A)
OUTPUT CURRENT (A)
OUTPUT CURRENT (A)
Load Regulation vs.
Load Regulation vs.
Output Current
Output Current
VOUT=1V
VOUT=1.2V
100
2
2
1.6
1.2
0.8
0.4
96 VIN=7V
1.6
1.2
0.8
0.4
0
92
88
84
80
76
72
68
64
60
VIN=12V
VIN=18V
VIN=18V
VIN=4.5V
VIN=18V
VIN=4.5V
VIN=12V
VIN=12V
0
-0.4
-0.8
-1.2
-0.4
-0.8
-1.2
-1.6
-2
-1.6
-2
0
2
4
6
8
10 12
0
2
4
6
8
10 12
0.01
0.1
1
10
100
OUTPUT CURRENT (A)
OUTPUT CURRENT (A)
OUTPUT CURRENT (A)
Load Regulation vs.
Load Regulation vs.
Load Regulation vs.
Output Current
Output Current
Output Current
VOUT=1.5V
VOUT=1.8V
VOUT=2.5V
2
1.6
1.2
0.8
0.4
2
1.6
1.2
0.8
0.4
2
1.6
1.2
0.8
0.4
VIN=4.5V
VIN=18V
VIN=18V
VIN=4.5V
VIN=18V
VIN=4.5V
VIN=12V
VIN=12V
VIN=12V
0
-0.4
-0.8
-1.2
0
-0.4
-0.8
-1.2
0
-0.4
-0.8
-1.2
-1.6
-2
-1.6
-2
-1.6
-2
0
2
4
6
8
10 12
0
2
4
6
8
10 12
0
2
4
6
8
10 12
OUTPUT CURRENT (A)
OUTPUT CURRENT (A)
OUTPUT CURRENT (A)
MP8712 Rev.1.01
3/28/2017
www.MonolithicPower.com
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© 2017 MPS. All Rights Reserved.
7
MP8712 – 18V, 12A, SYNCHRONOUS STEP-DOWN CONVERTER
TYPICAL PERFORMANCE CHARACTERISTICS (continued)
Performance waveforms are tested on the evaluation board.
VIN = 12V, VOUT = 1V, L = 1.5µH, FS = 500kHz, TA = 25°C, unless otherwise noted.
MP8712 Rev.1.01
3/28/2017
www.MonolithicPower.com
MPS Proprietary Information. Patent Protected. Unauthorized Photocopy and Duplication Prohibited.
© 2017 MPS. All Rights Reserved.
8
MP8712 – 18V, 12A, SYNCHRONOUS STEP-DOWN CONVERTER
TYPICAL PERFORMANCE CHARACTERISTICS (continued)
Performance waveforms are tested on the evaluation board.
VIN = 12V, VOUT = 1V, L = 1.5µH, FS = 500kHz, TA = 25°C, unless otherwise noted.
Input/Output Ripple
Input/Output Ripple
Input/Output Ripple
I
= 0A
I
= 0A
I
= 12A
OUT
OUT
OUT
V
/AC
OUT
10mV/div.
V
/AC
V
/AC
OUT
10mV/div.
/AC
OUT
10mV/div.
/AC
V
/AC
IN
V
V
IN
IN
200mV/div.
20mV/div.
20mV/div.
V
SW
5V/div.
V
V
SW
SW
10V/div.
10V/div.
I
I
L
L
2A/div.
2A/div.
I
L
10A/div.
Start-Up through
Input Voltage
Start-Up through
Input Voltage
Shutdown through
Input Voltage
I
= 0A
I
= 12A
I
= 0A
OUT
OUT
OUT
V
V
V
OUT
OUT
OUT
500mV/div.
500mV/div.
500mV/div.
V
V
V
IN
IN
IN
10V/div.
10V/div.
10V/div.
V
V
V
PG
PG
PG
5V/div.
5V/div.
5V/div.
V
V
V
SW
SW
SW
10V/div.
10V/div.
10V/div.
I
I
L
L
5A/div.
5A/div.
I
L
10A/div.
Shutdown through
Input Voltage
Start-Up through EN
Start-Up through EN
I
= 0A
I
= 12A
OUT
OUT
I
= 12A
OUT
V
OUT
500mV/div.
V
IN
5V/div.
V
V
OUT
OUT
500mV/div.
500mV/div.
V
V
V
EN
PG
EN
5V/div.
5V/div.
5V/div.
V
V
PG
SW
V
PG
5V/div.
10V/div.
5V/div.
V
SW
10V/div.
V
SW
I
L
10V/div.
10A/div.
I
L
I
L
5A/div.
10A/div.
MP8712 Rev.1.01
3/28/2017
www.MonolithicPower.com
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© 2017 MPS. All Rights Reserved.
9
MP8712 – 18V, 12A, SYNCHRONOUS STEP-DOWN CONVERTER
TYPICAL PERFORMANCE CHARACTERISTICS (continued)
Performance waveforms are tested on the evaluation board.
VIN = 12V, VOUT = 1V, L = 1.5µH, FS = 500kHz, TA = 25°C, unless otherwise noted.
Shutdown through EN
Shutdown through EN
Load Transient
I
= 0A
I
= 12A
I
= 6A-12A
OUT
OUT
OUT
V
/AC
OUT
50mV/div.
V
V
OUT
OUT
500mV/div.
500mV/div.
V
V
EN
EN
5V/div.
5V/div.
V
V
PG
PG
5V/div.
5V/div.
V
V
SW
SW
10V/div.
10V/div.
I
OUT
I
I
L
L
5A/div.
2A/div.
10A/div.
Short-Circuit
Short-Circuit
Short-Circuit
Protection Entry
Protection Recovery
Protection Steady State
I
= 0A
I
= 0A
Short Output to GND
OUT
OUT
V
OUT
V
V
OUT
OUT
1V/div.
1V/div.
1V/div.
V
V
V
PG
PG
PG
5V/div.
5V/div.
5V/div.
V
V
V
SW
SW
SW
10V/div.
10V/div.
10V/div.
I
L
I
I
L
L
10A/div.
10A/div.
10A/div.
MP8712 Rev.1.01
3/28/2017
www.MonolithicPower.com
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© 2017 MPS. All Rights Reserved.
10
MP8712 – 18V, 12A, SYNCHRONOUS STEP-DOWN CONVERTER
TYPICAL PERFORMANCE CHARACTERISTICS (continued)
Performance waveforms are tested on the evaluation board.
VIN = 3V, VOUT = 0.9V, L = 0.47µH, FS = 500kHz, TA = 25°C, unless otherwise noted.
V
/AC
OUT
V
/AC
20mV/div.
V
/AC
OUT
20mV/div.
OUT
20mV/div.
V
/AC
IN
V
/AC
IN
V
/AC
IN
50mV/div.
50mV/div.
50mV/div.
V
SW
V
V
2V/div.
SW
SW
2V/div.
2V/div.
I
I
I
L
L
L
10A/div.
2A/div.
2A/div.
V
/AC
OUT
20mV/div.
V
V
OUT
OUT
500mV/div.
500mV/div.
V
/AC
IN
100mV/div.
V
V
IN
IN
2V/div.
2V/div.
V
V
PG
PG
2V/div.
2V/div.
V
SW
2V/div.
V
V
SW
SW
2V/div.
2V/div.
I
L
10A/div.
I
I
L
L
10A/div.
10A/div.
2μ s/div.
V
V
V
OUT
OUT
OUT
500mV/div.
500mV/div.
500mV/div.
V
IN
2V/div.
V
V
EN
IN
2V/div.
V
2V/div.
PG
V
V
2V/div.
PG
PG
2V/div.
2V/div.
V
V
V
SW
SW
SW
2V/div.
2V/div.
2V/div.
I
I
I
L
L
L
10A/div.
10A/div.
10A/div.
MP8712 Rev.1.01
3/28/2017
www.MonolithicPower.com
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© 2017 MPS. All Rights Reserved.
11
MP8712 – 18V, 12A, SYNCHRONOUS STEP-DOWN CONVERTER
TYPICAL PERFORMANCE CHARACTERISTICS (continued)
Performance waveforms are tested on the evaluation board.
VIN = 3V, VOUT = 0.9V, L = 0.47µH, FS = 500kHz, TA = 25°C, unless otherwise noted.
V
V
OUT
V
OUT
OUT
500mV/div.
500mV/div.
500mV/div.
V
V
EN
EN
2V/div.
2V/div.
V
EN
V
V
PG
2V/div.
PG
V
2V/div.
2V/div.
PG
2V/div.
V
V
V
SW
SW
SW
2V/div.
2V/div.
2V/div.
I
I
I
L
L
L
10A/div.
10A/div.
10A/div.
V
/AC
V
V
OUT
OUT
OUT
20mV/div.
500mV/div.
500mV/div.
V
V
PG
PG
2V/div.
2V/div.
V
V
SW
SW
2V/div.
2V/div.
I
I
I
L
OUT
L
10A/div.
5A/div.
10A/div.
V
V
OUT
OUT
500mV/div.
500mV/div.
V
V
PG
PG
2V/div.
2V/div.
V
V
SW
SW
2V/div.
2V/div.
I
I
L
L
10A/div.
10A/div.
MP8712 Rev.1.01
3/28/2017
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12
MP8712 – 18V, 12A, SYNCHRONOUS STEP-DOWN CONVERTER
PIN FUNCTIONS
QFN-14
Pin#
Name
Description
Bootstrap. A capacitor is required between SW and BST to form a floating supply across
the high-side switch driver.
1
BST
2
SW
NC
Switch output. Connect using a wide PCB trace.
No connection. Leave NC floating.
3, 4, 6
Enable. Drive EN high to enable the MP8712. EN has a 1.5Mꢀ internal pull-down resistor
to GND. EN is a high-voltage pin and can be connected to VIN directly for auto start-up.
5
7
EN
PG
Power good indication. PG is an open-drain structure. PG is de-asserted if the output
voltage is out of the regulation window.
System power ground. PGND is the reference ground of the regulated output voltage.
PGND requires special consideration during the PCB layout. Connect PGND to the
ground plane with copper traces and vias.
8
PGND
Supply voltage. The MP8712 operates from a 3V to 18V input rail. VIN requires a
ceramic capacitor to decouple the input rail. Connect VIN using a wide PCB trace.
9
VIN
VOUT
FB
10
11
Output voltage sense. Connect VOUT to the positive terminal of the load.
Feedback. Connect FB to the tap of an external resistor divider from the output to GND to
set the output voltage.
12
13
SS
Soft start set-up. Connect a capacitor from SS to ground to set the soft-start time.
Internal LDO regulator output. Decouple VCC with a 0.47µF capacitor.
VCC
Signal ground. AGND is not connected to PGND internally. Ensure that AGND is
connected to PGND in the PCB layout.
14
AGND
MP8712 Rev.1.01
3/28/2017
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13
MP8712 – 18V, 12A, SYNCHRONOUS STEP-DOWN CONVERTER
BLOCK DIAGRAM
On Timer
COT
Control
1.5MΩ
Figure 1: Functional Block Diagram
MP8712 Rev.1.01
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3/28/2017
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MP8712 – 18V, 12A, SYNCHRONOUS STEP-DOWN CONVERTER
is a fairly constant 500kHz over the input
voltage range.
OPERATION
PWM Operation
Light-Load Operation
The MP8712 is a fully integrated, synchronous,
rectified, step-down, switch-mode converter.
The MP8712 uses constant-on-time (COT)
control to provide fast transient response and
ease loop stabilization. Figure 2 shows the
simplified ramp compensation block. At the
beginning of each cycle, the high-side MOSFET
(HS-FET) turns on whenever the ramp voltage
(VRAMP) is lower than the error amplifier output
voltage (VEAO), which indicates an insufficient
output voltage. The on period is determined by
both the output voltage and input voltage to
make the switching frequency fairly constant
over the input voltage range.
When the MP8712 works in light-load operation,
the MP8712 reduces the switching frequency
automatically to maintain high efficiency, and
the inductor current drops almost to zero. When
the inductor current reaches zero, the LS-FET
driver goes into tri-state (Hi-Z) (see Figure 3).
The output capacitors discharge slowly to GND
through R1 and R2. This operation improves
device efficiency greatly when the output
current is low.
After the on period elapses, the HS-FET enters
the off state. By cycling HS-FET between the
on and off states, the converter regulates the
output voltage. The integrated low-side
MOSFET (LS-FET) turns on when the HS-FET
is in its off state to minimize conduction loss.
Figure 3: Light-Load Operation
Shoot-through occurs when both the HS-FET
and LS-FET are turned on at the same time,
causing a dead short between the input and
Light-load operation is also called skip mode
since the HS-FET does not turn on as
frequently as it does during heavy-load
condition. The HS-FET turn-on frequency is a
function of the output current. As the output
current increases, the current modulator
regulation time period becomes shorter, and the
HS-FET turns on more frequently. The switching
frequency increases as well. The output current
reaches critical levels when the current
modulator time is zero and can be determined
with Equation (1):
GND.
Shoot-through
reduces
efficiency
dramatically, so the MP8712 prevents this by
generating a dead time (DT) internally between
the HS-FET off and LS-FET on time and the
LS-FET off and HS-FET on time. The MP8712
enters either heavy-load operation or light-load
operation depending on the amplitude of the
output current.
(VIN VOUT) VOUT
2LFSW VIN
IOUT
(1)
The MP8712 enters pulse-width modulation
(PWM) mode once the output current exceeds
the critical level. Afterward, the switching
frequency remains fairly constant over the
output current range.
Figure 2: Simplified Compensation Block
Switching Frequency
Operating without an External Ramp
The MP8712 uses COT control. There is no
dedicated oscillator in the IC. The input voltage
is forward fed to the one-shot on-timer through
the internal frequency resistor. The duty ratio is
kept as VOUT/VIN, and the switching frequency
The traditional COT control scheme is
intrinsically unstable if the output capacitor’s
ESR is not large enough to be an effective
current-sense resistor. Ceramic capacitors
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MP8712 – 18V, 12A, SYNCHRONOUS STEP-DOWN CONVERTER
usually cannot be used as output capacitors.
amplifier uses SS as the reference. When SS is
higher than REF, the error amplifier uses REF
as the reference.
The MP8712 has built-in internal ramp
compensation to ensure that the system is
stable even without the help of the output
capacitor’s ESR. A pure ceramic capacitor
solution can reduce output ripple, total BOM
cost, and board area significantly.
The approximate typical soft-start time can be
calculated with Equation (2):
Vref (V ) Css (nF)
(2)
tss (ms)
7 A
VCC Regulator
A 3.5V internal regulator powers most of the
If the output of the MP8712 is pre-biased to a
certain voltage during start-up, the IC disables
the switching of the high-side and low-side until
the voltage on the internal soft-start capacitor
exceeds the sensed output voltage at FB.
internal circuitries.
A
470nF decoupling
capacitor is needed to stabilize the regulator
and reduce ripple. This regulator takes the VIN
input and operates in the full VIN range. After
EN is pulled high and VIN is greater than 3.5V,
the output of the regulator is in full regulation.
When VIN is lower than 3.5V, the output
voltage decreases and follows the input voltage.
A 0.47μF ceramic capacitor is required for
decoupling purposes.
Over-Current Protection (OCP)
The MP8712 has hiccup, cycle-by-cycle, and
over-current limiting control. The current-limit
circuit employs both the high-side current limit
and the low-side (valley) current-sensing
algorithm. The MP8712 uses the RDS(ON) of the
LS-FET as a current-sensing element for the
valley current limit. If the magnitude of the high-
side current-sense signal is above the current-
limit threshold, the PWM on pulse is terminated,
and the low side is turned on. Afterward, the
inductor current is monitored by the voltage
between GND and SW. GND is used as the
positive current sensing node, so GND should
be connected to the source terminal of the
bottom MOSFET. PWM is not allowed to initiate
a new cycle before the inductor current falls to
the valley threshold.
Error Amplifier (EA)
The error amplifier (EA) compares the FB
voltage against the internal 0.6V reference
(REF) and outputs a PWM signal. The
optimized
internal
ramp
compensation
minimizes the external component count and
simplifies the control loop design.
Enable (EN)
EN is a digital control pin that turns the
regulator on and off. Drive EN high to turn on
the regulator; drive EN low to turn off the
regulator. An internal 1.5Mꢀ resistor is
connected from EN to ground. EN can operate
with an 18V input voltage, which allows EN to
be connected to VIN directly for automatic start-
up.
After the cycle-by-cycle over-current limit
occurs, the output voltage drops until VOUT is
below the under-voltage (UV) threshold,
typically 60% below the reference. Once UV is
triggered, the MP8712 enters hiccup mode to
restart the part periodically. This protection
mode is especially useful when the output is
dead-shorted to ground. The average short-
circuit current is reduced greatly to alleviate
thermal issues and protect the regulator. The
MP8712 exits hiccup mode once the over-
current condition is removed.
Under-Voltage Lockout (UVLO)
Under-voltage lockout (UVLO) protects the chip
from operating at an insufficient supply voltage.
The MP8712 UVLO comparator monitors both
the input voltage (VIN) and the output voltage
(VOUT) of the VCC regulator. The MP8712 is
active when both voltages exceed the UVLO
rising threshold.
Soft Start (SS) and Pre-Bias Start-Up
Soft start prevents the converter output voltage
from overshooting during start-up. When the
chip starts up, the internal circuitry generates a
soft-start voltage (SS) that ramps up from 0V to
VCC. When SS is lower than REF, the error
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MP8712 – 18V, 12A, SYNCHRONOUS STEP-DOWN CONVERTER
Power Good (PG)
Dynamic regulation mode is defined as turning
on the low side until the low-side negative
current limit is triggered, and then the body
diode of the HS-FET freewheels the current.
The output power charges to the input, which
may trigger a VIN OVP function. In VIN OVP,
neither the HS-FET or LS-FET turn on and stop
charging VIN to a higher voltage. If the output is
still over-voltage and the input voltage has
dropped below the VIN OVP threshold, repeat
dynamic regulation mode. If the output voltage
is lower than 110% of the internal reference
voltage, then output OVP is exited.
Power good (PG) indicates whether the output
voltage is in the normal range compared to the
internal reference voltage. PG is an open-drain
structure. An external pull-up supply is needed.
During power-up, the PG output is pulled low.
This indicates to the system to remain off and
keep the load on the output to a minimum. This
helps reduce inrush current at start-up.
When the output voltage is between 90% and
115% of the nominal voltage and the soft start
is finished, the PG signal is pulled high. When
the output voltage is lower than 85% after the
soft start finishes, the PG signal remains low.
When the output voltage is higher than 115% of
the nominal voltage, PG is switched low. The
PG signal rises high again after the output
voltage drops below 105% of the nominal
voltage.
Output Absolute Over-Voltage Protection
(OVP_ABS)
The MP8712 monitors VOUT to detect absolute
over-voltage protection. When VOUT is larger
than 6.5V, the controller enters dynamic
regulation mode. Absolute OVP can work once
both the input voltage and EN are higher than
their rising thresholds. Therefore, this function
can work even in a soft-start period.
PG uses a deglitch time whenever VOUT
crosses the UV/OV rising and falling threshold.
The PG output is pulled low immediately when
either EN UVLO, input UVLO, OCP, or OTP is
triggered.
Thermal Shutdown
Thermal shutdown prevents the chip from
operating at exceedingly high temperatures.
When the silicon die temperature exceeds
160°C, the entire chip shuts down. When the
temperature is less than its lower threshold
(typically 140°C), the chip is enabled again.
Input Over-Voltage Protection (VIN OVP)
The MP8712 monitors VIN to detect an input
over-voltage (OV) event. This function is only
active when the output is in OV. When the
output is in an over-voltage protection (OVP)
state, output discharge is enabled, charging the
input voltage high. When the input voltage
exceeds the input OVP threshold, both the HS-
FET and LS-FET stop switching.
Floating Driver and Bootstrap Charging
An external bootstrap capacitor powers the
floating power MOSFET driver. This floating
driver has its own UVLO protection. This
UVLO’s rising threshold is 2.4V with a
hysteresis of 150mV. The bootstrap capacitor
voltage is regulated internally by VIN through
Output Over-Voltage Protection (OVP)
The MP8712 monitors FB to detect an over-
voltage event. When the FB voltage becomes
higher than 125% of the internal reference
voltage, the controller enters dynamic
regulation mode, and the input voltage may be
charged up during this time. When input OVP is
triggered, the IC stops switching. Once the
input voltage drops below the VIN OVP
recovery threshold, the IC begins switching.
OVP auto-retry mode occurs only if the soft
start finishes.
D1, M1, C4, L1, and C2 (see Figure 4). If VBST
-
VSW exceeds 3.3V, U1 regulates M1 to maintain
a 3.3V BST voltage across C4.
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MP8712 – 18V, 12A, SYNCHRONOUS STEP-DOWN CONVERTER
Figure 4: Internal Bootstrap Charging Circuit
Start-Up and Shutdown
If both VIN, VCC, and EN exceed their
respective thresholds, the chip starts up. The
reference block starts first, generating stable
reference voltages and currents, and then the
internal regulator is enabled. The regulator
provides a stable supply for the remaining
circuitries. Several events can shut down the
chip: EN low, VIN low, VCC low, and thermal
shutdown. In the shutdown procedure, the
signaling path is first blocked to prevent any
fault triggering. VEAO and the internal supply rail
are then pulled down.
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MP8712 – 18V, 12A, SYNCHRONOUS STEP-DOWN CONVERTER
VOUT (V VOUT
)
APPLICATION INFORMATION
Setting the Output Voltage
IN
L1
V IL fOSC
IN
(4)
The MP8712 output voltage can be set by the
external resistor dividers. The reference voltage
is fixed at 0.6V.
Where ∆IL is the inductor ripple current.
Choose the inductor ripple current to be
approximately 30% of the maximum load
current. The maximum inductor peak current
can be calculated with Equation (5):
The feedback network is shown in Figure 5.
IL
2
IL(MAX) ILOAD
(5)
Use a larger inductor for improved efficiency
under light-load conditions below 100mA.
Selecting the Input Capacitor
The input current to the step-down converter is
Figure 5: Feedback Network
Choose R1 and R2 using Equation (3):
R1
discontinuous and therefore requires
a
capacitor to supply AC current to the step-down
converter while maintaining the DC input
voltage. Use low ESR capacitors for the best
performance. Ceramic capacitors with X5R or
X7R dielectrics are recommended because of
their low ESR and small temperature
coefficients. For most applications, use two
22µF capacitors. Since C1 absorbs the input
switching current, it requires an adequate ripple
current rating. The RMS current in the input
capacitor can be estimated with Equation (6):
R2
(3)
VOUT
1
0.6V
Table 1 lists the recommended feedback
resistor values for common output voltages.
Table 1: Resistor Selection for Common Output
Voltages (7)
Rt (kΩ) L (μH)
VOUT (V) R1 (kΩ) R2 (kΩ)
VOUT
VIN
VOUT
VIN
1.0
1.2
1.5
1.8
2.5
3.3
5
80.6
80.6
80.6
80.6
80.6
80.6
80.6
120
80.6
53.6
40.2
25.5
17.8
11
10
10
10
10
10
10
10
1.5
1.5
1.5
1.5
2.2
2.2
3.3
IC1 ILOAD
1
(6)
The worst-case condition occurs at VIN =
2VOUT, shown in Equation (7):
ILOAD
IC1
2
(7)
For simplification, choose an input capacitor
with an RMS current rating greater than half of
the maximum load current. The input capacitor
can be electrolytic, tantalum, or ceramic. When
using electrolytic or tantalum capacitors, add a
small, high-quality ceramic capacitor (e.g.:
0.1μF) placed as close to the IC as possible.
When using ceramic capacitors, ensure that
they have enough capacitance to provide a
sufficient charge to prevent excessive voltage
ripple at the input.
NOTE:
7) The recommended parameters are based on a 12V input
voltage and 22µFx4 output capacitor. Different input voltage
and output capacitor values may affect the selection of R1
and R2. For other component parameters, please refer to
the Typical Application Circuits on page 22 to page 25.
Selecting the Inductor
For most applications, use a 0.47µH to 5µH
inductor with a DC current rating at least 25%
higher than the maximum load current. For the
highest efficiency, use an inductor with a DC
resistance less than 5mꢀ.
For most designs, the inductance value can be
derived from Equation (4):
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MP8712 – 18V, 12A, SYNCHRONOUS STEP-DOWN CONVERTER
The input voltage ripple caused by capacitance
can be estimated with Equation (8):
External Bootstrap Diode
An external bootstrap diode can enhance the
efficiency of the regulator given the following
conditions:
ILOAD VOUT
V
V
1
OUT
IN
IN
fS C1
VIN
V
(8)
VOUT is 5V or 3.3V
Selecting the Output Capacitor
Duty cycle is high: D > 50%
The output capacitor (C2) maintains the DC
output voltage. Use ceramic, tantalum, or low-
ESR electrolytic capacitors. For best results,
use low ESR capacitors to keep the output
voltage ripple low. The output voltage ripple can
be estimated with Equation (9):
In these cases, add an external BST diode from
VCC to BST (see Figure 6).
External BST Diode
IN4148
BST
VCC
CBST
MP8712
VOUT
SW
VOUT
1
L
VOUT
1
R
ESR
COUT
fS L1
V
8fS C2
IN
(9)
Where L1 is the inductor value, and RESR is the
equivalent series resistance (ESR) value of the
output capacitor.
Figure 6: Optional External Bootstrap Diode to
Enhance Efficiency
The recommended external BST diode is
1N4148, and the recommended BST capacitor
value is 0.1μF to 1μF.
For ceramic capacitors, the capacitance
dominates the impedance at the switching
frequency, and the capacitance causes the
majority of the output voltage ripple. For
simplification, the output voltage ripple can be
estimated with Equation (10):
Connecting VCC to VIN at a Low Input
Voltage
VCC can be connected to VIN directly when
VIN is lower than 3.5V. This helps improve the
MP8712’s low input voltage efficiency
performance. To use this application set-up, the
VIN spike voltage must be limited below 4V;
otherwise, VCC could be damaged.
VOUT
8fS2 L1 C2
VOUT
ꢁVOUT
1
V
IN
(10)
For tantalum or electrolytic capacitors, the ESR
dominates the impedance at the switching
frequency. For simplification, the output ripple
can be approximated with Equation (11):
VOUT
VOUT
ꢁVOUT
1
RESR
fS L1
V
IN
(11)
The characteristics of the output capacitor also
affect the stability of the regulation system. The
MP8712 can be optimized for a wide range of
capacitance and ESR values.
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MP8712 – 18V, 12A, SYNCHRONOUS STEP-DOWN CONVERTER
PCB Layout Guidelines (8)
4. Add several vias close to the VIN and
PGND pads to help with thermal dissipation.
Efficient PCB layout is critical for stable
operation. A four-layer layout is strongly
recommended to achieve better thermal
performance. For best results, refer to Figure 7
and follow the guidelines below.
5. Place the input capacitors as close to VIN
and PGND as possible.
6. Place the decoupling capacitor as close to
VCC and PGND as possible.
1. Place the high current paths (PGND, VIN,
and SW) very close to the device with short,
direct, and wide traces.
7. Place the external feedback resistors next
to FB.
8. Ensure that there is no via on the FB trace.
2. Keep the VIN and PGND pads connected
with large coppers.
9. Keep the switching node (SW) short and
away from the feedback network.
3. Use at least two layers for the VIN and
PGND trace to achieve better thermal
performance.
10. Keep the BST voltage path (BST, C3, and
SW) as short as possible.
NOTE:
8) The recommended layout is based on the Typical
Application Circuits on page 22 to page 25.
Figure 7: Recommended Layout
Design Example
Table 2 is a design example following the
application guidelines for the specifications.
performance and circuit waveforms are shown
in the Typical Performance Characteristics
section. For more device applications, please
refer to the related evaluation board datasheets.
Table 2: Design Example
VIN
VOUT
IOUT
12V, 3V
1V
12A
The detailed application schematics are shown
in Figure 8 through Figure 17. The typical
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MP8712 – 18V, 12A, SYNCHRONOUS STEP-DOWN CONVERTER
TYPICAL APPLICATION CIRCUITS
R3
C3
0Ω
0.1µF
1
L1
12V
9
1.5µH
VIN
1V/12A
2
R5
499kΩ
VOUT
VOUT
VOUT
C1
C1A
C1B
0.1µF
C2
22µF
C2C
22µF
C2A
22µF
C2B
22µF
5
22µF 22µF
13
10
C5
0.47μF
RPG
100kΩ
EN
PG
C4
22pF
R1
80.6kΩ
R4
10kΩ
7
11
12
3, 4, 6
R2
120kΩ
14
8
C6
22nF
Figure 8: VIN = 12V, VOUT = 1V, IOUT = 12A
R3
0Ω
C3
0.1µF
1
L1
1.5µH
12V
9
VIN
1.2V/12A
2
R5
C1
C1A
C1B
0.1µF
499kΩ
C2
22µF
C2C
22µF
C2A
22µF
C2B
22µF
5
22µF 22µF
13
10
C5
0.47μF
RPG
100kΩ
EN
PG
C4
22pF
R1
80.6kΩ
R4
10kΩ
7
11
12
3, 4, 6
R2
80.6kΩ
14
8
C6
22nF
Figure 9: VIN = 12V, VOUT = 1.2V, IOUT = 12A
R3
0Ω
C3
0.1µF
1
L1
1.5µH
12V
9
VIN
1.5V/12A
2
R5
C1
C1A
C1B
0.1µF
499kΩ
C2
22µF
C2C
22µF
C2A
22µF
C2B
22µF
5
22µF 22µF
13
10
C5
0.47μF
RPG
100kΩ
EN
PG
C4
22pF
R1
80.6kΩ
R4
10kΩ
7
11
12
3, 4, 6
R2
53.6kΩ
14
8
C6
22nF
Figure 10: VIN = 12V, VOUT = 1.5V, IOUT = 12A
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MP8712 – 18V, 12A, SYNCHRONOUS STEP-DOWN CONVERTER
TYPICAL APPLICATION CIRCUITS (continued)
R3
C3
0Ω
0.1µF
1
L1
12V
9
1.5µH
VIN
1.8V/12A
2
R5
499kΩ
VOUT
VOUT
VOUT
C1
C1A
C1B
0.1µF
C2
22µF
C2C
22µF
C2A
22µF
C2B
22µF
5
22µF 22µF
13
10
C5
0.47μF
RPG
100kΩ
EN
PG
C4
22pF
R1
80.6kΩ
R4
10kΩ
7
11
12
3, 4, 6
R2
40.2kΩ
14
8
C6
22nF
Figure 11: VIN = 12V, VOUT = 1.8V, IOUT = 12A
R3
0Ω
C3
0.1µF
1
L1
2.2µH
12V
9
VIN
2.5V/12A
2
R5
C1
C1A
C1B
0.1µF
499kΩ
C2
22µF
C2C
22µF
C2A
22µF
C2B
22µF
5
22µF 22µF
13
10
C5
0.47μF
RPG
100kΩ
EN
PG
C4
22pF
R1
80.6kΩ
R4
10kΩ
7
11
12
3, 4, 6
R2
25.5kΩ
14
8
C6
22nF
Figure 12: VIN = 12V, VOUT = 2.5V, IOUT = 12A
R3
0Ω
C3
0.1µF
1
L1
2.2µH
12V
9
VIN
3.3V/12A
2
R5
C1
C1A
C1B
0.1µF
499kΩ
C2
22µF
C2C
22µF
C2A
22µF
C2B
22µF
5
22µF 22µF
13
10
C5
0.47μF
RPG
100kΩ
EN
PG
C4
22pF
R1
80.6kΩ
R4
10kΩ
7
11
12
3, 4, 6
R2
17.8kΩ
14
8
C6
22nF
Figure 13: VIN = 12V, VOUT = 3.3V, IOUT = 12A
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MP8712 – 18V, 12A, SYNCHRONOUS STEP-DOWN CONVERTER
TYPICAL APPLICATION CIRCUITS (continued)
R3
0Ω
C3
0.1µF
1
L1
12V
9
3.3µH
VIN
5V/12A
2
R5
499kΩ
VOUT
C1
C1A
C1B
0.1µF
C2
22µF
C2C
22µF
C2A
22µF
C2B
22µF
5
22µF 22µF
13
10
C5
0.47μF
RPG
100kΩ
EN
PG
C4
22pF
R1
80.6kΩ
R4
10kΩ
7
11
12
3, 4, 6
R2
11kΩ
14
8
C6
22nF
Figure 14: VIN = 12V, VOUT = 5V, IOUT = 12A (9)
NOTE:
9) Based on the evaluation board test result at 25°C ambient temperature. A lower input voltage will trigger over-temperature protection with
full load.
R3
C3
0Ω
0.1µF
1
L1
3V
9
0.47µH
VIN
0.9V/12A
2
R5
499kΩ
VOUT
C1A
22µF 22µF
C1B
C1C
0.1µF
C1
220µF
C2
22µF
C2C
22µF
C2A
22µF
C2B
22µF
5
13
10
C5
0.47μF
RPG
100kΩ
EN
PG
C4
NS
R1
80.6kΩ
R4
10kΩ
7
11
12
3, 4, 6
R2
162kΩ
14
8
C6
22nF
Figure 15: VIN = 3V, VOUT = 0.9V, IOUT = 12A
R3
C3
0Ω
0.1µF
1
L1
3V
9
0.47µH
VIN
1.2V/12A
2
R5
499kΩ
VOUT
C1A
22µF 22µF
C1B
C1C
0.1µF
C1
220µF
C2
22µF
C2C
22µF
C2A
22µF
C2B
22µF
5
13
10
C5
0.47μF
RPG
100kΩ
EN
PG
C4
NS
R1
80.6kΩ
R4
10kΩ
7
11
12
3, 4, 6
R2
80.6kΩ
14
8
C6
22nF
Figure 16: VIN = 3V, VOUT = 1.2V, IOUT = 12A
MP8712 Rev.1.01
3/28/2017
www.MonolithicPower.com
MPS Proprietary Information. Patent Protected. Unauthorized Photocopy and Duplication Prohibited.
© 2017 MPS. All Rights Reserved.
24
MP8712 – 18V, 12A, SYNCHRONOUS STEP-DOWN CONVERTER
TYPICAL APPLICATION CIRCUITS (continued)
R3
C3
0Ω
0.1µF
1
L1
3V
9
0.47µH
VIN
1.8V/12A
2
R5
499kΩ
VOUT
C1A
22µF 22µF
C1B
C1C
0.1µF
C1
220µF
C2
22µF
C2C
22µF
C2A
22µF
C2B
22µF
5
13
10
C5
0.47μF
RPG
100kΩ
EN
PG
C4
NS
R1
80.6kΩ
R4
10kΩ
7
11
12
3, 4, 6
R2
40.2kΩ
14
8
C6
22nF
Figure 17: VIN = 3V, VOUT = 1.8V, IOUT = 12A
MP8712 Rev.1.01
3/28/2017
www.MonolithicPower.com
MPS Proprietary Information. Patent Protected. Unauthorized Photocopy and Duplication Prohibited.
© 2017 MPS. All Rights Reserved.
25
MP8712 – 18V, 12A, SYNCHRONOUS STEP-DOWN CONVERTER
QFN-14 (3mmx4mm)
PACKAGE INFORMATION
NOTICE: The information in this document is subject to change without notice. Please contact MPS for current specifications.
Users should warrant and guarantee that third party Intellectual Property rights are not infringed upon when integrating MPS
products into any application. MPS will not assume any legal responsibility for any said applications.
MP8712 Rev.1.01
3/28/2017
www.MonolithicPower.com
MPS Proprietary Information. Patent Protected. Unauthorized Photocopy and Duplication Prohibited.
© 2017 MPS. All Rights Reserved.
26
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