MP2363DN-LF [MPS]
Switching Regulator, Current-mode, 4A, 415kHz Switching Freq-Max, PDSO8, ROHS COMPLIANT, MS-012BA, SOIC-8;
| 型号： | MP2363DN-LF |
| 厂家： | 
MONOLITHIC POWER SYSTEMS |
| 描述： | Switching Regulator, Current-mode, 4A, 415kHz Switching Freq-Max, PDSO8, ROHS COMPLIANT, MS-012BA, SOIC-8 转换器 |
| 文件： | 总11页 (文件大小：353K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
MP2363
3A, 27V, 365KHz
Step-Down Converter
The Future of Analog IC Technology
DESCRIPTION
FEATURES
The MP2363 is a non-synchronous step-down
regulator with an integrated Power MOSFET. It
achieves 3A continuous output current over a
wide input supply range with excellent load and
line regulation.
•
3A Continuous Output Current, 4A Peak
Output Current
Programmable Soft-Start
100mΩ Internal Power MOSFET Switch
Stable with Low ESR Output Ceramic
Capacitors
Up to 95% Efficiency
20µA Shutdown Mode
Fixed 365KHz frequency
Thermal Shutdown
•
•
•
Current mode operation provides fast transient
response and eases loop stabilization.
•
•
•
•
•
•
•
•
Fault condition protection includes cycle-by-
cycle current limiting and thermal shutdown.
Adjustable soft-start reduces the stress on the
input source at turn-on. In shutdown mode, the
regulator draws 20µA of supply current.
Cycle-by-Cycle Over Current Protection
Wide 4.75V to 27V Operating Input Range
Output is Adjustable From 0.92V to 21V
Under Voltage Lockout
The MP2363 requires a minimum number of
readily available external components to
complete a 3A step-down DC to DC converter
solution.
APPLICATIONS
•
•
•
Distributed Power Systems
Battery Chargers
Pre-Regulator for Linear Regulators
The MP2363 is available in an 8-pin SOIC
package.
“MPS” and “The Future of Analog IC Technology” are Registered Trademarks of
Monolithic Power Systems, Inc.
EVALUATION BOARD REFERENCE
Board Number
Dimensions
EV2363DN-00A
2.0”X x 1.9”Y x 0.4”Z
TYPICAL APPLICATION
Efficiency Curve
V
= 12V
IN
INPUT
100
90
80
70
60
50
4.75V to 27V
10nF
1
2
V
=5.0V
OUT
IN
BS
OUTPUT
2.5V
3A
7
3
5
OPEN = AUTOMATIC
EN
SW
STARTUP
MP2363
8
V
=2.5V
SS
GND
FB
OUT
COMP
4
6
V
=3.3V
OUT
B330A
6.8nF
OPEN
0
0.5 1.0 1.5 2.0 2.5 3.0 3.5
LOAD CURRENT (A)
MP2363 Rev. 1.0
6/15/2006
www.MonolithicPower.com
MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.
© 2006 MPS. All Rights Reserved.
1
MP2363 – 3A, 27V, 365KHz STEP-DOWN CONVERTER
PACKAGE REFERENCE
ABSOLUTE MAXIMUM RATINGS (1)
Supply Voltage VIN.......................–0.3V to +28V
Switch Voltage VSW................. –1V to VIN + 0.3V
Boost Voltage VBS..........VSW – 0.3V to VSW + 6V
All Other Pins.................................–0.3V to +6V
Junction Temperature...............................150°C
Lead Temperature....................................260°C
Storage Temperature .............–65°C to +150°C
TOP VIEW
BS
IN
1
2
3
4
8
7
6
5
SS
EN
SW
GND
COMP
FB
Recommended Operating Conditions (2)
Input Voltage VIN............................ 4.75V to 27V
Ambient Operating Temp ..........–40°C to +85°C
EXPOSED PAD
ON BACKSIDE
CONNECT TO PIN 4
Thermal Resistance (3)
θJA
θJC
Part Number*
MP2363DN
Package
Temperature
SOIC8N ..................................50...... 10... °C/W
SOIC8N
–40°C to +85°C
Notes:
1) Exceeding these ratings may damage the device.
2) The device is not guaranteed to function outside of its
operating conditions.
For Tape & Reel, add suffix –Z (eg. MP2363DN–Z)
For RoHS Compliant Packaging, add suffix –LF (eg.
MP2363DN–LF–Z)
*
3) Measured on approximately 1” square of 1 oz copper.
ELECTRICAL CHARACTERISTICS
VIN = 12V, TA = +25°C, unless otherwise noted.
Parameters
Symbol Condition
Min
Typ
20
Max Units
Shutdown Supply Current
Supply Current
VEN = 0V
30
µA
mA
V
VEN = 3V, VFB = 1.4V
4.75V ≤ VIN ≤ 27V
1.0
1.2
Feedback Voltage
VFB
AVEA
0.90 0.92 0.94
400
Error Amplifier Voltage Gain (4)
Error Amplifier Transconductance
High-Side Switch On-Resistance (4)
Low-Side Switch On-Resistance
High-Side Switch Leakage Current
Short Circuit Current Limit
Current Sense to COMP Transconductance
Oscillation Frequency
V/V
GEA
500
800 1120 µA/V
∆ICOMP = ±10µA
RDS(ON)1
RDS(ON)2
100
6
mΩ
Ω
VEN = 0V, VSW = 0V
0.1
5.7
7.0
365
35
10
µA
A
4.5
GCS
fS
A/V
KHz
KHz
%
315
20
415
50
Short Circuit Oscillation Frequency
Maximum Duty Cycle
Minimum On Time (4)
VFB = 0V
DMAX
TON
VFB = 0.8V
88
120
1.2
1.4
ns
EN Threshold Voltage
0.9
0.9
1.5
2.2
V
Enable Pull Up Current
VEN = 0V
µA
V
Under Voltage Lockout Threshold
Under Voltage Lockout Threshold Hysteresis
Thermal Shutdown (4)
VIN Rising
2.37 2.54 2.71
210
160
mV
°C
Note:
4) Guaranteed by design.
MP2363 Rev. 1.0
6/15/2006
www.MonolithicPower.com
MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.
© 2006 MPS. All Rights Reserved.
2
MP2363 – 3A, 27V, 365KHz STEP-DOWN CONVERTER
PIN FUNCTIONS
Pin # Name Description
High-Side Gate Drive Boost Input. BS supplies the drive for the high-side N-Channel MOSFET
switch. Connect a 10nF or greater capacitor from SW to BS to power the high-side switch.
Power Input. IN supplies the power to the IC, as well as the step-down converter switches.
Drive IN with a 4.75V to 27V power source. Bypass IN to GND with a suitably large capacitor
to eliminate noise on the input to the IC. See Input Capacitor section of Application
Information.
1
2
BS
IN
Power Switching Output. SW is the switching node that supplies power to the output. Connect
the output LC filter from SW to the output load. Note that a capacitor is required from SW to BS
to power the high-side switch.
3
4
5
SW
GND Ground. Connect the exposed pad on backside to Pin 4.
Feedback Input. FB senses the output voltage to regulate said voltage. Drive FB with a
resistive voltage divider from the output voltage. The feedback threshold is 0.92V. See Setting
the Output Voltage section of Application Information.
FB
Compensation Node. COMP is used to compensate the regulation control loop. Connect a
series RC network from COMP to GND to compensate the regulation control loop. In some
cases, an additional capacitor from COMP to GND is required. See Compensation section of
Application Information.
6
COMP
Enable Input. EN is a digital input that turns the regulator on or off. Drive EN higher than 2.71V
to turn on the regulator, lower than 0.9V to turn it off. For automatic startup, leave EN
unconnected.
Soft Start Control Input. SS controls the soft start period. Connect a capacitor from SS to GND
to set the soft-start period. Soft-start cap is always recommended to eliminate the start-up
inrush current and for a smooth start-up waveform.
7
8
EN
SS
TYPICAL PERFORMANCE CHARACTERISTICS
VIN = 12V, VOUT = 2.5V, L = 15µH, C1 = 10µF, C2 = 22µF, TA = +25°C, unless otherwise noted.
Efficiency Curve vs
Load Current
Limit Current vs
Duty Cycle
Efficiency Curve vs
Load Current
V
= 5V
V
= 3.3V
OUT
OUT
100
95
90
85
80
75
70
65
60
55
50
95
90
85
80
75
70
65
60
55
50
7.0
6.5
6.0
5.5
5.0
4.5
4.0
V
=9V
IN
V
=9V
IN
V
=12V
V
=12V
IN
IN
V
=24V
IN
V
=24V
IN
0
0.5 1.0 1.5 2.0 2.5 3.0 3.5
LOAD CURRENT (A)
0
0.1 0.2 0.3 0.4 0.5 0.6 0.7
DUTY CYCLE (%)
0
0.5 1.0 1.5 2.0 2.5 3.0 3.5
LOAD CURRENT (A)
MP2363 Rev. 1.0
6/15/2006
www.MonolithicPower.com
MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.
© 2006 MPS. All Rights Reserved.
3
MP2363 – 3A, 27V, 365KHz STEP-DOWN CONVERTER
TYPICAL PERFORMANCE CHARACTERISTICS (continued)
VIN = 12V, VOUT = 2.5V, L = 15µH, C1 = 10µF, C2 = 22µF, TA = +25°C, unless otherwise noted.
Switching Frequency vs
Die Temperature
Steady State Test
= 1.5A Resistive Load
OUT
400
390
380
370
360
350
340
330
320
I
L
1A/div.
V
OUT
AC Coupled
100mV/div.
V
OUT
10mV/div.
V
IN
200mV/div.
I
LOAD
1A/div.
V
SW
10V/div.
-20
0
20 40 60 80 100 120
-40
DIE TEMPERATURE (oC)
Startup through Enable
Steady State Test
Startup through Enable
I
= 3A Resistive Load
I
= 3A Resistive Load
OUT
I
= 1.5A Resistive Load
OUT
OUT
I
L
2A/div.
V
OUT
10mV/div.
V
V
OUT
OUT
1V/div.
1V/div.
V
IN
200mV/div.
I
L
I
L
2A/div.
1A/div.
V
SW
10V/div.
2ms/div.
4ms/div.
Shutdown through Enable
Shutdown through Enable
I
= 3A Resistive Load
I
= 1.5A Resistive Load
OUT
OUT
V
V
OUT
OUT
1V/div.
1V/div.
I
I
L
L
2A/div.
1A/div.
MP2363 Rev. 1.0
6/15/2006
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MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.
© 2006 MPS. All Rights Reserved.
4
MP2363 – 3A, 27V, 365KHz STEP-DOWN CONVERTER
OPERATION
The MP2363 is a current-mode step-down
regulator. It regulates an input voltage between
4.75V to 27V down to an output voltage as low as
0.92V, and is able to supply up to 3A of load
current.
The converter uses an internal N-Channel
MOSFET switch to step-down the input voltage
to the regulated output voltage. Since the
MOSFET requires a gate voltage greater than
the input voltage, a boost capacitor connected
between SW and BS drives the gate. The
capacitor is charged by an internal 5V supply
while SW is low.
The MP2363 uses current-mode control to
regulate the output voltage. The output voltage
is measured at the FB pin through a resistive
voltage divider and amplified through the internal
error amplifier. The output current of the
transconductance error amplifier is presented at
COMP where a network compensates the
regulation control system. The voltage at COMP
is compared to the switch current measured
internally to control the output voltage.
An internal 10ꢀ switch from SW to GND is used
to insure that SW is pulled to GND when SW is
low to fully charge the boost.capacitor.
2
IN
CURRENT
SENSE
AMPLIFIER
INTERNAL
REGULATORS
+
--
5V
OSCILLATOR
SLOPE
COMP
35KHz/
365KHz
1
3
BS
CLK
+
--
+
S
R
Q
Q
SW
CURRENT
COMPARATOR
SHUTDOWN
COMPARATOR
--
1.2V
7
EN
LOCKOUT
COMPARATOR
--
+
2.54V/
2.33V
+
--
+
4
1.8V
GND
0.35V
0.92V
FB
--
FREQUENCY
FOLDBACK
COMPARATOR
ERROR
AMPLIFIER
5
8
6
SS
COMP
Figure 1—Functional Block Diagram
MP2363 Rev. 1.0
6/15/2006
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© 2006 MPS. All Rights Reserved.
5
MP2363 – 3A, 27V, 365KHz STEP-DOWN CONVERTER
APPLICATION INFORMATION
COMPONENT SELECTION (Refer to the
Typical Application Circuit on page 10)
Choose an inductor that will not saturate under
the maximum inductor peak current. The peak
inductor current can be calculated by:
Setting the Output Voltage
⎛
⎜
⎝
⎞
VOUT
VOUT
VIN
The output voltage is set using a resistive
voltage divider from the output voltage to FB
pin. The voltage divider divides the output
voltage down to the feedback voltage by the
ratio:
⎜
⎟
⎟
⎠
ILP = ILOAD
+
× 1−
2× fS ×L
Where ILOAD is the load current and fS is the
365KHz switching frequency.
Table 1 lists a number of suitable inductors
from various manufacturers. The choice of
which style inductor to use mainly depends on
the price vs. size requirements and any EMI
requirement.
R2
VFB = VOUT
R1+ R2
Where VFB is the feedback voltage and VOUT is
the output voltage.
Thus the output voltage is:
Table 1—Inductor Selection Guide
R1+ R2
Package
Dimensions
VOUT = 0.92 ×
R2
(mm)
Vendor/
Model
Core
Type
Core
Material
A typical value for R2 can be as high as 100kꢀ,
but a typical value is 10kꢀ. Using that value, R1
is determined by:
W
L
H
Sumida
CR75
Open
Open
Ferrite
Ferrite
7.0 7.8 5.5
7.3 8.0 5.2
5.5 5.7 5.5
5.5 5.7 5.5
6.7 6.7 3.0
R1= 8.18 × (VOUT − 0.92)(kΩ)
CDH74
Inductor
CDRH5D28 Shielded Ferrite
CDRH5D28 Shielded Ferrite
CDRH6D28 Shielded Ferrite
The inductor is required to supply constant
current to the output load while being driven by
the switched input voltage. A larger value
inductor will result in less ripple current that will
result in lower output ripple voltage. However,
the larger value inductor will have a larger
physical size, higher series resistance, and/or
lower saturation current. A good rule for
determining the inductance to use is to allow
the peak-to-peak ripple current in the inductor
to be approximately 30% of the maximum
switch current limit. Also, make sure that the
peak inductor current is below the maximum
switch current limit. The inductance value can
be calculated by:
CDRH104R Shielded Ferrite 10.1 10.0 3.0
Toko
D53LC
Type A
Shielded Ferrite
Shielded Ferrite
5.0 5.0 3.0
7.6 7.6 5.1
D75C
D104C
Shielded Ferrite 10.0 10.0 4.3
D10FL
Open
Ferrite
9.7 1.5 4.0
Coilcraft
DO3308
DO3316
Open
Open
Ferrite
Ferrite
9.4 13.0 3.0
9.4 13.0 5.1
Output Rectifier Diode
⎛
⎞
⎟
⎟
⎠
VOUT
VOUT
⎜
L =
× 1−
The output rectifier diode supplies the current to
the inductor when the high-side switch is off. To
reduce losses due to the diode forward voltage
and recovery times, use a Schottky diode.
⎜
⎝
fS × ∆IL
V
IN
Where VIN is the input voltage, fS is the 365KHz
switching frequency, and ∆IL is the peak-to-
peak inductor ripple current.
MP2363 Rev. 1.0
6/15/2006
www.MonolithicPower.com
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© 2006 MPS. All Rights Reserved.
6
MP2363 – 3A, 27V, 365KHz STEP-DOWN CONVERTER
Choose a diode whose maximum reverse voltage
rating is greater than the maximum input voltage,
and whose current rating is greater than the
maximum load current. Table 2 lists example
Schottky diodes and manufacturers.
The input capacitor can be electrolytic, tantalum
or ceramic. When using electrolytic or tantalum
capacitors, a small, high quality ceramic
capacitor, i.e. 0.1µF, should be placed as close
to the IC as possible. When using ceramic
capacitors, make sure that they have enough
capacitance to provide sufficient charge to
prevent excessive voltage ripple at input. The
input voltage ripple caused by capacitance can
be estimated by:
Table 2—Diode Selection Guide
Voltage/Current
Diode
Manufacture
Rating
30V, 3A
40V, 3A
30V, 3A
40V, 3A
30V, 3A
40V, 3A
SK33
SK34
Diodes Inc.
⎛
⎜
⎝
⎞
⎟
⎟
⎠
ILOAD
VOUT
VIN
VOUT
Diodes Inc.
⎜
∆V
=
×
× 1−
IN
fS × C1
V
IN
B330
Diodes Inc.
B340
Diodes Inc.
Output Capacitor
MBRS330
MBRS340
On Semiconductor
On Semiconductor
The output capacitor (C2) is required to
maintain the DC output voltage. Ceramic,
tantalum or low ESR electrolytic capacitors are
recommended. Low ESR capacitors are
preferred to keep the output voltage ripple low.
The output voltage ripple can be estimated by:
Input Capacitor
The input current to the step-down converter is
discontinuous, therefore a capacitor is required
to supply the AC current to the step-down
converter while maintaining the DC input
voltage. Use low ESR capacitors for the best
performance. Ceramic capacitors are preferred,
but tantalum or low-ESR electrolytic capacitors
may also suffice.
⎛
⎞
⎟
⎟
⎛
⎞
⎟
⎟
⎠
VOUT
VOUT
VIN
1
⎜
⎜
∆VOUT
=
× 1−
× RESR
+
⎜
⎜
fS × L
8 × fS × C2
⎝
⎠
⎝
Where L is the inductor value and RESR is the
equivalent series resistance (ESR) value of the
output capacitor.
Since the input capacitor (C1) absorbs the input
switching current it requires an adequate ripple
current rating. The RMS current in the input
capacitor can be estimated by:
In the case of ceramic capacitors, the
impedance at the switching frequency is
dominated by the capacitance. The output
voltage ripple is mainly caused by the
capacitance. For simplification, the output
voltage ripple can be estimated by:
⎛
⎞
⎟
VOUT
VIN
VOUT
VIN
⎜
IC1 = ILOAD
×
× 1−
⎜
⎝
⎟
⎠
ILOAD is the load current, VOUT is the output
voltage, and VIN is the input voltage. The worst-
case condition occurs at VIN = 2VOUT, where:
⎛
⎜
⎝
⎞
VOUT
VOUT
VIN
⎜
⎟
⎟
⎠
∆VOUT
=
× 1−
2
8 × fS × L × C2
In the case of tantalum or electrolytic
capacitors, the ESR dominates the impedance
at the switching frequency. For simplification,
the output ripple can be approximated to:
ILOAD
IC1
=
2
For simplification, choose the input capacitor
whose RMS current rating greater than half of
the maximum load current.
VOUT
VOUT
VIN
⎛
⎞
⎟
∆VOUT
=
× 1−
× R
ESR
⎜
fS × L
⎝
⎠
The characteristics of the output capacitor also
affect the stability of the regulation system. The
MP2363 can be optimized for a wide range of
capacitance and ESR values.
MP2363 Rev. 1.0
6/15/2006
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7
MP2363 – 3A, 27V, 365KHz STEP-DOWN CONVERTER
Compensation Components
In this case, a third pole set by the
compensation capacitor (C6) and the
compensation resistor (R3) is used to
compensate the effect of the ESR zero on the
loop gain. This pole is located at:
MP2363 employs current mode control for easy
compensation and fast transient response. The
system stability and transient response are
controlled through the COMP pin. COMP pin is
the output of the internal transconductance
error amplifier. A series capacitor-resistor
combination sets a pole-zero combination to
control the characteristics of the control system.
1
fP3
=
2π × C6 × R3
The goal of compensation design is to shape
the converter transfer function to get a desired
loop gain. The system crossover frequency
where the feedback loop has the unity gain is
important.
The DC gain of the voltage feedback loop is
given by:
VFB
AVDC = RLOAD × GCS × AVEA
×
VOUT
Lower crossover frequencies result in slower
line and load transient responses, while higher
crossover frequencies can cause system
instability. A good rule of thumb is to set the
crossover frequency to approximately one-tenth
of the switching frequency. Switching frequency
for the MP2363 is 365KHz, so the desired
crossover frequency is around 36.5KHz.
Where AVEA is the error amplifier voltage gain,
400V/V; GCS is the current sense
transconductance, 7A/V, and RLOAD is the load
resistor value.
The system has two poles of importance. One
is due to the compensation capacitor (C3) and
the output resistor of error amplifier, and the
other is due to the output capacitor and the load
resistor. These poles are located at:
Table 3 lists the typical values of compensation
components for some standard output voltages
with various output capacitors and inductors.
The values of the compensation components
have been optimized for fast transient
responses and good stability at given
conditions.
GEA
fP1
=
2π× C3× AVEA
1
fP2
=
2π × C2× RLOAD
Table 3—Compensation Values for Typical
Output Voltage/Capacitor Combinations
Where
GEA
is
the
error
amplifier
transconductance, 800µA/V.
VOUT
L
C2
R3
C3
C6
The system has one zero of importance, due to
the compensation capacitor (C3) and the
compensation resistor (R3). This zero is located
at:
1.8V
4.7µH
100µF
Ceramic
5.6kꢀ 3.3nF None
2.5V
3.3V
5V
47µF
Ceramic
3.32kꢀ 6.8nF None
4.7–10µH
6.8–10µH
10–15µH
15–20µH
22µFx2 4.02kꢀ 8.2nF None
Ceramic
1
fZ1
=
2π × C3×R3
22µFx2 6.49kꢀ 10nF
Ceramic
None
The system may have another zero of
importance, if the output capacitor has a large
capacitance and/or a high ESR value. The zero,
due to the ESR and capacitance of the output
capacitor, is located at:
12V
22µFx2
Ceramic
15kꢀ 4.7nF None
1
fESR
=
2π × C2× RESR
MP2363 Rev. 1.0
6/15/2006
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© 2006 MPS. All Rights Reserved.
8
MP2363 – 3A, 27V, 365KHz STEP-DOWN CONVERTER
To optimize the compensation components for
conditions not listed in Table 2, the following
procedure can be used.
Soft-Start Capacitor
To reduce input inrush current during startup, a
programmable soft-start is provided by
connecting a capacitor (C4) from pin SS to
GND. The soft-start time is given by:
1. Choose the compensation resistor (R3) to set
the desired crossover frequency. Determine the
R3 value by the following equation:
tSS (ms) = 45 × CSS (µF)
2π × C2× fC VOUT
To reduce the susceptibility to noise, do not
leave SS pin open. Use a capacitor with small
value if you do not need soft-start function.
R3 =
×
GEA × GCS
VFB
Where fC is the desired crossover frequency
(which typically has a value no higher than
37.5KHz).
External Bootstrap Diode
It is recommended that an external bootstrap
diode be added when the system has a 5V
fixed input or the power supply generates a 5V
output. This helps improve the efficiency of the
regulator. The bootstrap diode can be a low
cost one such as IN4148 or BAT54.
2. Choose the compensation capacitor (C3) to
achieve the desired phase margin. For
applications with typical inductor values, setting
the compensation zero, fZ1, below one forth of
the crossover frequency provides sufficient
phase margin. Determine the C3 value by the
following equation:
5V
DIODE
1
4
BS
C3 >
2π × R3 × fC
10nF
MP2363
3
3. Determine if the second compensation
capacitor (C6) is required. It is required if the
ESR zero of the output capacitor is located at
less than half of the 365KHz switching
frequency, or the following relationship is valid:
SW
Figure 2—External Bootstrap Diode
This diode is also recommended for high duty
VOUT
cycle operation (when
>65%) and high
fS
2
1
<
VIN
output voltage (VOUT>12V) applications.
2π × C2× RESR
If this is the case, then add the second
compensation capacitor (C6) to set the pole fP3
at the location of the ESR zero. Determine the
C6 value by the equation:
C2 × RESR
C6 =
R3
MP2363 Rev. 1.0
6/15/2006
www.MonolithicPower.com
MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.
© 2006 MPS. All Rights Reserved.
9
MP2363 – 3A, 27V, 365KHz STEP-DOWN CONVERTER
TYPICAL APPLICATION CIRCUITS
C5
10nF
INPUT
4.75V to 27V
2
1
IN
BS
SW
OUTPUT
3.3V
3A
7
8
3
5
EN
OPEN = AUTOMATIC
STARTUP
MP2363
SS
FB
COMP
GND
4
6
C3
8.2nF
D1
B330A
C6
OPEN
Figure 3—MP2363 for 3.3V Output with 47µF, 6.3V Ceramic Output Capacitor
C5
10nF
INPUT
4.75V to 27V
2
1
IN
BS
OUTPUT
5V
3A
7
8
3
5
EN
SW
OPEN = AUTOMATIC
STARTUP
MP2363
SS
FB
GND
COMP
4
6
D1
C3
10nF
C6
OPEN
Figure 4—MP2363 for 5V Output with 47µF, 6.3V Ceramic Output Capacitor
MP2363 Rev. 1.0
6/15/2006
www.MonolithicPower.com
MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.
© 2006 MPS. All Rights Reserved.
10
MP2363 – 3A, 27V, 365KHz STEP-DOWN CONVERTER
PACKAGE INFORMATION
SOIC8N (EXPOSED PAD)
0.229(5.820)
0.244(6.200)
PIN 1 IDENT.
NOTE 4
0.150(3.810)
0.157(4.000)
0.0075(0.191)
0.0098(0.249)
SEE DETAIL "A"
NOTE 2
0.011(0.280)
0.020(0.508)
x 45o
0.013(0.330)
0.020(0.508)
0.050(1.270)BSC
0o-8o
0.016(0.410)
0.050(1.270)
DETAIL "A"
NOTE 3
0.189(4.800)
0.197(5.000)
.050
.028
0.049(1.250)
0.060(1.524)
0.053(1.350)
0.068(1.730)
0.200 (5.07 mm)
SEATING PLANE
0.001(0.030)
0.004(0.101)
0.140 (3.55mm)
0.060
Land Pattern
NOTE:
1) Control dimension is in inches. Dimension in bracket is millimeters.
2) Exposed Pad Option (N-Package) ; 2.31mm -2.79mm x 2.79mm - 3.81mm.
Recommend Solder Board Area: 2.80mm x 3.82mm = 10.7mm2 (16.6 mil2)
3) The length of the package does not include mold flash. Mold flash shall not exceed 0.006in. (0.15mm) per side.
With the mold flash included, over-all length of the package is 0.2087in. (5.3mm) max.
4) The width of the package does not include mold flash. Mold flash shall not exceed 0.10in. (0.25mm) per side.
With the mold flash included, over-all width of the package is 0.177in. (4.5mm) max.
NOTICE: The information in this document is subject to change without notice. Please contact MPS for current specifications.
Users should warrant and guarantee that third party Intellectual Property rights are not infringed upon when integrating MPS
products into any application. MPS will not assume any legal responsibility for any said applications.
MP2363 Rev. 1.0
6/15/2006
www.MonolithicPower.com
MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.
© 2006 MPS. All Rights Reserved.
11
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