MP1540 [MPS]
1.3MHz,18V Step-Up Converter; 1.3MHz ， 18V升压型转换器
| 型号： | MP1540 |
| 厂家： | 
MONOLITHIC POWER SYSTEMS |
| 描述： | 1.3MHz,18V Step-Up Converter |
| 文件： | 总8页 (文件大小：231K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
TM
MP1540
1.3MHz, 18V
Step-Up Converter
TM
The Future of Analog IC Technology
DESCRIPTION
FEATURES
The MP1540 is a 5-pin thin TSOT23 current
mode step-up converter intended for small, low
power applications. The MP1540 switches at
1.3MHz and allows the use of tiny, low cost
capacitors and inductors 2mm or less in height.
Internal soft-start results in small inrush current
and extends battery life. The MP1540 operates
from an input voltage as low as 2.5V and can
generate 12V at up to 200mA from a 5V
supply.
•
•
•
•
•
On Board Power MOSFET
Uses Tiny Capacitors and Inductors
1.3MHz Fixed Switching Frequency
Internal Soft-Start
Operates with Input Voltage as Low as
2.5V and Output Voltage as High as 18V
12V at 200mA from 5V Input
UVLO, Thermal Shutdown
•
•
•
•
Internal Current Limit
Available in a TSOT23-5 Package
The MP1540 includes under voltage lockout,
current limiting, and thermal overload
protection to prevent damage in the event of an
output overload. The MP1540 is available in a
small 5-pin TSOT23 package.
APPLICATIONS
•
•
•
•
•
•
Camera Phone Flash
Handheld Computers and PDAs
Digital Still and Video Cameras
External Modems
Small LCD Displays
White LED Driver
“MPS” and “The Future of Analog IC Technology” are Trademarks of Monolithic
Power Systems, Inc.
TYPICAL APPLICATION
D1
Efficiency vs Load Current
VIN
5V
VOUT
12V
200mA
100
95
90
85
80
75
70
65
60
55
50
V
= 5V
IN
V
= 3.3V
IN
5
1
V
= 4.2V
IN
IN
SW
4
2
OFF ON
EN
MP1540
GND
3
FB
0
75 150 225 300 375 450
LOAD CURRENT (mA)
MP1540_TAC01
MP1540_TAC_EC01
MP1540 Rev. 1.0
8/15/2005
www.MonolithicPower.com
MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.
© 2005 MPS. All Rights Reserved.
1
TM
MP1540 – 1.3MHz, 18V STEP-UP CONVERTER
PACKAGE REFERENCE
ABSOLUTE MAXIMUM RATINGS (1)
SW Pin ........................................ –0.3V to +20V
All Other Pins ............................. –0.3V to +6.5V
Junction Temperature .............................. 150°C
Lead Temperature.................................... 260°C
Storage Temperature .................. 65°C to 150°C
Recommended Operating Conditions (2)
Supply Voltage VIN ............................ 2.5V to 6V
Output Voltage VOUT ........................... 3V to 18V
Operating Temperature.............–40°C to +85°C
TOP VIEW
SW
GND
FB
1
2
3
5
IN
4
EN
MP1540_PD01_TSOT23-5
Thermal Resistance (3)
θJA
θJC
TSOT23-5.............................. 220.....110 ..°C/W
Part Number*
MP1540DJ
Package
TSOT23-5
Temperature
Notes:
1) Exceeding these ratings may damage the device.
2) The device is not guaranteed to function outside of its
operating conditions.
–40°C to +85°C
For Tape & Reel, add suffix –Z (eg. MP1540DJ–Z)
For Lead Free, add suffix –LF (eg. MP1540DJ–LF–Z)
*
3) Measured on approximately 1” square of 1 oz copper.
ELECTRICAL CHARACTERISTICS
VIN = VEN = 5V, TA = +25°C unless specified otherwise.
Parameters
Symbol Condition
Min
Typ
Max
6
Units
Operating Input Voltage
Under Voltage Lockout
VIN
2.5
V
V
2.25
92
2.45
Under Voltage Lockout
Hysteresis
mV
Supply Current (Shutdown)
Supply Current (Quiescent)
Switching Frequency
Maximum Duty Cycle
EN Threshold
VEN = 0V
VFB = 1.3V
fSW
0.1
635
1.3
85
1
µA
µA
MHz
%
850
1.6
1.0
80
VFB = 0V
VEN Rising
1.0
1.3
1.1
100
1.6
V
EN Threshold
VEN Rising, VIN = 2.5V
V
EN Hysteresis
mV
µA
V
EN Input Bias Current
FB Voltage
VEN = 0V, 6V
VFB = 1.25V
1
VFB
1.21
1.25
–30
0.65
1.9
1.29
FB Input Bias Current
SW On-Resistance (4)
SW Current Limit (4)
SW Leakage
–100
nA
Ω
RDS (ON)
A
VSW = 15V
1
µA
°C
Thermal Shutdown (4)
160
Note:
4) Guaranteed by design.
MP1540 Rev. 1.0
8/15/2005
www.MonolithicPower.com
MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.
© 2005 MPS. All Rights Reserved.
2
TM
MP1540 – 1.3MHz, 18V STEP-UP CONVERTER
TYPICAL PERFORMANCE CHARACTERISTICS
VIN = VEN = 5V, TA = +25°C unless specified otherwise.
Feedback Voltage vs
Frequency vs
Temperature
Temperature
1.270
1.6
1.5
1.4
1.3
1.2
1.1
1.0
1.260
1.250
1.240
1.230
-50
0
50
100
150
-50
0
50
100
150
TEMPERATURE (°C)
TEMPERATURE (°C)
MP1540_TPC01
MP1540_TPC02
Maximum Duty Cycle vs
Temperature
Supply Current vs
Temperature
85.0
84.6
84.2
83.8
83.4
83.0
82.6
750
700
650
600
550
500
-50
0
50
100
150
-50
0
50
100
150
TEMPERATURE (°C)
TEMPERATURE (°C)
MP1540_TPC03
MP1540_TPC04
R
vs
)
Current Limit vs
Duty Cycle
(
DS ON
Input Voltage
0.80
0.75
0.70
0.65
0.60
0.55
0.50
1.6
1.5
1.4
1.3
1.2
1.1
1.0
2
3
4
5
6
30
40
50
60
70
80
INPUT VOLTAGE (V)
DUTY CYCLE (%)
MP1540_TPC05
MP1540_TPC06
MP1540 Rev. 1.0
8/15/2005
www.MonolithicPower.com
MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.
© 2005 MPS. All Rights Reserved.
3
TM
MP1540 – 1.3MHz, 18V STEP-UP CONVERTER
PIN FUNCTIONS
Pin #
Name Pin Function
Power Switch Output. SW is the drain of the internal MOSFET switch. Connect the power
inductor and output rectifier to SW. SW can swing between GND and 20V.
1
SW
2
3
GND
FB
Ground.
Feedback Input.
Regulator On/Off Control Input. A high input at EN turns on the converter, and a low input
turns it off. When not used, connect EN to the input source for automatic startup. The EN
pin cannot be left floating.
4
5
EN
IN
Input Supply Pin. Must be locally bypassed.
OPERATION
The MP1540 uses a fixed frequency, peak
current mode boost regulator architecture to
regulate voltage at the feedback pin. The
operation of the MP1540 can be understood by
referring to the block diagram of Figure 1.
The voltage at the output of the error amplifier is
an amplified version of the difference between
the 1.25V bandgap reference voltage and the
feedback voltage. In this way the peak current
level keeps the output in regulation. If the
feedback voltage starts to drop, the output of the
error amplifier increases. This results in more
current to flow through the power MOSFET, thus
increasing the power delivered to the output.
At the start of each oscillator cycle the MOSFET
is turned on through the control circuitry. To
prevent sub-harmonic oscillations at duty cycles
greater than 50 percent, a stabilizing ramp is
added to the output of the current sense
amplifier and the result is fed into the negative
input of the PWM comparator. When this voltage
equals the output voltage of the error amplifier
the power MOSFET is turned off.
The MP1540 has internal soft start to limit the
amount of input current at startup and to also
limit the amount of overshoot on the output.
The current limit is increased by a fourth every
40µs giving a total soft start time of 120µs.
R
C
C
C
SW
1
-
3
FB
+
-
CONTROL
M1
+
LOGIC
ERROR
AMPLIFIER
PWM
COMPARATOR
1.25V
+
-
+
CURRENT
SENSE
AMPLIFIER
2
1.3MHz
OSC
GND
MP1540_F01_BD01
Figure 1—Functional Block Diagram
MP1540 Rev. 1.0
8/15/2005
www.MonolithicPower.com
MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.
© 2005 MPS. All Rights Reserved.
4
TM
MP1540 – 1.3MHz, 18V STEP-UP CONVERTER
APPLICATIONS INFORMATION
Selecting the Inductor
COMPONENT SELECTION
The inductor is required to force the output
voltage higher while being driven by the lower
input voltage. Choose an inductor that does not
saturate at the SW current limit. A good rule for
determining the inductance is to allow the peak-
to-peak ripple current to be approximately 30%-
50% of the maximum input current. Make sure
that the peak inductor current is below 75% of
the typical current limit at the duty cycle used to
prevent loss of regulation due to the current
limit variation.
Setting the Output Voltage
Set the output voltage by selecting the resistive
voltage divider ratio. Use 11.8kΩ for the low-
side resistor R2 of the voltage divider.
Determine the high-side resistor R1 by the
equation:
R2
(
VOUT - VFB
)
R1=
VFB
Where VOUT is the output voltage and VFB is the
feedback voltage.
Calculate the required inductance value L using
the equations:
For R2 = 11.8kΩ and VFB = 1.25V, then
R1 (kΩ) = 9.44kΩ (VOUT – 1.25V).
VIN(VOUT - VIN )
L =
VOUT × fSW × ∆I
Selecting the Input Capacitor
An input capacitor is required to supply the AC
ripple current to the inductor, while limiting noise
at the input source. This capacitor must have low
ESR, so ceramic is the best choice.
VOUT ×ILOAD
(MAX)
IIN(MAX)
=
VIN ×η
30% − 50% IIN(MAX)
∆I =
)
Use an input capacitor value of 4.7µF or
greater. This capacitor must be placed
physically close to the IN pin. Since it reduces
the voltage ripple seen at IN, it also reduces the
amount of EMI passed back along that line to
the other circuitry.
Where ILOAD(MAX) is the maximum load current, ∆I
is the peak-to-peak inductor ripple current and η
is efficiency. For the MP1540, 4.7µH is
recommended for input voltages less than 3.3V
and 10µH for inputs greater than 3.3V.
Selecting the Diode
Selecting the Output Capacitor
The output rectifier diode supplies current to the
inductor when the internal MOSFET is off. To
reduce losses due to diode forward voltage and
recovery time, use a Schottky diode. Choose a
diode whose maximum reverse voltage rating is
greater than the maximum output voltage. It is
recommended to choose the MBR0520 for most
applications. This diode is used for load currents
less than 500mA. If the average current is more
than 500mA the Microsemi UPS5817 is a good
choice.
A single 4.7µF to 10µF ceramic capacitor
usually provides sufficient output capacitance
for most applications. If larger amounts of
capacitance are desired for improved line
support and transient response, tantalum
capacitors can be used in parallel with the
ceramic. The impedance of the ceramic capacitor
at the switching frequency is dominated by the
capacitance, and so the output voltage ripple is
mostly independent of the ESR. The output
voltage ripple VRIPPLE is calculated as:
ILOAD
UT
VO − VIN
UT
VRIPPLE
=
VO × C2× fSW
Where VIN is the input voltage, ILOAD is the load
current, C2 is the capacitance of the output
capacitor, and fSW is the 1.3MHz switching
frequency.
MP1540 Rev. 1.0
8/15/2005
www.MonolithicPower.com
MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.
© 2005 MPS. All Rights Reserved.
5
TM
MP1540 – 1.3MHz, 18V STEP-UP CONVERTER
Compensation
To stabilize the regulation control loop, the
crossover frequency (the frequency where the
loop gain drops to 0dB or a gain of 1, indicated
as fC) should be at least one decade below the
right-half-plane zero and should be at most
75KHz. fRHPZ is at its lowest frequency at
maximum output load current (RLOAD is at a
minimum) and minimum input voltage.
The MP1540 uses an amplifier to compensate
the feedback loop rather than a traditional
transconductance amplifier like most current
mode regulators. Frequency compensation is
provided by an internal resistor and capacitor
along with an external resistor. The system
uses two poles and one zero to stabilize the
control loop. The poles are fP1 set by the output
capacitor and load resistance, and fP2 set by the
internal compensation capacitor, the gain of the
error amplifier and the resistance seen looking
out at the feedback node REQ. The zero fZ1 is set
internally around 20KHz. These are determined
by the equations:
For the MP1540 it is recommended that a 47kꢀ
to 100kꢀ resistor be placed in series with the FB
pin and the resistor divider as seen in Figure 2.
For most applications this is all that is needed for
stable operation. If greater phase margin is
needed a series resistor and capacitor can be
placed in parallel with the high-side resistor R1 as
seen in Figure 2. The pole and zero set by the
lead-lag compensation network are:
1
fP1
=
π × C2×RLOAD
1
1
fP3
=
fP2
=
⎛
⎞
⎟
2× π×
(
7.9×10−9
)
×REQ
⎜
1
1
⎜
⎟
⎟
2× π× C3× R4 +
1
1
⎜
fZ1 = 20KHz
+
+
⎜
⎝
⎟
⎠
R1 R2 R3
Where RLOAD is the load resistance and REQ is:
1
fZ2
=
(R1×R2)
(R1+ R2)
2× π× C3×
(
R1+ R4
)
REQ = R3 +
Layout Considerations
Where R1, R2, and R3 are seen in Figure 2.
The DC loop gain is:
High frequency switching regulators require
very careful layout for stable operation and low
noise. All components must be placed as close
to the IC as possible. Keep the path between
L1, D1, and C2 extremely short for minimal
noise and ringing. C1 must be placed close to
the IN pin for best decoupling. All feedback
components must be kept close to the FB pin to
prevent noise injection on the FB pin trace. The
ground return of C1 and C2 should be tied
close to the GND pin.
VIN × RLOAD × VFB
AVDC = 500 ×
2
VOUT
There is also a right-half-plane zero (fRHPZ) that
exists in all continuous mode (inductor current
does not drop to zero on each cycle) step up
converters. The frequency of the right half plane
zero is:
VIN2 ×RLOAD
fRHPZ
=
2
2× π×L × VOUT
MP1540 Rev. 1.0
8/15/2005
www.MonolithicPower.com
MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.
© 2005 MPS. All Rights Reserved.
6
TM
MP1540 – 1.3MHz, 18V STEP-UP CONVERTER
TYPICAL APPLICATIONS
D1
MBR0520L
V
OUT
V
5V
IN
12V
200mA
5
1
C3
100pF
IN
SW
4
2
OFF ON
EN
MP1540
GND
3
FB
MP1540_F02
Figure 2—VIN = 5V, VOUT = 12V, IOUT = 200mA Boost Circuit
D1
MBR0520
V
IN
3V to 5.5V
LED1
LED2
LED3
5
1
IN
SW
4
2
OFF ON
EN
MP1540
GND
3
FB
Q1
ZXMN2A03E6TA
FLASH
MP1540_F03
Figure 3—Typical Application Circuit for Driving Flashlight LEDs
(20mA Torch Current, 100mA Flash Current)
MP1540 Rev. 1.0
8/15/2005
www.MonolithicPower.com
MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.
© 2005 MPS. All Rights Reserved.
7
TM
MP1540 – 1.3MHz, 18V STEP-UP CONVERTER
PACKAGE INFORMATION
TSOT23-5
3
2.90 BSC
0.950
TYP.
0.950
TYP.
10°TYP.
(2 plcs)
C
L
+
-
4°
0°
0°
±0.10
0.400
0.25 BSC.
Gauge Plane
0.300(Min)
0.500(Max)
C
L
(5 PLCS)
SEATING PLANE
0.127 TYP.
0.00-0.10
10° TYP.
(2 plcs)
NOTE:
1. Dimensions and tolerances are as per ANSI
Y14.5M, 1994.
2. Die is facing up for mold. Die is facing
down for trim/form, ie. reverse trim/form.
3. Dimensions are exclusive of mold flash and gate burr.
4. The footlength measuring is based on the
gauge plane method.
5. All specification comply to Jedec Spec MO193 Issue C.
NOTICE: The information in this document is subject to change without notice. Please contact MPS for current specifications.
Users should warrant and guarantee that third party Intellectual Property rights are not infringed upon when integrating MPS
products into any application. MPS will not assume any legal responsibility for any said applications.
MP1540 Rev. 1.0
8/15/2005
www.MonolithicPower.com
MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.
© 2005 MPS. All Rights Reserved.
8
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