MAX9000ESA-T [MAXIM]
Analog Circuit, 1 Func, PDSO8, 0.150 INCH, MS-012A, SOIC-8;
| 型号： | MAX9000ESA-T |
| 厂家： | 
MAXIM INTEGRATED PRODUCTS |
| 描述： | Analog Circuit, 1 Func, PDSO8, 0.150 INCH, MS-012A, SOIC-8 光电二极管 |
| 文件： | 总20页 (文件大小：255K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
19-0499; Rev 1; 7/98
Lo w -P o w e r, Hig h -S p e e d , S in g le -S u p p ly
Op Am p + Co m p a ra t o r + Re fe re n c e ICs
–MAX905
Ge n e ra l De s c rip t io n
Fe a t u re s
The MAX9000 family features the combination of a high-
speed operational amplifier, a 185ns comparator, and a
precision 1.230V reference. These devices operate from a
single +2.5V to +5.5V supply and draw less than 500µA of
quiescent current. The MAX9001/MAX9004 feature a shut-
down mode that reduces supply current to 2µA and puts
the outputs into a high-impedance state, making them
ideal for portable and battery-powered applications.
♦ Op Amp + Comparator + Reference in
Space-Saving µMAX Package
♦ +2.5V to +5.5V Single-Supply Voltage Range
♦ 340µA Supply Current (MAX9002/MAX9005)
♦ Unity-Gain Stable (GBW = 1.25MHz) and
Decompensated (A ≥ 10V/V, GBW = 8MHz) Options
V
♦ Op-Amp/Comparator Outputs Swing Rail-to-Rail
The amplifiers in the MAX9000/MAX9001/MAX9002 are
unity-gain stable with a 1.25MHz gain-bandwidth product,
while the amplifiers in the MAX9003/MAX9004/MAX9005
are stable for closed-loop gains of +10V/V or greater with
an 8MHz gain-bandwidth product. The input common-
mode voltage extends from 150mV below the negative
supply to within 1.2V of the positive supply for the amplifi-
er, and to within 1.1V for the comparator. The amplifier and
♦ Ground-Sensing Inputs for Both Op Amp and
Comparator
♦ Op Amp Stable with Capacitive Loads up to 250pF
♦ Internal ±2mV Comparator Hysteresis
♦ Fast 185ns Propagation-Delay Comparator
®
♦ No Phase Reversal for Overdriven Inputs
comparator outputs can swing Rail-to-Rail and deliver up
(Both Op Amp and Comparator)
to ±2.5mA and ±4.0mA, respectively, to an external load
while maintaining excellent DC accuracy. The unique
design of the comparator output stage substantially
reduces switching current during output transitions, virtually
eliminating power-supply glitches.
♦ Internal 1.230V Precision Reference (MAX9000/
MAX9001/MAX9003/MAX9004)
±1% Initial Accuracy
Low 8ppm/°C Temperature Drift
Sink or Source up to 1mA
Stable for Capacitive Loads up to 100nF
The comparator’s ±2mV of built-in hysteresis provides
noise immunity and prevents oscillations even with a
s low-moving inp ut s ig na l. The MAX9000/MAX9001/
MAX9003/MAX9004 have an internal 1.230V ±1% preci-
sion reference with a low 8ppm/°C temperature coeffi-
cient that can sink or source up to 1mA. The amplifier and
reference are stable with capacitive loads up to 250pF
and 100nF, respectively. The comparator’s inverting input
is internally connected to the reference output in the
MAX9000/MAX9003.
Ord e rin g In fo rm a t io n
PART
TEMP. RANGE
-40°C to +85°C
-40°C to +85°C
-40°C to +85°C
-40°C to +85°C
PIN-PACKAGE
8 µMAX
8 SO
MAX9000EUA
MAX9000ESA
MAX9001EUB
MAX9001ESD
10 µMAX
14 SO
________________________Ap p lic a t io n s
Ordering Information continued at end of data sheet.
Single-Supply Zero-
Crossing Detector
Photodiode Preamps
Smart Card Readers
Infrared Receivers
for Remote Controls
Pin Configurations and Typical Operating Circuit appear at
end of data sheet.
Instruments, Terminals,
and Bar-Code Readers
Rail-to-Rail is a registered trademark of Nippon Motorola, Ltd.
Keyless Entry
Sensor Signal Detection
______________________________________________________________________________S e le c t o r Gu id e
INTERNAL
PRECISION
REFERENCE
OP-AMP GAIN
STABILITY
(V/V)
OP-AMP GAIN
BANDWIDTH
(MHz)
PART
SHUTDOWN
PIN-PACKAGE
MAX9000
MAX9001
MAX9002
MAX9003
MAX9004
MAX9005
Yes
Yes
No
1
1
No
Yes
No
1.25
1.25
1.25
8
8 SO/µMAX
10 µMAX, 14 SO
8 SO/µMAX
1
Yes
Yes
No
10
10
10
No
8 SO/µMAX
Yes
No
8
10 µMAX, 14 SO
8 SO/µMAX
8
________________________________________________________________ Maxim Integrated Products
1
For free samples & the latest literature: http://www.maxim-ic.com, or phone 1-800-998-8800.
For small orders, phone 408-737-7600 ext. 3468.
Lo w -P o w e r, Hig h -S p e e d , S in g le -S u p p ly
Op Am p + Co m p a ra t o r + Re fe re n c e ICs
ABSOLUTE MAXIMUM RATINGS
Supply Voltage (V to V ) ....................................-0.3V to +6V
10-Pin µMAX (derate 5.6mW/°C above +70°C) ............444mW
14-Pin SO (derate 8.3mW/°C above +70°C).................667mW
Operating Temperature Range
MAX900_E _ _...................................................-40°C to +85°C
Maximum Junction Temperature .....................................+150°C
Storage Temperature Range .............................-65°C to +160°C
Lead Temperature (soldering, 10sec) .............................+300°C
DD
SS
Voltage Inputs (AIN_, CIN_).............(V - 0.3V) to (V + 0.3V)
SS
DD
Output Short-Circuit Duration (AOUT, COUT, REF)...Continuous
to either V or V
SS
DD
Continuous Power Dissipation (T = +70°C)
A
8-Pin SO (derate 5.88mW/°C above +70°C).................471mW
8-Pin µMAX (derate 4.1mW/°C above +70°C) ..............330mW
Stresses beyond those listed under “Absolute Maximum Ratings” may cause permanent damage to the device. These are stress ratings only, and functional
operation of the device at these or any other conditions beyond those indicated in the operational sections of the specifications is not implied. Exposure to
absolute maximum rating conditions for extended periods may affect device reliability.
ELECTRICAL CHARACTERISTICS
(V = +2.5V to +5.5V, V = 0, SHDN = V (MAX9001/MAX9004 only), V
= 0, V
= V / 2, V
= 0 (for
DD
SS
DD
CM(OP AMP)
AOUT
DD
CM(COMP)
MAX9001/MAX9002/MAX9004/MAX9005), COUT = low, I
= 0, T = T
to T , unless otherwise noted. Typical values are
MAX
OUT(REF)
A
MIN
at V = 5V and T = +25°C.)
DD
A
PARAMETER
SYMBOL
CONDITIONS
Guaranteed by PSRR tests
MIN
TYP
MAX
5.5
UNITS
Supply Voltage Range
Supply Current
V
DD
2.5
V
V
= 3V
410
450
340
375
500
550
425
475
DD
9
MAX9000/MAX9001/
MAX9003/MAX9004
µA
µA
µA
µA
V
DD
= 5V
= 3V
= 5V
I
DD
V
DD
MAX9002/MAX9005
V
DD
Supply Current in
Shutdown
I
MAX9001/MAX9004 (V
MAX9001/MAX9004 (V
= 0)
2
1
5
SHDN
SHDN
SHDN
Shutdown Input Bias
Current
I
IN(
= 0 to V )
DD
2.5
)
SHDN
Shutdown Logic High
Shutdown Logic Low
OP AMP
V
0.7 x V
DD
V
V
IH(
)
SHDN
V
0.3 x V
DD
IL(
SHDN
)
Input Offset Voltage
V
MAX900_ES_
MAX900_ES_
±0.5
±1
±1.5
mV
OS
Input Offset Voltage
Temperature Coefficient
TCV
µV/°C
OS
Input Bias Current
Input Offset Current
Input Resistance
I
AIN+, AIN-
AIN+, AIN-
±0.05
±0.02
1000
±2
±1
nA
nA
BIAS
R
Differential or common mode
MΩ
IN
Input Common-Mode
Voltage Range
CMVR
CMRR
PSRR
Guaranteed by CMRR test
-0.15
72
V
DD
- 1.2
V
Common-Mode
Rejection Ratio
MAX900_ES_, (V - 0.15V) ≤ V ≤ (V - 1.2V),
SS
CM
DD
96
dB
V
DD
= 5.5V
Power-Supply Rejection
Ratio
V
= 2.5V to 5.5V
= 1V/V
74
100
dB
Ω
DD
Output Resistance
A
V
0.01
10
Shorted to V
Output Short-Circuit
Current
SS
mA
Shorted to V
65
DD
Disabled Mode Output
Leakage
I
OUT
V
≤ (0.3V x V ), V
= 0 to V
DD
±0.01
±1
µA
DD
AOUT
SHDN
(DISABLED)
2
_______________________________________________________________________________________
Lo w -P o w e r, Hig h -S p e e d , S in g le -S u p p ly
Op Am p + Co m p a ra t o r + Re fe re n c e ICs
–MAX905
ELECTRICAL CHARACTERISTICS (continued)
(V = +2.5V to +5.5V, V = 0, SHDN = V (MAX9001/MAX9004 only), V
= 0, V
= V / 2, V
= 0 (for
DD
SS
DD
CM(OP AMP)
AOUT
DD
CM(COMP)
MAX9001/MAX9002/MAX9004/MAX9005), COUT = low, I
= 0, T = T
to T , unless otherwise noted. Typical values are
MAX
OUT(REF)
A
MIN
at V = 5V and T = +25°C.)
DD
A
PARAMETER
SYMBOL
CONDITIONS
= 0.05V to 2.45V, R = 100kΩ
MIN
94
TYP
125
115
120
106
1
MAX
UNITS
V
AOUT
L
V
= 2.5V
= 5.5V
DD
V
= 0.2V to 2.3V, R = 1kΩ
84
AOUT
L
Large-Signal Voltage Gain
Output Voltage Swing
A
VOL
dB
V
= 0.05V to 5.4V, R = 100kΩ
94
AOUT
L
V
DD
V
= 0.25V to 5.2V, R = 1kΩ
86
AOUT
L
V
- V
5
DD
OH
R = 100kΩ
L
V
OL
1
5
V
- V
≥ 10mV
V
OL
/ V
OH
mV
AIN+
AIN-
V
- V
140
60
250
100
DD
OH
R = 1kΩ
L
V
OL
MAX9000/MAX9001/MAX9002
MAX9003/MAX9004/MAX9005
MAX9000/MAX9001/MAX9002
MAX9003/MAX9004/MAX9005
MAX9000/MAX9001/MAX9002
MAX9003/MAX9004/MAX9005
1.25
8
Gain-Bandwidth Product
Phase Margin
GBW
MHz
degrees
dB
75
80
30
Gain Margin
40
MAX9000/MAX9001/
MAX9002 (A = 1V/V)
V
0.009
0.028
0.85
6.0
f = 10kHz,
= 2Vp-p,
Total Harmonic Distortion
plus Noise
THD+N
SR
V
AOUT
%
V/µs
µs
MAX9003/MAX9004/
MAX9005 (A = 10V/V)
V
V
DD
= 5V
MAX9000/MAX9001/
MAX9002 (A = 1V/V)
V
V
DD
= 5V,
Slew Rate
V
AOUT
= 4V step
MAX9003/MAX9004/
MAX9005 (A = 10V/V)
V
MAX9000/MAX9001/
MAX9002 (A = 1V/V)
V
6.9
V
= 5V,
= 4V step
DD
Settling Time to within 0.01%
V
AOUT
MAX9003/MAX9004/
2.1
MAX9005 (A = 10V/V)
V
Input Capacitance
C
2.5
36
1
pF
nV/√Hz
fA/√Hz
µs
IN
Input Noise Voltage Density
Input Noise Current Density
Shutdown Delay Time
Enable Delay Time
V
f = 10kHz
f = 10kHz
NOISE
I
NOISE
0.2
2
µs
Power-On Time
2
µs
MAX9000/MAX9001/MAX9002 (A = 1V/V)
250
250
V
Capacitive-Load Stability
C
pF
LOAD
MAX9003/MAX9004/MAX9005 (A = 10V/V)
V
COMPARATOR
Input Offset Voltage
V
MAX900_ES_ (Notes 1, 2)
MAX900_ES_
±1
±1
4
±2
7
mV
µV/°C
mV
OS
Input Offset Voltage
Temperature Coefficient
TCV
OS
Input-Referred Hysteresis
V
= 5V (Notes 2, 3)
DD
_______________________________________________________________________________________
3
Lo w -P o w e r, Hig h -S p e e d , S in g le -S u p p ly
Op Am p + Co m p a ra t o r + Re fe re n c e ICs
ELECTRICAL CHARACTERISTICS (continued)
(V = +2.5V to +5.5V, V = 0, SHDN = V (MAX9001/MAX9004 only), V
= 0, V
= V / 2, V
= 0 (for
DD
SS
DD
CM(OP AMP)
AOUT
DD
CM(COMP)
MAX9001/MAX9002/MAX9004/MAX9005), COUT = low, I
= 0, T = T
to T , unless otherwise noted. Typical values are
MAX
OUT(REF)
A
MIN
at V = 5V and T = +25°C.)
DD
A
PARAMETER
SYMBOL
CONDITIONS
MIN
TYP
8
MAX
80
UNITS
nA
Input Bias Current
Input Offset Current
I
BIAS
I
OS
MAX9001/MAX9002/MAX9004/MAX9005
Guaranteed by CMRR test
±2
±15
nA
Common-Mode
Voltage Range
V
SS
-
V
DD
-
V
CM
V
0.15
1.1
Common-Mode
Rejection Ratio
MAX9001/MAX9002/MAX9004/MAX9005,
CMRR
PSRR
72
72
100
100
dB
dB
0.15V ≤ V ≤ (V - 1.1V), V = 5.5V
CM
DD
DD
Power-Supply Rejection
Ratio
V
DD
= 2.5V to 5.5V
I
= 10µA
= 4mA
5
SOURCE
V
DD
- V
OH
I
400
(V
≥ 20mV
- V
)
SOURCE
CIN+
CIN-
Output Voltage Swing
V
/V
mV
OL OH
I
= 10µA
5
SINK
V
OL
I
= 4mA
400
SINK
–MAX905
Output Short-Circuit
Current
55
mA
µA
Disabled Mode Output
Leakage
I
OUT
V
SHDN
≤ (0.3V x V ), V = 0 to V
COUT
±0.01
±1
DD
DD
(DISABLED)
Propagation Delay
Rise/Fall Time
t
, t
V
= 25mV, R = 10kΩ, C = 15pF (Note 4)
185
10
ns
ns
ns
ns
ns
PD+ PD-
OD
L
L
t , t
V
= 5V, R = 10kΩ, C = 15pF (Note 5)
R
F
DD L L
Shutdown Delay Time
Enable Delay Time
Power-On Time
100
100
100
VOLTAGE REFERENCE (MAX9000/MAX9001/MAX9003/MAX9004)
Output Voltage
V
MAX900_ES_, V = 5V, T = +25°C
1.218
1.230
8
1.242
V
REF
DD
A
Output Voltage
Temperature Coefficient
TCV
ppm/°C
REF
Line Regulation
V
= 2.5V to 5.5V
20
0.15
0.6
6
250
0.8
2.0
µV/V
DD
Sourcing
Sinking
mV/mA
mV/mA
V
= 5V,
= 0 to 1mA
DD
Load Regulation
I
OUT
Shorted to V
Output Short-Circuit
Current
SS
mA
µA
Shorted to V
10
DD
Disabled Mode Output
Leakage
V
SHDN
≤ (0.3V x V ), V
= 0 to V
DD
±0.01
±1
DD
REF
Output Noise
0.1Hz to 10Hz
20
µVp-p
µs
Shutdown Delay Time
Enable Delay Time
Power-On Time
1
16
R
R
= 100kΩ to V , V
within 1%
within 1%
µs
L
L
SS REF
= 100kΩ to V , V
16
µs
SS REF
Capacitive Load Stability
0 to 100
nF
Note 1: Comparator Input Offset is defined as the center of the input-referred hysteresis zone.
Note 2: Measured at V = 0 for the MAX9001/MAX9002/MAX9004/MAX9005; or V
= V for the MAX9000/MAX9003.
REF
CM(COMP)
CM(COMP)
Note 3: Input-referred hysteresis is defined as the difference of the trip points required to change comparator output states.
Note 4: V is the overdrive that is beyond the offset and hysteresis-determined trip points.
OD
Note 5: Rise and fall times are measured between 10% and 90% at COUT.
4
_______________________________________________________________________________________
Lo w -P o w e r, Hig h -S p e e d , S in g le -S u p p ly
Op Am p + Co m p a ra t o r + Re fe re n c e ICs
–MAX905
__________________________________________Typ ic a l Op e ra t in g Ch a ra c t e ris t ic s
(V = +5V, V = 0, V (op amp) = 0, SHDN = V , COUT = low, R = ∞, T = +25°C, unless otherwise noted.)
DD
SS
CM
DD
L
A
SUPPLY CURRENT
vs. SUPPLY VOLTAGE
SHUTDOWN LOGIC THRESHOLD
vs. SUPPLY VOLTAGE
SHUTDOWN SUPPLY CURRENT
vs. SUPPLY VOLTAGE
3.5
3.0
2.5
2.0
1.5
1.0
0.5
0
500
2.5
2.0
1.5
1.0
0.5
0
450
400
350
300
250
200
MAX9000/MAX9001/MAX9003/MAX9004
MAX9002/MAX9005
2.5
3.0
3.5
4.0
4.5
5.0
5.5
2.5
3.0
3.5
4.0
4.5
5.0
5.5
2.5
3.0
3.5
4.0
4.5
5.0
5.5
SUPPLY VOLTAGE (V)
SUPPLY VOLTAGE (V)
SUPPLY VOLTAGE (V)
MAX9000/MAX9001/MAX9003/MAX9004
SUPPLY CURRENT vs. TEMPERATURE
SHUTDOWN SUPPLY CURRENT
vs. TEMPERATURE
SHUTDOWN LOGIC THRESHOLD
vs. TEMPERATURE
5.0
4.5
4.0
3.5
3.0
2.5
2.0
1.5
1.0
0.5
0
2.00
1.98
1.96
1.94
1.92
1.90
500
450
400
350
300
V
= 5.5V
DD
V
= 5.5V
= 2.5V
DD
V
DD
V
DD
= 2.5V
-40 -20
0
20
40
60
80 100
-40 -20
0
20
40
60
80 100
-40 -20
0
20
40
60
80 100
TEMPERATURE (°C)
TEMPERATURE (°C)
TEMPERATURE (°C)
MAX9002/MAX9005
SUPPLY CURRENT vs. TEMPERATURE
OP-AMP OUTPUT VOLTAGE SWING LOW (V )
OL
OP-AMP OUTPUT VOLTAGE SWING HIGH (V
)
OH
vs. SINK CURRENT
vs. SOURCE CURRENT
450
400
350
300
250
200
150
100
50
500
450
400
350
300
600
T = +85°C
A
500
400
300
200
100
0
T = +85°C
A
T = +25°C
A
T = +25°C
A
V
= 5.5V
= 2.5V
DD
T = -40°C
A
T = -40°C
A
V
DD
0
0
1
2
3
4
5
6
-40 -20
0
20
40
60
80 100
0
2
4
6
8
10 12 14 16 18 20
SOURCE CURRENT (mA)
TEMPERATURE (°C)
SINK CURRENT (mA)
_______________________________________________________________________________________
5
Lo w -P o w e r, Hig h -S p e e d , S in g le -S u p p ly
Op Am p + Co m p a ra t o r + Re fe re n c e ICs
____________________________________Typ ic a l Op e ra t in g Ch a ra c t e ris t ic s (c o n t in u e d )
(V = +5V, V = 0, V (op amp) = 0, SHDN = V , COUT = low, R = ∞, T = +25°C, unless otherwise noted.)
DD
SS
CM
DD
L
A
CHANGE IN OP-AMP OFFSET VOLTAGE (V
)
OS
OP-AMP COMMON-MODE REJECTION RATIO
vs. TEMPERATURE
CHANGE IN OP-AMP OFFSET VOLTAGE (V )
OS
vs. SUPPLY VOLTAGE
vs. TEMPERATURE
92
30
100
50
91
90
89
88
87
86
85
84
20
10
0
0
-50
-100
-150
-10
-20
-30
2.5
3.0
3.5
4.0
4.5
5.0
5.5
-40 -20
0
20
40
60
80 100
-40 -20
0
20
40
60
80 100
–MAX905
SUPPLY VOLTAGE (V)
TEMPERATURE (°C)
TEMPERATURE (°C)
OP-AMP LARGE-SIGNAL GAIN
vs. OUTPUT VOLTAGE
OP-AMP LARGE-SIGNAL GAIN
vs. OUTPUT VOLTAGE
OP-AMP LARGE-SIGNAL GAIN
vs. TEMPERATURE
140
130
120
110
100
90
140
130
120
110
100
90
140
130
120
110
100
90
V
= 5.5V
DD
R = 100kΩ
L
R TO GND
L
R = 100kΩ
L
R = 100kΩ
L
R = 10kΩ
L
R = 10kΩ
L
R = 2kΩ
R = 10kΩ
L
L
R = 2kΩ
L
R = 1kΩ
L
V
= 5.5V
DD
DD
V
DD
= 2.5V
R TO V /2
L
R TO GND
L
V
OUT
SWING = 0.2V TO 5.3V
80
80
80
0
100
200
300
400
500
600
0
100
200
300
400
500
600
-40 -20
0
20
40
60
80 100
OUTPUT VOLTAGE FROM EITHER SUPPLY (mV)
OUTPUT VOLTAGE FROM EITHER SUPPLY (mV)
TEMPERATURE (°C)
OP-AMP LARGE-SIGNAL GAIN
vs. OUTPUT VOLTAGE
OP-AMP LARGE-SIGNAL GAIN
vs. OUTPUT VOLTAGE
OP-AMP LARGE-SIGNAL GAIN
vs. TEMPERATURE
140
130
120
110
100
90
140
130
120
110
100
140
130
120
110
100
90
V
= 2.7V
DD
DD
R = 100kΩ
L
R TO V
L
R = 100kΩ
L
R = 10kΩ
L
R = 10kΩ
L
R = 100kΩ
L
R = 2kΩ
L
R = 10kΩ
L
R = 1kΩ
L
R = 2kΩ
L
V
= 2.5V
DD
SWING = 0.2V TO 2.3V
DD
V
DD
= 5.5V
R TO V /2
L
R TO V
L
DD
V
OUT
80
80
0
100
200
300
400
500
600
0
100
200
300
400
500
600
-40 -20
0
20
40
60
80 100
OUTPUT VOLTAGE FROM EITHER SUPPLY (mV)
OUTPUT VOLTAGE FROM EITHER SUPPLY (mV)
TEMPERATURE (°C)
6
_______________________________________________________________________________________
Lo w -P o w e r, Hig h -S p e e d , S in g le -S u p p ly
Op Am p + Co m p a ra t o r + Re fe re n c e ICs
–MAX905
_____________________________Typ ic a l Op e ra t in g Ch a ra c t e ris t ic s (c o n t in u e d )
(V = +5V, V = 0, V (op amp) = 0, SHDN = V , COUT = low, R = ∞, T = +25°C, unless otherwise noted.)
DD
SS
CM
DD
L
A
MAX9000/MAX9001/MAX9002
OP-AMP POWER-SUPPLY REJECTION
vs. FREQUENCY
MAX9000/MAX9001/MAX9002
OP-AMP GAIN AND PHASE
vs. FREQUENCY (NO LOAD)
MAX9000/MAX9001/MAX9002
OP-AMP GAIN AND PHASE
vs. FREQUENCY (WITH C
)
LOAD
MAX9000 TOC 19
MAX9000 TOC20
60
40
20
0
180
144
60
40
20
0
0
180
144
A = +1
V
NO LOAD
A = +1000
NO LOAD
A = +1000
C = 270pF
V
V
L
108
72
108
72
-20
-40
-60
-80
GAIN
GAIN
36
36
0
0
-36
-72
-108
-144
-180
-36
-72
-108
-144
-180
PHASE
PHASE
-20
-20
-40
100
-40
100
-100
1k
10k
100k
1M
10M
1k
10k
100k
1M
10M
100
1k
10k
100k
1M
10M
FREQUENCY (Hz)
FREQUENCY (Hz)
FREQUENCY (Hz)
MAX9003/MAX9004/MAX9005
OP-AMP GAIN AND PHASE
MAX9003/MAX9004/MAX9005
OP-AMP GAIN AND PHASE
vs. FREQUENCY (NO LOAD)
MAX9003/MAX9004/MAX9005
OP-AMP POWER-SUPPLY REJECTION
vs. FREQUENCY
vs. FREQUENCY (WITH C
)
LOAD
MAX9000 TOC23
MAX9000 TOC22
180
60
60
180
144
108
0
A = +1000
V
A = +1000
V
NO LOAD
A = +10
V
NO LOAD
144
108
72
C = 270pF
L
40
20
0
40
20
0
GAIN
-20
-40
-60
-80
GAIN
72
36
36
0
0
-36
-72
-108
-144
-180
-36
-72
-108
-144
-180
PHASE
PHASE
-20
-20
-40
-40
100
-100
100
1k
10k
100k
1M
10M
1k
10k
100k
1M
10M
100
1k
10k
100k
1M
10M
FREQUENCY (Hz)
FREQUENCY (Hz)
FREQUENCY (Hz)
MAX9000/MAX9001/MAX9002
OP-AMP PERCENT OVERSHOOT
vs. LOAD CAPACITANCE
MAX9003/MAX9004/MAX9005
OP-AMP PERCENT OVERSHOOT
vs. LOAD CAPACITANCE
OP-AMP VOLTAGE NOISE DENSITY
vs. FREQUENCY
50
40
30
20
10
0
50
40
30
20
10
0
1000
A = +1
R TO V /2
L
A = +10
V
R TO V /2
L DD
V
DD
R = 10kΩ
L
R = 100kΩ
L
R = 100kΩ
L
300
100
R = 1kΩ
L
R = 10kΩ
L
R = 1kΩ
L
30
10
0
100 200 300 400 500 600 700 800 900 1000
(pF)
0
100 200 300 400 500 600 700 800 900 1000
(pF)
1
10
100
1k
10k
100k
C
C
LOAD
FREQUENCY (Hz)
LOAD
_______________________________________________________________________________________
7
Lo w -P o w e r, Hig h -S p e e d , S in g le -S u p p ly
Op Am p + Co m p a ra t o r + Re fe re n c e ICs
_____________________________Typ ic a l Op e ra t in g Ch a ra c t e ris t ic s (c o n t in u e d )
(V = +5V, V = 0, V (op amp) = 0, SHDN = V , COUT = low, R = ∞, T = +25°C, unless otherwise noted.)
DD
SS
CM
DD
L
A
MAX9000/MAX9001/MAX9002
OP-AMP TOTAL HARMONIC DISTORTION
MAX9000/MAX9001/MAX9002
OP-AMP TOTAL HARMONIC DISTORTION
PLUS NOISE vs. FREQUENCY
MAX9000/MAX9001/MAX9002
OP-AMP OUTPUT IMPEDANCE vs. FREQUENCY
PLUS NOISE vs. V
AOUT
1
0.25
0.20
0.15
0.10
0.05
0
1k
A = +1
V
A = +1
V
A = +1
V
NO LOAD
V
IN
= 2Vp-p
V = 10kHz SINE WAVE
IN
500 kHz LOWPASS FILTER
R TO V /2
500kHz LOWPASS FILTER
R TO V /2
100
10
L
DD
L
DD
R = 10kΩ
L
0.1
R = 1kΩ
L
R = 10kΩ
L
1
R = 1kΩ
L
0.01
R = 100kΩ
L
R = 100kΩ
L
0.1
0.01
0.001
10
100
1k
10k
100k
4.0 4.1 4.2 4.3 4.4 4.5 4.6 4.7 4.8 4.9 5.0
SWING (Vp-p)
100
1k
10k
100k
1M
10M
–MAX905
FREQUENCY (Hz)
V
AOUT
FREQUENCY (Hz)
MAX9003/MAX9004/MAX9005
OP-AMP TOTAL HARMONIC DISTORTION
PLUS NOISE vs. FREQUENCY
MAX9003/MAX9004/MAX9005
OP-AMP TOTAL HARMONIC DISTORTION
MAX9003/MAX9004/MAX9005
OP-AMP OUTPUT IMPEDANCE vs. FREQUENCY
PLUS NOISE vs. V
AOUT
10k
1
0.25
0.20
0.15
0.10
0.05
0
A = +10
V
A = +10
V
A = +10
V
NO LOAD
V = 10kHz SINE WAVE
IN
V = 200mVp-p
IN
500kHz LOWPASS FILTER
R = 1kΩ
L
500kHz LOWPASS FILTER
1k
100
10
R TO V /2
L
DD
R TO V /2
L
DD
V
IN
V
OUT
R = 10kΩ
L
R
L
0.1
36k
4k
V
IN
V
R = 100kΩ
L
R = 1kΩ
OUT
L
R
1
L
R = 10kΩ
L
36k
4k
100
R = 100kΩ
L
0.1
0.01
100
1k
10k
100k
1M
10M
10
1k
FREQUENCY (Hz)
10k
100k
4.0 4.1 4.2 4.3 4.4 4.5 4.6 4.7 4.8 4.9 5.0
SWING (Vp-p)
FREQUENCY (Hz)
V
AOUT
COMPARATOR COMMON-MODE
REJECTION RATIO (CMRR)
vs. TEMPERATURE
CHANGE IN COMPARATOR OFFSET
VOLTAGE (V ) vs. SUPPLY VOLTAGE
CHANGE IN COMPARATOR OFFSET
VOLTAGE (V ) vs. TEMPERATURE
OS
OS
95
200
200
150
100
50
150
100
50
93
91
89
87
85
0
0
-50
-100
-150
-200
-50
-100
-150
-200
2.5
3.0
3.5
4.0
4.5
5.0
5.5
-40 -20
0
20
40
60
80 100
-40 -20
0
20
40
60
80 100
SUPPLY VOLTAGE (V)
TEMPERATURE (°C)
TEMPERATURE (°C)
8
_______________________________________________________________________________________
Lo w -P o w e r, Hig h -S p e e d , S in g le -S u p p ly
Op Am p + Co m p a ra t o r + Re fe re n c e ICs
–MAX905
_____________________________Typ ic a l Op e ra t in g Ch a ra c t e ris t ic s (c o n t in u e d )
(V = +5V, V = 0, V (op amp) = 0, SHDN = V , COUT = low, R = ∞, T = +25°C, unless otherwise noted.)
DD
SS
CM
DD
L
A
COMPARATOR HYSTERESIS
vs. TEMPERATURE
COMPARATOR OUTPUT VOLTAGE
SWING LOW (V ) vs. SINK CURRENT
OL
COMPARATOR OUTPUT VOLTAGE
SWING HIGH (V ) vs. SOURCE CURRENT
OH
3.5
600
500
400
300
200
100
0
600
500
400
300
200
100
0
3.2
2.9
2.6
2.3
2.0
T = +85°C
A
T = +85°C
A
T = +25°C
A
T = +25°C
A
T = -40°C
A
T = -40°C
A
0
1
2
3
4
5
6
7
8
9
10
-40 -20
0
20
40
60
80 100
0
1
2
3
4
5
6
7
8
9
10
SINK CURRENT (mA)
TEMPERATURE (°C)
SOURCE CURRENT (mA)
POSITIVE COMPARATOR PROPAGATION
DELAY (t ) vs. LOAD CAPACITANCE
PD+
NEGATIVE COMPARATOR PROPAGATION
DELAY (t ) vs. LOAD CAPACITANCE
PD-
COMPARATOR PROPAGATION DELAY
vs. INPUT OVERDRIVE
800
700
600
500
400
300
200
100
800
700
600
500
400
300
200
100
300
275
250
225
200
175
150
OVERDRIVE = 5mV
OVERDRIVE = 25mV
t
PD-
OVERDRIVE = 5mV
OVERDRIVE = 25mV
OVERDRIVE = 100mV
OVERDRIVE = 100mV
t
PD+
0
2000
4000
C
6000
(pF)
8000 10,000
0
2000
4000
C
6000
(pF)
8000 10,000
0
10 20 30 40 50 60 70 80 90 100
INPUT OVERDRIVE (mV)
LOAD
LOAD
V
REF
POWER-SUPPLY REJECTION
vs. FREQUENCY
COMPARATOR PROPAGATION DELAY
vs. TEMPERATURE
V
REF
OUTPUT VOLTAGE CHANGE
vs. TEMPERATURE
0
-20
200
175
150
125
100
1.0
0.5
OVERDRIVE VOLTAGE = 50mV
t
PD-
t
PD+
0
-40
-0.5
-1.0
-1.5
-2.0
-60
-80
-100
-40 -20
0
20
40
60
80 100
1
10
100
1k
10k 100k 1M
-40 -20
0
20
40
60
80 100
TEMPERATURE (°C)
FREQUENCY (Hz)
TEMPERATURE (°C)
_______________________________________________________________________________________
9
Lo w -P o w e r, Hig h -S p e e d , S in g le -S u p p ly
Op Am p + Co m p a ra t o r + Re fe re n c e ICs
_____________________________Typ ic a l Op e ra t in g Ch a ra c t e ris t ic s (c o n t in u e d )
(V = +5V, V = 0, V (op amp) = 0, SHDN = V , COUT = low, R = ∞, T = +25°C, unless otherwise noted.)
DD
SS
CM
DD
L
A
V
REF
OUTPUT VOLTAGE CHANGE
vs. LOAD CURRENT
V
REF
OUTPUT VOLTAGE CHANGE
vs. SUPPLY VOLTAGE
V
REF
LOAD-TRANSIENT RESPONSE
4
3
2
1
0
100
+1mA
I
OUT
-1mA
50
0
2mA/div
SINKING
V
REF
SOURCING
200mV/div
-50
-100
-1
-2
-2.0 -1.5 -1.0 -0.5
0
0.5 1.0 1.5 2.0
2.5
3.0
3.5
4.0
4.5
5.0
5.5
50µs/div
–MAX905
LOAD CURRENT (mA)
SUPPLY VOLTAGE (V)
V
REF
0.1Hz to 10Hz VOLTAGE NOISE
COMPARATOR PROPAGATION DELAY
V
REF
LINE-TRANSIENT RESPONSE
MAX9000-TOC51
V - = GND
IN
NO LOAD
5.0V
V
DD
+50mW
-50mW
V
IN+
500mV/div
4.5V
50mV/div
5µV/div
V
OUT
V
REF
2V/div
100mV/div
t
t
PD-
PD+
1sec/div
100ns/div
5µs/div
MAX9000/MAX9001/MAX9002
OP-AMP SMALL-SIGNAL TRANSIENT
MAX9003/MAX9004/MAX9005
MAX9000/MAX9001/MAX9002
RESPONSE WITH C
LOAD
OP-AMP SMALL-SIGNAL TRANSIENT RESPONSE
OP-AMP SMALL-SIGNAL TRANSIENT RESPONSE
A = +1
V
NO LOAD
A = +1
V
C = 270pF
L
A = +10
V
NO LOAD
V
IN
10mV/div
V
IN
V
IN
50mV/div
50mV/div
V
OUT
50mV/div
V
OUT
50mV/div
V
OUT
50mV/div
1µs/div
500ns/div
500ns/div
10 ______________________________________________________________________________________
Lo w -P o w e r, Hig h -S p e e d , S in g le -S u p p ly
Op Am p + Co m p a ra t o r + Re fe re n c e ICs
–MAX905
_____________________________Typ ic a l Op e ra t in g Ch a ra c t e ris t ic s (c o n t in u e d )
(V = +5V, V = 0, V (op amp) = 0, SHDN = V , COUT = low, R = ∞, T = +25°C, unless otherwise noted.)
DD
SS
CM
DD
L
A
MAX9003/MAX9004/MAX9005
OP-AMP SMALL-SIGNAL TRANSIENT
MAX9000/MAX9001/MAX9002
OP-AMP LARGE-SIGNAL TRANSIENT RESPONSE
MAX9003/MAX9004/MAX9005
OP-AMP LARGE-SIGNAL TRANSIENT RESPONSE
RESPONSE WITH C
LOAD
A = +1
C = 270pF
L
V
A = +1
V
NO LOAD
A = +10
V
NO LOAD
V
5V/div
V
IN
IN
V
IN
0.5V/div
10mV/div
4V
5V
V
1V/div
OUT
V
OUT
V
1V/div
OUT
50mV/div
0V
0V
2µs/div
500ns/div
1µs/div
P in De s c rip t io n
PIN
MAX9001/MAX9004
NAME
FUNCTION
MAX9000/
MAX9003
MAX9002/
MAX9005
10 µMAX
14 SO
—
1
—
1
1
2
2
Shutdown Logic Input
Op-Amp Output
SHDN
AOUT
AIN-
3
2
2
3
4
Inverting Op-Amp Input
3
3
4
5
AIN+
Noninverting Op-Amp Input
Negative Supply or Ground
Internal Reference Output
Inverting Comparator Input
Noninverting Comparator Input
Comparator Output
4
4
5
6
V
SS
5
—
5
6
9
REF
CIN-
—
6
7
10
11
6
8
CIN+
COUT
7
7
9
12
8
8
10
—
13
V
Positive Supply
DD
—
—
1, 7, 8, 14
N.C.
No Connection. Not internally connected.
______________________________________________________________________________________ 11
Lo w -P o w e r, Hig h -S p e e d , S in g le -S u p p ly
Op Am p + Co m p a ra t o r + Re fe re n c e ICs
_______________De t a ile d De s c rip t io n
The MAX9001–MAX9005 are combinations of a high-
speed operational amplifier, a 185ns comparator, and a
1%-accurate, 8ppm/°C, 1.230V reference. The devices
are offered in space-saving 8-pin and 10-pin µMAX pack-
ages. The comparator’s inverting input is internally con-
nected to the reference output in the MAX9000/MAX9003.
The MAX9002/MAX9005 do not have an internal refer-
ence, but the inverting input of the comparator is avail-
able externally. The MAX9001/MAX9004 include both the
inverting input and the reference output. The MAX9000/
MAX9001/MAX9003/MAX9004 typically consume only
410µA of q uie s c e nt c urre nt, while the MAX9002/
MAX9004 typically consume 340µA. These low-power,
Rail-to-Rail devices provide excellent AC and DC perfor-
mance and are ideally suited to operate from a single
supply. The MAX9001/MAX9004 feature a shutdown
mode that sets the outputs in a high-impedance state and
reduces the supply current to 2µA, making these devices
ideal for portable and battery-powered systems.
MAX9000
MAX9003
1
2
3
4
AOUT
AIN-
V
8
7
6
5
DD
OP AMP
COUT
CIN+
REF
COMP
AIN+
REF
V
SS
–MAX905
MAX9002
MAX9005
1
AOUT
AIN-
V
DD
8
OP AMP
Op Am p
The op amps in the MAX9000/MAX9001/MAX9002 are
unity-ga in sta ble with a ga in-b a ndwid th p roduc t of
1.25MHz and a slew rate of 0.85V/µs. The amplifiers in
the MAX9003/MAX9004/MAX9005 are stable at closed-
loop gains greater than or equal to 10V/V, with a gain-
bandwidth product of 8MHz and a slew rate of 6.0V/µs.
2
3
4
COUT
CIN+
CIN-
7
6
5
COMP
AIN+
V
SS
The common-mode input voltage range extends from
150mV below the negative rail to within 1.2V of the pos-
itive rail. The amplifier output does not undergo phase
re ve rs a l whe n the c ommon-mod e inp ut ra ng e is
exceeded, and the input impedance is relatively con-
stant for input voltages within both supply rails. The
MOS d iffe re ntia l inp uts of the a mp lifie rs fe a ture
extremely high input impedance and ultra-low input
bias currents. The CMOS output stage achieves true
rail-to-rail operation; the outputs swing to within a few
millivolts of the supply rails, thus extending the dynamic
range. A proprietary design achieves high open-loop
gain, enabling these devices to operate at low quies-
cent currents yet maintain excellent DC and AC char-
a c te ris tic s und e r va rious loa d c ond itions . The s e
devices have been designed to maintain low offset volt-
age over the entire operating-temperature, common-
mode, and supply-voltage ranges.
2
SHDN
NORMAL/SHUTDOWN CONTROL
V
13
DD
4M
3
AOUT
V
DD
12
OP AMP
COMP
4
5
6
AIN-
CIN+ 11
CIN- 10
AIN+
V
SS
REF 9
MAX9001
MAX9004
REF
Figure 1. MAX9000–MAX90005 Functional Diagrams
12 ______________________________________________________________________________________
Lo w -P o w e r, Hig h -S p e e d , S in g le -S u p p ly
Op Am p + Co m p a ra t o r + Re fe re n c e ICs
–MAX905
amplifier’s output, add a 1µF to 10µF power-supply
bypass capacitor.
Co m p a ra t o r
The common-mode input range extends from 150mV
below the negative rail to within 1.1V of the positive rail.
The bipolar differential inputs of the comparator feature
high input impedance and low input bias currents. The
comparators are designed to maintain low offset volt-
age over the entire operating-temperature, common-
mode, and supply-voltage ranges. In the MAX9000/
MAX9003, the comparator’s inverting input is internally
connected to the reference output.
The device has a high degree of isolation between the
various blocks. To maintain isolation, careful layout is
required. Take special precautions to avoid crossing
signal traces, especially from the outputs to the inputs.
For sensitive applications, shielding might be required.
In addition, stray capacitance may affect the stability
and frequency response of the amplifier. Decrease
stray capacitance by minimizing lead lengths in the
board layout, as well as placing external components
as close to the device as possible.
The CMOS output stage achieves true rail-to-rail opera-
tion; the outputs swing to within a few millivolts of the
supply rails. The comparator’s propagation delay is
185ns and is a function of the overdrive (see Typical
Operating Characteristics). TTL/CMOS compatibility is
maintained even with a ±4mA output load. A propri-
etary design of the output stage substantially reduces
the cross-conduction current during output transitions,
thereby minimizing power-supply glitches typical of
most comparators. In addition, the comparator’s ±2mV
of built-in hysteresis provides noise immunity and pre-
vents unstable outputs even with slow-moving input
signals.
Op -Am p Fre q u e n c y S t a b ilit y
Driving large capacitive loads can cause instability in
most low-power, rail-to-rail output amplifiers. These
amplifiers are stable with capacitive loads up to 250pF in
their minimum gain configuration. Stability with higher
capacitive loads can be improved by adding an isolation
resistor in series with the op-amp output, as shown in
Figure 2. This resistor improves the circuit’s phase mar-
gin by isolating the load capacitor from the amplifier’s
output. Figures 3 and 4 show the response of the ampli-
fier with and without an isolation resistor, respectively.
Vo lt a g e Re fe re n c e
The 1%-accurate, precision 1.230V internal bandgap
re fe re nc e in the MAX9000/MAX9001/MAX9003/
MAX9004 achieves an 8ppm/°C temperature coefficient
(tempco). The reference can sink or source 1mA of load
current with excellent load regulation. The output typical-
ly changes only 60µV for a 3V change in input voltage
(line regulation). The reference is stable for capacitive
loads up to 100nF.
The total capacitance at the op amp’s inputs (input
capacitance + stray capacitance) along with large-value
feedback resistors can cause additional poles within the
amplifier’s bandwidth, thus degrading the phase margin.
To compensate for this effect, place a 2pF to 10pF
capacitor across the feedback resistor, as shown in
Figure 5.
Ap p lic a t io n s In fo rm a t io n
The MAX9000–MAX9005 offer excellent performance
a nd low p owe r c ons ump tion, a nd a re a va ila b le in
space-saving µMAX packages. The following section
provides some practical application guidelines.
R
S
C
LOAD
MAX9000
MAX9001
MAX9002
Byp a s s in g a n d La yo u t
The MAX9000–MAX9005 operate from a +2.5V to +5.5V
single supply or from ±1.25V to ±2.75V dual supplies.
(In the MAX9000/MAX9001/MAX9003/MAX9004, the
reference voltage is referred to as V .). For single-
R
S
SS
C
LOAD
s up p ly op e ra tion, b yp a s s the p owe r s up p ly with a
0.1µF capacitor. For dual supplies, bypass each supply
to ground. Bypass with capacitors as close as possible
to the device to minimize lead inductance and noise.
Use a low-inductance ground plane if possible. A print-
ed circuit board with a ground plane is recommended.
Avoid using wire -wra p boa rds, b re a d boa rd s, or IC
sockets. For heavy loads at the comparator’s and/or
R
R
MAX9003
MAX9004
MAX9005
Figure 2. Isolation Resistors to Drive Capacitive Loads
______________________________________________________________________________________ 13
Lo w -P o w e r, Hig h -S p e e d , S in g le -S u p p ly
Op Am p + Co m p a ra t o r + Re fe re n c e ICs
V
IN
V
IN
50mV/
div
50mV/
div
V
OUT
V
OUT
50mV/
div
50mV/
div
V
= +1
DD
C = 510pF
L
2µs/div
2µs/div
Figure 4. MAX9000/MAX9001/MAX9002 Op-Amp Small-Signal
Figure 3. MAX9000/MAX9001/MAX9002 Op-Amp Small-Signal
Transient Response with Capacitive Load (C = 510pF) and
Transient Response with Capacitive Load (C = 510pF) and
L
L
No Isolation Resistor
Isolation Resistor (R
= 91Ω)
ISO
–MAX905
AIN+
R2
AOUT
V
IN
R1
COUT
R2
R1
REF
2pF TO 10pF
Figure 5. Compensation for Input Capacitance
Figure 6. External Hysteresis
comparator. The outputs do not undergo phase rever-
sal when the input common-mode range is exceeded,
and the input impedance is relatively constant for input
voltages within both supply rails.
Re fe re n c e Byp a s s in g
While the internal reference is stable with capacitive
loads up to 100nF, it does not require an output capaci-
tor for stability. However, in applications where the load
or the supply could experience large step changes, an
output capacitor reduces the amount of overshoot and
improves the circuit’s transient response.
Co m p a ra t o r Hys t e re s is
Built-in ±2mV hysteresis improves the comparator’s
noise immunity. It prevents unstable outputs with slow-
moving or noisy input signals. If additional hysteresis is
required, add positive feedback as shown in Figure 6.
This configuration increases the hysteresis band to
desired levels, but also increases power consumption
and slows down the output response.
Co m p a ra t o r In p u t S t a g e
The comparator’s input bias current is typically 8nA. To
reduce the offset error caused by the bias current flow-
ing through the external source impedance, match the
effective impedance seen by each input. High source
impedance together with the comparator’s input capaci-
tance can increase the propagation delay through the
14 ______________________________________________________________________________________
Lo w -P o w e r, Hig h -S p e e d , S in g le -S u p p ly
Op Am p + Co m p a ra t o r + Re fe re n c e ICs
–MAX905
To add hysteresis, use the following procedure:
tive supply without an increase in the SHDN input cur-
rent, allowing them to be driven from independent logic
c irc uits p owe re d from a d iffe re nt s up p ly volta g e .
Howe ve r, the log ic thre s hold volta g e re q uire me nts
mus t b e me t for p rop e r op e ra tion. If SHDN is le ft
unconnected, the device defaults to the enabled mode
Step 1: The device’s input bias current can be as high
a s 80nA. To minimize e rror d ue to the inp ut b ia s ,
choose a value for R2 of 100kΩ (V
/ R2), which
REF
allows a current of 12.33µA at the upper trip point.
Step 2: Choose the width of the hysteresis band. In this
example, choose 20mV for the added external hystere-
through an internal 4MΩ pull-up to V . If SHDN is to
DD
be left unconnected, take proper care to ensure that no
signals are coupled to this pin, as this may cause false
triggering.
s is (V
= 20mV). Tota l hys te re s is = V
+
EHYST
EHYST
V
IHYST
= 24mV.
R1 = R2 (V
- 2V
) / (V + 2V
)
EHYST
IHYST
DD
IHYST
In shutdown mode, all outputs are set to a high-imped-
ance state and the supply current reduces to 2µA.
Enable times for the op amp, comparator, and refer-
ence are 2µs, 100ns, and 16µs, respectively. Shutdown
delay times for the op amp, comparator, and reference
are 200ns, 100ns, and 1µs, respectively (Figure 7).
where
is the device’s internal hysteresis.
IHYST
Step 3: Determine R1. If V = 5V, then R1 = 319Ω.
DD
Step 4: Check the hysteresis trip points. The following
equation represents the upper trip point (V ):
IN(H)
V
= [(R1 + R2) / R2] (V
+ V
) = 1.238V
IN(H)
REF
IHYST
________________Ap p lic a t io n Circ u it s
The lower trip point is 24mV lower than upper trip point.
= 1.238V - 0.024V = 1.214V.
V
IN(L
)
Ra d io Re c e ive r fo r Ala rm s
a n d De t e c t o rs
Co m p a ra t o r P ro p a g a t io n De la y
Figure 8’s circuit is useful as a front end for RF alarms.
An unshielded inductor is used with capacitors C1A,
C1B, and C1C in a resonant circuit to provide frequen-
cy selectivity. The op amp from a MAX9003 amplifies
the signal received. The comparator improves noise
immunity, provides a signal-strength threshold, and
translates the received signal into a pulse train. The
tuned LC circuit in Figure 8 is set for 300kHz. The lay-
out and routing of components for the amplifier should
be tight to minimize 60Hz interference and crosstalk
from the comparator. Metal shielding is recommended
to prevent RFI from the comparator or digital circuitry
from exciting the receiving antenna. The transmitting
The comparator’s propagation delay is a function of the
input overdrive voltage. Overdrive voltage is measured
from beyond the edge of the offset and hysteresis-
d e te rmine d trip p oints (s e e Typ ic a l Op e ra ting
Characteristics for a graph of Propagation Delay vs.
Input Overdrive). High source impedance coupled with
the comparator’s input capacitance increases the prop-
agation delay. Large capacitive loads also increase the
propagation delay.
SHDN
S h u t d o w n (
)
Shutdown is active-low enabled. The SHDN input for
the MAX9001/MAX9004 can be taken above the posi-
V
CC
= 5V
ANTENNA
SHDN
5V/div
MAX9003
0.1µF
0.1µF
AOUT
2V/div
20k
10M
C1A
390pF
AMP
9.1k
C1B
0.01nF
COUT
5V/div
L1
33µH
C1C
50-100pF
COMP
10k
VREF
5.1M
1V/div
REF
1.230V
LAYOUT-SENSITIVE AREA,
METAL RFI SHIELDING ADVISED
1
L1 x C1 =
5µs/div
2
(2π f )
C
A = +1V/V, C
= 2.5V, C
= 2.5V
V
AIN+
CIN+
Figure 7. Enable/Disable Response of Op Amp, Comparator,
Figure 8. Radio Receiver Application
and Reference to SHDN
______________________________________________________________________________________ 15
Lo w -P o w e r, Hig h -S p e e d , S in g le -S u p p ly
Op Am p + Co m p a ra t o r + Re fe re n c e ICs
antenna can be long parallel wires spaced about 7.2cm
apart, with equal but opposite currents. Radio waves
from this antenna are detectable when the receiver is
brought within close proximity, but cancel out at greater
V
CC
= 5V
100kHz,
5Vp-p
distances.
C2
15pF, 5%
NEC
PH302B
In fra re d Re c e ive r Fro n t En d fo r
Re m o t e Co n t ro ls a n d Da t a Lin k s
R2
100k,
1%
NEC
SE307-C
0.1µF
4.99k
The circuit in Figure 9 uses the MAX9003 as a PIN pho-
todiode preamplifier and discriminator for an infrared
receiver. The op amp is configured as a Delyiannis-
noise and eliminates low-frequency interference from
sunlight, fluorescent lights, etc. This circuit is applica-
ble for TV remote controls and low-frequency data links
up to 200kb p s . Ca rrie r fre q ue nc ie s a re limite d to
around 100kHz, as in the example circuit. Component
layout and routing for the amplifier should be tight to
reduce stray capacitance, 60Hz interference, and RFI
from the comparator. Crosstalk from comparator edges
distorts the amplifier signal. To minimize this effect, add
a lowpass RC filter to the connection from the reference
to the op amp’s noninverting input.
51Ω
R1
A
49.9k
1%
AMP
C1
150pF,
5%
R1
B
4.99k
1%
COMP
100k
0.1µF
1.230V
MAX9003
REF
LAYOUT-SENSITIVE AREA
1
9
R1 x C1 = R2 x C2 =
2π f
C
S ig n a l Co n d it io n in g
For incoming signals that require filtering, the internal
amplifier provides an opportunity to create an active fil-
ter. This may be required for relatively high-speed sig-
na ls tha t re q uire a d e q ua te filte ring of hig h-s p e e d
carrier frequencies, harmonics, and external noise. In
addition, the amplifier can be used to amplify the signal
prior to digitizing it through the comparator to improve
the comparator’s overall output response and improve
its noise immunity.
Figure 9. Infrared Receiver Application
16 ______________________________________________________________________________________
Lo w -P o w e r, Hig h -S p e e d , S in g le -S u p p ly
Op Am p + Co m p a ra t o r + Re fe re n c e ICs
–MAX905
P in Co n fig u ra t io n s
TOP VIEW
N.C.
SHDN
AOUT
AIN-
1
2
3
4
5
6
7
14 N.C.
13
SHDN
AOUT
AIN-
1
2
3
4
5
10
9
V
DD
AOUT
AIN-
1
2
3
4
8
7
6
5
V
DD
V
DD
COUT
CIN+
CIN-
COUT
MAX9001
MAX9004
MAX9000
MAX9002
MAX9003
MAX9005
12 COUT
11 CIN+
10 CIN-
8
AIN+
CIN+
AIN+
7
MAX9001
MAX9004
V
SS
REF (CIN-)
AIN+
V
SS
6
REF
V
SS
9
8
REF
N.C.
µMAX
SO/µMAX
N.C.
SO
( ) ARE FOR THE MAX9002/MAX9005.
Typ ic a l Op e ra t in g Circ u it
V
DD
0.1µF
INPUT
AIN+
AIN-
MAX9000
MAX9003
OP AMP
R2
AOUT
1M
COUT
CIN+
REF
COMP
R1
REF
1.230V
V
SS
______________________________________________________________________________________ 17
Lo w -P o w e r, Hig h -S p e e d , S in g le -S u p p ly
Op Am p + Co m p a ra t o r + Re fe re n c e ICs
Ord e rin g In fo rm a t io n (c o n t in u e d )
Ch ip In fo rm a t io n
PART
TEMP. RANGE
-40°C to +85°C
-40°C to +85°C
-40°C to +85°C
-40°C to +85°C
-40°C to +85°C
-40°C to +85°C
-40°C to +85°C
-40°C to +85°C
PIN-PACKAGE
8 µMAX
8 SO
TRANSISTOR COUNT: 283
MAX9002EUA
MAX9002ESA
MAX9003EUA
MAX9003ESA
MAX9004EUB
MAX9004ESD
MAX9005EUA
MAX9005ESA
8 µMAX
8 SO
10 µMAX
14 SO
8 µMAX
8 SO
P a c k a g e In fo rm a t io n
–MAX905
18 ______________________________________________________________________________________
Lo w -P o w e r, Hig h -S p e e d , S in g le -S u p p ly
Op Am p + Co m p a ra t o r + Re fe re n c e ICs
–MAX905
P a c k a g e In fo rm a t io n (c o n t in u e d )
______________________________________________________________________________________ 19
Lo w -P o w e r, Hig h -S p e e d , S in g le -S u p p ly
Op Am p + Co m p a ra t o r + Re fe re n c e ICs
P a c k a g e In fo rm a t io n (c o n t in u e d )
–MAX905
Maxim cannot assume responsibility for use of any circuitry other than circuitry entirely embodied in a Maxim product. No circuit patent licenses are
implied. Maxim reserves the right to change the circuitry and specifications without notice at any time.
20 ____________________Ma x im In t e g ra t e d P ro d u c t s , 1 2 0 S a n Ga b rie l Drive , S u n n yva le , CA 9 4 0 8 6 4 0 8 -7 3 7 -7 6 0 0
© 1998 Maxim Integrated Products
Printed USA
is a registered trademark of Maxim Integrated Products.
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