LT1206CR#TR [Linear]
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| 型号： | LT1206CR#TR |
| 厂家： | 
Linear |
| 描述： | 暂无描述 放大器 |
| 文件： | 总16页 (文件大小：386K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
LT1206
250mA/60MHz Current
Feedback Amplifier
U
DESCRIPTIO
EATURE
S
F
■
■
■
■
■
■
■
■
■
■
The LT1206 is a current feedback amplifier with high
output current drive capability and excellent video char-
acteristics. The LT1206 is stable with large capacitive
loads, and can easily supply the large currents required
by the capacitive loading. A shutdown feature switches
the device into a high impedance, low current mode,
reducing dissipation when the device is not in use. For
lower bandwidth applications, the supply current can be
reduced with a single external resistor. The low differen-
tial gain and phase, wide bandwidth, and the 250mA
minimum output current drive make the LT1206 well
suited to drive multiple cables in video systems.
250mA Minimum Output Drive Current
60MHz Bandwidth, AV = 2, RL = 100Ω
900V/µs Slew Rate, AV = 2, RL = 50Ω
0.02% Differential Gain, AV = 2, RL = 30Ω
0.17° Differential Phase, AV = 2, RL = 30Ω
High Input Impedance, 10MΩ
Wide Supply Range, ±5V to ±15V
Shutdown Mode: IS < 200µA
Adjustable Supply Current
Stable with CL = 10,000pF
U
APPLICATIO S
■
The LT1206 is manufactured on Linear Technology’s
proprietary complementary bipolar process.
Video Amplifiers
Cable Drivers
RGB Amplifiers
Test Equipment Amplifiers
Buffers
■
■
■
■
U
TYPICAL APPLICATIO S
Large-Signal Response, CL = 10,000pF
Noninverting Amplifier with Shutdown
15V
V
IN
+
V
OUT
LT1206 COMP
S/D**
C
–
COMP
0.01µF*
–15V
R
R
F
15V
*OPTIONAL, USE WITH CAPACITIVE LOADS
**GROUND SHUTDOWN PIN FOR
NORMAL OPERATION
G
5V
24k
ENABLE
LT1206 • TA01
74C906
LT1206 • TA02
VS = ±15V
R
L = ∞
RF = RG = 3k
1
LT1206
W W W
U
ABSOLUTE AXI U RATI GS
Supply Voltage ..................................................... ±18V
Input Current .................................................... ±15mA
Output Short-Circuit Duration (Note 1) ....... Continuous
Specified Temperature Range (Note 2) ...... 0°C to 70°C
Operating Temperature Range
LT1206C ........................................... –40°C to 85°C
Junction Temperature......................................... 150°C
Storage Temperature Range ................. –65°C to 150°C
Lead Temperature (Soldering, 10 sec)................. 300°C
W
U
/O
PACKAGE RDER I FOR ATIO
TOP VIEW
TOP VIEW
ORDER PART
ORDER PART
+
+
+
V
1
2
3
4
8
7
6
5
V
NC
–IN
1
2
3
4
V
8
7
6
5
NUMBER
NUMBER
OUT
–IN
+IN
OUT
LT1206CS8**
–
–
LT1206CN8**
+IN
V
V
S/D*
COMP
S/D*
COMP
PART MARKING
1206
S8 PACKAGE
8-LEAD PLASTIC SO
N8 PACKAGE
8-LEAD PLASTIC DIP
θJA = 100°C/W
θ
JA ≈ 60°C/W
FRONT VIEW
FRONT VIEW
ORDER PART
NUMBER
ORDER PART
NUMBER
OUT
V
7
6
5
4
3
2
1
OUT
V
7
6
5
4
3
2
1
–
–
COMP
COMP
+
+
LT1206CY**
LT1206CR**
V
V
S/D*
+IN
–IN
S/D*
+IN
–IN
TAB IS
TAB IS
+
+
V
V
Y PACKAGE
7-LEAD TO-220
R PACKAGE
7-LEAD PLASTIC DD
θJA ≈ 30°C/W
*Ground shutdown pin for normal operation
θJC = 5°C/W
**See Note 2
ELECTRICAL CHARACTERISTICS VCM = 0, ±5V ≤ VS ≤ ±15V, pulse tested, VS/D = 0V, unless otherwise noted.
SYMBOL
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNITS
V
Input Offset Voltage
T = 25°C
±3
±10
±15
mV
mV
OS
A
●
●
Input Offset Voltage Drift
Noninverting Input Current
10
µV/°C
+
I
I
T = 25°C
A
±2
±5
±20
µA
µA
IN
●
●
–
Inverting Input Current
T = 25°C
A
±10
±60
±100
µA
µA
IN
e
Input Noise Voltage Density
Input Noise Current Density
Input Noise Current Density
Input Resistance
f = 10kHz, R = 1k, R = 10Ω, R = 0Ω
3.6
2
nV/√Hz
pA/√Hz
pA/√Hz
n
F
G
S
+i
–i
f = 10kHz, R = 1k, R = 10Ω, R = 10k
F G S
n
n
f = 10kHz, R = 1k, R = 10Ω, R = 10k
30
F
G
S
R
V
IN
V
IN
= ±12V, V = ±15V
●
●
1.5
0.5
10
5
MΩ
MΩ
IN
S
= ±2V, V = ±5V
S
C
IN
Input Capacitance
V = ±15V
S
2
pF
Input Voltage Range
V = ±15V
S
●
●
±12
±2
±13.5
±3.5
V
V
S
V = ±5V
2
LT1206
V
CM = 0, ±5V ≤ VS ≤ ±15V, pulse tested, VS/D = 0V, unless otherwise noted.
ELECTRICAL CHARACTERISTICS
SYMBOL
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNITS
CMRR
Common-Mode Rejection Ratio
V = ±15V, V = ±12V
●
●
55
50
62
60
dB
dB
S
CM
V = ±5V, V = ±2V
S
CM
Inverting Input Current
Common-Mode Rejection
V = ±15V, V = ±12V
V = ±5V, V = ±2V
S CM
●
●
0.1
0.1
10
10
µA/V
µA/V
S
CM
PSRR
Power Supply Rejection Ratio
V = ±5V to ±15V
●
●
60
77
30
dB
S
Noninverting Input Current
Power Supply Rejection
V = ±5V to ±15V
S
500
5
nA/V
Inverting Input Current
Power Supply Rejection
V = ±5V to ±15V
S
●
0.7
µA/V
A
Large-Signal Voltage Gain
V = ±15V, V
= ±10V, R = 50Ω
●
●
55
55
71
68
dB
dB
V
S
OUT
L
V = ±5V, V
= ±2V, R = 25Ω
S
OUT
L
–
R
OL
Transresistance, ∆V /∆I
V = ±15V, V
= ±10V, R = 50Ω
●
●
100
75
260
200
kΩ
kΩ
OUT IN
S
OUT
L
V = ±5V, V
= ±2V, R = 25Ω
L
S
OUT
V
Maximum Output Voltage Swing
V = ±15V, R = 50Ω, T = 25°C
±11.5
±10.0
±2.5
±12.5
V
V
V
V
OUT
S
L
A
●
V = ±5V, R = 25Ω, T = 25°C
±3.0
S
L
A
●
●
±2.0
I
I
Maximum Output Current
Supply Current
R = 1Ω
L
250
500
20
1200
mA
OUT
S
V = ±15V, V = 0V, T = 25°C
30
35
mA
mA
S
S/D
A
●
Supply Current, R = 51k (Note 3)
V = ±15V, T = 25°C
12
17
200
10
mA
µA
S/D
S
A
Positive Supply Current, Shutdown
Output Leakage Current, Shutdown
Slew Rate (Note 4)
V = ±15V, V = 15V
●
●
S
S/D
V = ±15V, V = 15V
µA
S
S/D
SR
A = 2, T = 25°C
400
900
0.02
0.17
60
V/µs
%
V
A
Differential Gain (Note 5)
Differential Phase (Note 5)
Small-Signal Bandwidth
V = ±15V, R = 560Ω, R = 560Ω, R = 30Ω
S F G L
V = ±15V, R = 560Ω, R = 560Ω, R = 30Ω
DEG
MHz
S
F
G
L
BW
V = ±15V, Peaking ≤ 0.5dB
S
R = R = 620Ω, R = 100Ω
F
G
L
V = ±15V, Peaking ≤ 0.5dB
52
43
27
MHz
MHz
MHz
S
R = R = 649Ω, R = 50Ω
F
G
L
V = ±15V, Peaking ≤ 0.5dB
S
R = R = 698Ω, R = 30Ω
F
G
L
V = ±15V, Peaking ≤ 0.5dB
S
R = R = 825Ω, R = 10Ω
F
G
L
The
● denotes specifications which apply for 0°C ≤ T ≤ 70°C.
A
beyond 0°C to 70°C. Industrial grade parts tested over –40°C to 85°C are
available on special request. Consult factory.
Note 1: Applies to short circuits to ground only. A short circuit between
the output and either supply may permanently damage the part when
operated on supplies greater than ±10V.
Note 2: Commercial grade parts are designed to operate over the
temperature range of –40°C to 85°C but are neither tested nor guaranteed
Note 3: R is connected between the shutdown pin and ground.
S/D
Note 4: Slew rate is measured at ±5V on a ±10V output signal while
operating on ±15V supplies with R = 1.5k, R = 1.5k and R = 400Ω.
F
G
L
Note 5: NTSC composite video with an output level of 2V.
3
LT1206
W
U
U
-
S ALL SIG AL BA DWIDTH
IS = 20mA Typical, Peaking ≤ 0.1dB
–3dB BW
(MHz)
–0.1dB BW
(MHz)
–3dB BW
(MHz)
–0.1dB BW
(MHz)
A
R
L
R
R
G
A
R
L
R
R
V
F
G
V
F
V = ±5V, R = 0Ω
V = ±5V, R = 0Ω
S
SD
S
SD
–1
1
150
30
681
768
887
768
909
1k
681
768
887
–
–
–
50
35
24
66
37
23
19.2
17
–1
1
150
30
562
649
732
619
715
806
562
649
732
–
–
–
48
34
22
54
36
22.4
21.4
17
10
12.3
10
12.5
150
30
10
22.3
17.5
11.5
150
30
10
22.4
17.5
12
2
150
30
10
576
649
750
576
649
750
48
35
22.4
20.7
18.1
11.7
2
150
30
10
665
787
931
665
787
931
55
36
22.5
23
18.5
11.8
10
150
30
10
442
511
649
48.7
56.2
71.5
40
31
20
19.2
16.5
10.2
10
150
30
10
487
590
768
536
64.9
84.5
44
33
20.7
20.7
17.5
10.8
IS = 10mA Typical, Peaking ≤ 0.1dB
–3dB BW
(MHz)
–0.1dB BW
(MHz)
–3dB BW
(MHz)
–0.1dB BW
(MHz)
A
R
L
R
R
G
A
R
L
R
R
V
F
V
F
G
V = ±5V, R = 10.2k
V = ±15V, R = 60.4k
S
SD
S
SD
–1
1
150
30
576
681
750
665
768
845
576
681
750
–
–
–
35
25
17
12.5
8.7
17.5
12.6
8.2
–1
1
150
30
634
768
866
768
909
1k
634
768
866
–
–
–
41
26.5
17
44
28
16.8
19.1
14
10
16.4
10
9.4
150
30
10
37
25
16.5
150
30
10
18.8
14.4
8.3
2
150
30
10
590
681
768
590
681
768
35
25
16.2
16.8
13.4
8.1
2
150
30
10
649
787
931
649
787
931
40
27
16.5
18.5
14.1
8.1
10
150
30
10
301
392
499
33.2
43.2
54.9
31
23
15
15.6
11.9
7.8
10
150
30
10
301
402
590
33.2
44.2
64.9
33
25
15.3
15.6
13.3
7.4
IS = 5mA Typical, Peaking ≤ 0.1dB
–3dB BW
(MHz)
–0.1dB BW
(MHz)
–3dB BW
(MHz)
–0.1dB BW
(MHz)
A
R
L
R
R
G
A
R
L
R
R
G
V
F
V
F
V = ±5V, R = 22.1k
V = ±15V, R = 121k
S
SD
S
SD
–1
1
150
30
604
715
681
604
715
681
21
10.5
7.4
–1
1
150
30
619
787
825
619
787
825
25
12.5
8.5
14.6
10.5
15.8
10.5
10
6.0
10
5.4
150
30
10
768
866
825
–
–
–
20
14.1
9.8
9.6
6.7
5.1
150
30
10
845
1k
1k
–
–
–
23
15.3
10
10.6
7.6
5.2
2
150
30
10
634
750
732
634
750
732
20
14.1
9.6
9.6
7.2
5.1
2
150
30
10
681
845
866
681
845
866
23
15
10
10.2
7.7
5.4
10
150
30
10
100
100
100
11.1
11.1
11.1
16.2
13.4
9.5
5.8
7.0
4.7
10
150
30
10
100
100
100
11.1
11.1
11.1
15.9
13.6
9.6
4.5
6
4.5
4
LT1206
W U
TYPICAL PERFOR A CE CHARACTERISTICS
Bandwidth and Feedback Resistance
vs Capacitive Load for 0.5dB Peak
Bandwidth vs Supply Voltage
Bandwidth vs Supply Voltage
10k
100
10
1
50
40
30
20
10
0
100
90
80
70
60
50
40
30
20
10
0
BANDWIDTH
PEAKING ≤ 0.5dB
PEAKING ≤ 5dB
A
= 2
A
= 2
PEAKING ≤ 0.5dB
PEAKING ≤ 5dB
V
L
V
L
R
= 10Ω
R
= 100Ω
R
F
R
F
= 560Ω
= 750Ω
R = 470Ω
F
R = 560Ω
F
R = 680Ω
F
1k
R
F
= 1k
R = 750Ω
F
FEEDBACK RESISTOR
R
F
= 2k
A
= 2
V
L
R = 1k
F
R
= ∞
V
C
= ±15V
S
R = 1.5k
F
= 0.01µF
COMP
100
1
10
100
1000
10000
4
12
14
16
6
8
10
18
4
12
14
16
6
8
10
18
CAPACITIVE LOAD (pF)
SUPPLY VOLTAGE (±V)
SUPPLY VOLTAGE (±V)
LT1206 • TPC03
LT1206 • TPC02
LT1206 • TPC01
Bandwidth and Feedback Resistance
vs Capacitive Load for 5dB Peak
Bandwidth vs Supply Voltage
Bandwidth vs Supply Voltage
50
40
30
20
10
0
100
90
80
70
60
50
40
30
20
10
0
10k
100
A
= 10
= 10Ω
A
= 10
= 100Ω
PEAKING ≤ 0.5dB
PEAKING ≤ 5dB
PEAKING ≤ 0.5dB
PEAKING ≤ 5dB
V
L
V
L
BANDWIDTH
R
R
R
F
=390Ω
R
F
= 330Ω
R = 560Ω
F
1k
10
R = 680Ω
F
R
R
= 470Ω
= 680Ω
F
R = 1k
F
A
= +2
F
V
L
FEEDBACK RESISTOR
R = 1.5k
F
R
= ∞
V
C
= ±15V
S
R
F
= 1.5k
= 0.01µF
COMP
100
1
10k
16
4
6
8
10
12
14
16
18
4
12
14
6
8
10
18
1
10
100
1k
CAPACITIVE LOAD (pF)
SUPPLY VOLTAGE (±V)
SUPPLY VOLTAGE (±V)
LT1206 • TPC05
LT1206 • TPC04
LT1206 • TPC06
Spot Noise Voltage and Current
vs Frequency
Differential Phase
vs Supply Voltage
Differential Gain
vs Supply Voltage
100
10
1
0.50
0.40
0.30
0.10
0.08
0.06
R
V
= R = 560Ω
F
G
A
= 2
R
R
= 15Ω
= 30Ω
L
R
= 15Ω
= 30Ω
N PACKAGE
L
L
–i
n
R
A
= R = 560Ω
F
V
G
R
= 2
N PACKAGE
0.20
0.10
0
0.04
0.02
0
L
R
= 50Ω
L
e
n
R
R
= 50Ω
L
i
n
= 150Ω
L
R
7
= 150Ω
L
5
7
9
11
13
15
5
9
11
13
15
10
100
1k
FREQUENCY (Hz)
10k
100k
SUPPLY VOLTAGE (±V)
SUPPLY VOLTAGE (±V)
LT1206 • TPC09
LT1206 • TPC07
LT1206 • TPC08
5
LT1206
W U
TYPICAL PERFOR A CE CHARACTERISTICS
Supply Current vs
Ambient Temperature, VS = ±5V
Supply Current vs
Ambient Temperature, VS = ±15V
Supply Current vs Supply Voltage
24
22
20
25
20
15
10
5
25
20
15
10
5
V
S/D
= 0V
A
= 1
A
= 1
V
V
L
T = –40˚C
R
= 0Ω
J
R
= ∞
R
= ∞
L
SD
R
= 0Ω
SD
N PACKAGE
N PACKAGE
T = 25˚C
J
18
16
14
R
R
= 10.2k
= 22.1k
R
R
= 60.4k
= 121k
SD
SD
T = 85˚C
J
SD
SD
T = 125˚C
J
12
10
0
0
50
75 100 125
4
12
14
16
50
–50
–25
0
25
6
8
10
18
–50
0
25
75 100 125
–25
SUPPLY VOLTAGE (±V)
TEMPERATURE (°C)
TEMPERATURE (°C)
LT1206 • TPC10
LT1206 • TPC12
LT1206 • TPC11
Supply Current
vs Shutdown Pin Current
Input Common-Mode Limit
vs Junction Temperature
Output Short-Circuit Current
vs Junction Temperature
+
V
20
18
16
14
12
10
8
1.0
0.9
V
S
= ±15V
– 0.5
–1.0
–1.5
–2.0
2.0
0.8
0.7
0.6
0.5
0.4
SOURCING
SINKING
1.5
6
1.0
4
0.5
2
–
0.3
0
V
50
TEMPERATURE (°C)
100 125
0
100
200
300
400
500
–50 –25
0
25
75
–50 –25
0
100 125
25
50
75
TEMPERATURE (°C)
SHUTDOWN PIN CURRENT (µA)
LT1206 • TPC11
LT1206 • TPC15
LT1206 • TPC14
Supply Current vs Large Signal
Output Frequency (No Load)
Output Saturation Voltage
vs Junction Temperature
Power Supply Rejection Ratio
vs Frequency
+
70
60
50
40
30
20
10
0
60
50
40
30
20
10
V
A
= 2
V
= ±15V
V
L
S
S
R
V
= 50Ω
R
= 2k
L
S
F
L
–1
–2
–3
–4
4
R
= ∞
= ±15V
NEGATIVE
POSITIVE
V
V
= ±15V
R
= R = 1k
G
= 20V
OUT
P-P
R
= 50Ω
L
R
R
= 50Ω
L
L
3
2
= 2k
1
–
V
10k
100k
1M
10M
100M
10k
100k
1M
10M
–50 –25
0
100 125
25
50
75
FREQUENCY (Hz)
TEMPERATURE (°C)
FREQUENCY (Hz)
LT1206 • TPC17
LT1206 • TPC18
LT1206 • TPC16
6
LT1206
W U
TYPICAL PERFOR A CE CHARACTERISTICS
Output Impedance in Shutdown
vs Frequency
2nd and 3rd Harmonic Distortion
vs Frequency
Output Impedance vs Frequency
–30
–40
–50
–60
–70
–80
–90
100
10
100k
10k
V
V
= ±15V
V
I
= ±15V
= 0mA
A
= 1
S
O
S
O
V
F
S
= 2V
R = 1k
P-P
V
= ±15V
R
= 121k
2nd
S/D
R
L
= 10Ω
3rd
2nd
R
= 0Ω
S/D
1
1k
R
= 30Ω
L
3rd
0.1
100
0.01
100k
10
100k
1
2
3
4
5
6 7 8 9 10
1M
10M
100M
1M
10M
100M
FREQUENCY (MHz)
FREQUENCY (Hz)
FREQUENCY (Hz)
LT1206 • TPC21
LT1206 • TPC19
LT1206 • TPC20
3rd Order Intercept vs Frequency
Test Circuit for 3rd Order Intercept
60
50
40
30
V
= ±15V
S
L
F
G
+
R
= 50Ω
R = 590Ω
R
P
LT1206
O
= 64.9Ω
–
590Ω
50Ω
65Ω
MEASURE INTERCEPT AT P
O
LT1206 • TPC23
20
10
0
10
15
20
25
30
5
FREQUENCY (MHz)
LT1206 • TPC22
7
LT1206
W
W
SI PLIFIED SCHE ATIC
+
V
TO ALL
CURRENT
SOURCES
Q5
Q10
Q2
D1
Q11
Q6
Q15
Q18
Q1
Q17
Q9
–
–
V
1.25k
+IN
50Ω
COMP
V
C
C
–IN
R
C
OUTPUT
+
V
SHUTDOWN
+
V
Q12
Q3
Q8
Q16
Q14
D2
Q4
Q13
Q7
–
V
LT1206 • TC
O U
W
U
PPLICATI
A
S I FOR ATIO
The LT1206 is a current feedback amplifier with high
output current drive capability. The device is stable with
large capacitive loads and can easily supply the high
currents required by capacitive loads. The amplifier will
drive low impedance loads such as cables with excellent
linearity at high frequencies.
line when the response has 0.5dB to 5dB of peaking. The
curves stop where the response has more than 5dB of
peaking.
For resistive loads, the COMP pin should be left open (see
section on capacitive loads).
Capacitive Loads
Feedback Resistor Selection
The LT1206 includes an optional compensation network
for driving capacitive loads. This network eliminates most
of the output stage peaking associated with capacitive
loads, allowing the frequency response to be flattened.
Figure 1 shows the effect of the network on a 200pF load.
Without the optional compensation, there is a 5dB peak at
40MHz caused by the effect of the capacitance on the
output stage. Adding a 0.01µF bypass capacitor between
theoutputandtheCOMPpinsconnectsthecompensation
and completely eliminates the peaking. A lower value
feedbackresistorcannowbeused, resultinginaresponse
The optimum value for the feedback resistors is a function
of the operating conditions of the device, the load imped-
ance and the desired flatness of response. The Typical AC
Performance tables give the values which result in the
highest 0.1dB and 0.5dB bandwidths for various resistive
loads and operating conditions. If this level of flatness is
not required, a higher bandwidth can be obtained by use
of a lower feedback resistor. The characteristic curves of
Bandwidth vs Supply Voltage indicate feedback resistors
for peaking up to 5dB. These curves use a solid line when
the response has less than 0.5dB of peaking and a dashed
8
LT1206
O U
W
U
PPLICATI
S I FOR ATIO
A
12
a40pFcapacitorandthesupplycurrentistypically100µA.
The shutdown pin is referenced to the positive supply
through an internal bias circuit (see the simplified sche-
matic). Aneasywaytoforceshutdownistouseopendrain
(collector) logic. The circuit shown in Figure 2 uses a
74C904 buffer to interface between 5V logic and the
LT1206. The switching time between the active and shut-
down states is less than 1µs. A 24k pull-up resistor
speeds up the turn-off time and insures that the LT1206
is completely turned off. Because the pin is referenced to
the positive supply, the logic used should have a break-
down voltage of greater than the positive supply voltage.
No other circuitry is necessary as the internal circuit
limits the shutdown pin current to about 500µA. Figure 3
shows the resulting waveforms.
V
S
= ±15V
10
8
R = 1.2k
F
COMPENSATION
6
4
2
R = 2k
F
NO COMPENSATION
0
R = 2k
F
–2
–4
–6
–8
COMPENSATION
1
10
100
FREQUENCY (MHz)
LT1206 • F01
Figure 1.
which is flat to 0.35dB to 30MHz. The network has the
greatest effect for CL in the range of 0pF to 1000pF. The
graph of Maximum Capacitive Load vs Feedback Resistor
can be used to select the appropriate value of feedback
resistor. The values shown are for 0.5dB and 5dB peaking
at a gain of 2 with no resistive load. This is a worst case
condition, as the amplifier is more stable at higher gains
and with some resistive load in parallel with the capaci-
tance. Also shown is the –3dB bandwidth with the sug-
gested feedback resistor vs the load capacitance.
15V
V
+
IN
V
LT1206
OUT
S/D
–
–15V
R
R
F
15V
24k
G
5V
Although the optional compensation works well with
capacitive loads, it simply reduces the bandwidth when it
is connected with resistive loads. For instance, with a 30Ω
load, the bandwidth drops from 55MHz to 35MHz when
thecompensationisconnected. Hence, thecompensation
wasmadeoptional.Todisconnecttheoptionalcompensa-
tion, leave the COMP pin open.
ENABLE
LT1206 • F02
74C906
Figure 2. Shutdown Interface
Shutdown/Current Set
If the shutdown feature is not used, the SHUTDOWN pin
must be connected to ground or V–.
Theshutdownpincanbeusedtoeitherturnoffthebiasing
for the amplifier, reducing the quiescent current to less
than 200µA, or to control the quiescent current in normal
operation.
LT1206 • F3
AV = 1
R
PU = 24k
The total bias current in the LT1206 is controlled by the
current flowing out of the shutdown pin. When the shut-
down pin is open or driven to the positive supply, the part
is shut down. In the shutdown mode, the output looks like
R
R
F = 825Ω
L = 50Ω
VIN = 1VP-P
Figure 3. Shutdown Operation
9
LT1206
PPLICATI
For applications where the full bandwidth of the amplifier
is not required, the quiescent current of the device may be
reducedbyconnectingaresistorfromtheshutdownpinto
ground. The quiescent current will be approximately 40
times the current in the shutdown pin. The voltage across
the resistor in this condition is V+ – 3VBE. For example, a
60k resistor will set the quiescent supply current to 10mA
with VS = ±15V.
O U
W
U
A
S I FOR ATIO
Slew Rate
Unlike a traditional op amp, the slew rate of a current
feedback amplifier is not independent of the amplifier gain
configuration. There are slew rate limitations in both the
input stage and the output stage. In the inverting mode,
and for higher gains in the noninverting mode, the signal
amplitude on the input pins is small and the overall slew
rate is that of the output stage. The input stage slew rate
is related to the quiescent current and will be reduced as
the supply current is reduced. The output slew rate is set
by the value of the feedback resistors and the internal
capacitance. Larger feedback resistors will reduce the
slew rate as will lower supply voltages, similar to the way
the bandwidth is reduced. The photos (Figures 5a, 5b and
5c) show the large-signal response of the LT1206 for
various gain configurations. The slew rate varies from
860V/µs for a gain of 1, to 1400V/µs for a gain of –1.
Thephotos(Figures4aand4b)showtheeffectofreducing
thequiescentsupplycurrentonthelarge-signalresponse.
The quiescent current can be reduced to 5mA in the
invertingconfigurationwithoutmuchchangeinresponse.
In noninverting mode, however, the slew rate is reduced
as the quiescent current is reduced.
LT1206 • F04a
RF = 750Ω
RL = 50Ω
IQ = 5mA, 10mA, 20mA
S = ±15V
V
Figure 4a. Large-Signal Response vs IQ, AV = –1
LT1206 • F05a
RF = 825Ω
RL = 50Ω
VS = ±15V
Figure 5a. Large-Signal Response, AV = 1
LT1206 • F04b
RF = 750Ω
L = 50Ω
IQ = 5mA, 10mA, 20mA
VS = ±15V
R
Figure 4b. Large-Signal Response vs IQ, AV = 2
LT1206 • F05b
RF = RG = 750Ω
L = 50Ω
VS = ±15V
R
Figure 5b. Large-Signal Response, AV = –1
10
LT1206
O U
W
U
PPLICATI
A
S
I FOR ATIO
the maximum allowable input voltage. To allow for some
margin, it is recommended that the input signal be less
than ±5V when the device is shut down.
Capacitance on the Inverting Input
Current feedback amplifiers require resistive feedback
from the output to the inverting input for stable operation.
Take care to minimize the stray capacitance between the
output and the inverting input. Capacitance on the invert-
ing input to ground will cause peaking in the frequency
response (and overshoot in the transient response), but it
does not degrade the stability of the amplifier.
LT1206 • F04c
RF = 750Ω
RL = 50Ω
Figure 5c. Large-Signal Response, AV = 2
Power Supplies
When the LT1206 is used to drive capacitive loads, the
available output current can limit the overall slew rate. In
the fastest configuration, the LT1206 is capable of a slew
rateofover1V/ns. Thecurrentrequiredtoslewacapacitor
at this rate is 1mA per picofarad of capacitance, so
10,000pF would require 10A! The photo (Figure 6) shows
thelargesignalbehaviorwithCL =10,000pF. Theslewrate
isabout60V/µs,determinedbythecurrentlimitof600mA.
The LT1206 will operate from single or split supplies from
±5V (10V total) to ±15V (30V total). It is not necessary to
use equal value split supplies, however the offset voltage
and inverting input bias current will change. The offset
voltage changes about 500µV per volt of supply mis-
match. The inverting bias current can change as much as
5µA per volt of supply mismatch, though typically the
change is less than 0.5µA per volt.
Thermal Considerations
The LT1206 contains a thermal shutdown feature which
protects against excessive internal (junction) tempera-
ture. If the junction temperature of the device exceeds the
protection threshold, the device will begin cycling be-
tween normal operation and an off state. The cycling is not
harmful to the part. The thermal cycling occurs at a slow
rate, typically10mstoseveralseconds, whichdependson
the power dissipation and the thermal time constants of
the package and heat sinking. Raising the ambient tem-
perature until the device begins thermal shutdown gives a
good indication of how much margin there is in the
thermal design.
LT1206 • F06
VS = ±15V
F = RG = 3k
RL = ∞
R
Figure 6. Large-Signal Response, CL = 10,000pF
Differential Input Signal Swing
For surface mount devices heat sinking is accomplished
by using the heat spreading capabilities of the PC board
and its copper traces. Experiments have shown that the
heat spreading copper layer does not need to be electri-
cally connected to the tab of the device. The PCB material
can be very effective at transmitting heat between the pad
area attached to the tab of the device, and a ground or
The differential input swing is limited to about ±6V by an
ESD protection device connected between the inputs. In
normal operation, the differential voltage between the
input pins is small, so this clamp has no effect; however,
in the shutdown mode the differential swing can be the
same as the input swing. The clamp voltage will then set
11
LT1206
PPLICATI
power plane layer either inside or on the opposite side of
the board. Although the actual thermal resistance of the
PCB material is high, the length/area ratio of the thermal
resistance between the layer is small. Copper board stiff-
eners and plated through holes can also be used to spread
the heat generated by the device.
O U
W
U
A
S I FOR ATIO
Calculating Junction Temperature
The junction temperature can be calculated from the
equation:
TJ = (PD × θJA) + TA
where:
Tables1and2listthermalresistanceforeachpackage.For
the TO-220 package, thermal resistance is given for junc-
tion-to-case only since this package is usually mounted to
a heat sink. Measured values of thermal resistance for
severaldifferentboardsizesandcopperareasarelistedfor
each surface mount package. All measurements were
taken in still air on 3/32" FR-4 board with 1oz copper. This
data can be used as a rough guideline in estimating
thermal resistance. The thermal resistance for each appli-
cation will be affected by thermal interactions with other
components as well as board size and shape.
TJ = Junction Temperature
TA = Ambient Temperature
PD = Device Dissipation
θJA = Thermal Resistance (Junction-to Ambient)
As an example, calculate the junction temperature for the
circuitinFigure7fortheN8,S8,andRpackagesassuming
a 70°C ambient temperature.
15V
39mA
I
+
Table 1. R Package, 7-Lead DD
12V
LT1206
S/D
–
330Ω
COPPER AREA
–12V
THERMAL RESISTANCE
f = 2MHz
0.01µF
TOPSIDE*
BACKSIDE
BOARD AREA (JUNCTION-TO-AMBIENT)
2k
300pF
2500 sq. mm 2500 sq. mm 2500 sq. mm
1000 sq. mm 2500 sq. mm 2500 sq. mm
25°C/W
27°C/W
35°C/W
–15V
2k
LT1206 • F07
125 sq. mm
2500 sq. mm 2500 sq. mm
Figure 7. Thermal Calculation Example
*Tab of device attached to topside copper
The device dissipation can be found by measuring the
supply currents, calculating the total dissipation, and
then subtracting the dissipation in the load and feedback
network.
Table 2. S8 Package, 8-Lead Plastic SOIC
COPPER AREA
THERMAL RESISTANCE
TOPSIDE*
BACKSIDE
BOARD AREA (JUNCTION-TO-AMBIENT)
2500 sq. mm 2500 sq. mm 2500 sq. mm
1000 sq. mm 2500 sq. mm 2500 sq. mm
60°C/W
62°C/W
65°C/W
69°C/W
73°C/W
80°C/W
83°C/W
PD = (39mA × 30V) – (12V)2/(2k||2k) = 1.03W
225 sq. mm
100 sq. mm
100 sq. mm
100 sq. mm
100 sq. mm
2500 sq. mm 2500 sq. mm
2500 sq. mm 2500 sq. mm
1000 sq. mm 2500 sq. mm
225 sq. mm 2500 sq. mm
100 sq. mm 2500 sq. mm
Then:
TJ = (1.03W × 100°C/W) + 70°C = 173°C
for the N8 package
TJ = (1.03W × 65°C/W) × + 70°C = 137°C
*Pins 1 and 8 attached to topside copper
for the S8 with 225 sq. mm topside heat sinking
TJ = (1.03W × 35°C/W) × + 70°C = 106°C
for the R package with 100 sq. mm topside
heat sinking
Y Package, 7-Lead TO-220
Thermal Resistance (Junction-to-Case) = 5°C/W
N8 Package, 8-Lead DIP
Thermal Resistance (Junction-to-Ambient) = 100°C/W
Since the Maximum Junction Temperature is 150°C, the
N8 package is clearly unacceptable. Both the S8 and R
packages are usable.
12
LT1206
U
TYPICAL APPLICATIO S
Precision ×10 Hi Current Amplifier
CMOS Logic to Shutdown Interface
15V
V
IN
+
LT1097
+
+
LT1206
COMP
S/D
OUT
–
24k
LT1206
S/D
–
–
0.01µF
500pF
LT1206 • TA05
5V
–15V
330Ω
3k
10k
2N3904
10k
LT1206 • TA03
OUTPUT OFFSET: < 500µV
SLEW RATE: 2V/µs
1k
BANDWIDTH: 4MHz
STABLE WITH C < 10nF
L
Distribution Amplifier
V
IN
+
–
75Ω CABLE
75Ω
Low Noise ×10 Buffered Line Driver
LT1206
S/D
75Ω
75Ω
R
F
15V
1µF
15V
1µF
75Ω
+
LT1206 • TA06
+
+
–
R
G
LT1115
+
–
OUTPUT
75Ω
LT1206
S/D
1µF
+
0.01µF
R
L
–15V
1µF
68pF
+
Buffer AV = 1
–15V
560Ω
909Ω
560Ω
V
+
IN
LT1206
COMP
S/D
V
*OPTIONAL, USE WITH CAPACITIVE LOADS
**VALUE OF R DEPENDS ON SUPPLY
F
VOLTAGE AND LOADING. SELECT
FROM TYPICAL AC PERFORMANCE
TABLE OR DETERMINE EMPIRICALLY
OUT
LT1206 • TA04
–
0.01µF*
100Ω
R
O
= 32Ω
L
V
= 5V
RMS
THD + NOISE = 0.0009% AT 1kHz
= 0.004% AT 20kHz
SMALL SIGNAL 0.1dB BANDWIDTH = 600kHz
R **
F
LT1206 • TA07
13
LT1206
U
PACKAGE DESCRIPTIO Dimensions in inches (millimeters) unless otherwise noted.
N8 Package
8-Lead Plastic DIP
0.400
(10.160)
MAX
8
7
6
3
5
4
0.250 ± 0.010
(6.350 ± 0.254)
1
2
0.130 ± 0.005
0.300 – 0.320
0.045 – 0.065
(3.302 ± 0.127)
(1.143 – 1.651)
(7.620 – 8.128)
0.065
(1.651)
TYP
0.009 – 0.015
(0.229 – 0.381)
0.125
0.020
(0.508)
MIN
(3.175)
MIN
+0.025
0.045 ± 0.015
(1.143 ± 0.381)
0.325
–0.015
+0.635
8.255
(
)
–0.381
0.100 ± 0.010
(2.540 ± 0.254)
0.018 ± 0.003
(0.457 ± 0.076)
N8 0392
R Package
7-Lead Plastic DD
0.060
0.401 ± 0.015
(1.524)
(10.185 ± 0.381)
0.175 ± 0.008
0.050 ± 0.008
(4.445 ± 0.203)
(1.270 ± 0.203)
15° TYP
+0.008
0.004
+0.012
–0.020
+0.305
–0.508
–0.004
0.331
0.059
(1.499)
TYP
+0.203
–0.102
0.102
(
)
8.407
(
)
0.105 ± 0.008
(2.667 ± 0.203)
0.050 ± 0.010
(1.270 ± 0.254)
0.030 ± 0.008
(0.762 ± 0.203)
0.050 ± 0.012
(1.270 ± 0.305)
+0.012
–0.020
+0.305
–0.508
0.022 ± 0.005
(0.559 ± 0.127)
0.143
3.632
(
)
DD7 0693
14
LT1206
U
PACKAGE DESCRIPTIO Dimensions in inches (millimeters) unless otherwise noted.
S8 Package
8-Lead Plastic SOIC
0.189 – 0.197
(4.801 – 5.004)
7
5
8
6
0.150 – 0.157
(3.810 – 3.988)
0.228 – 0.244
(5.791 – 6.197)
1
3
4
2
0.010 – 0.020
(0.254 – 0.508)
× 45°
0.053 – 0.069
(1.346 – 1.752)
0.004 – 0.010
(0.101 – 0.254)
0.008 – 0.010
(0.203 – 0.254)
0°– 8° TYP
0.016 – 0.050
0.406 – 1.270
0.050
(1.270)
BSC
0.014 – 0.019
(0.355 – 0.483)
SO8 0392
Y Package
7-Lead TO-220
0.390 – 0.410
(9.91 – 10.41)
0.147 – 0.155
(3.73 – 3.94)
DIA
0.169 – 0.185
(4.29 – 4.70)
0.045 – 0.055
(1.14 – 1.40)
0.235 – 0.258
(5.97 – 6.55)
0.103 – 0.113
(2.62 – 2.87)
0.560 – 0.590
(14.22 – 14.99)
0.620
(15.75)
TYP
0.700 – 0.728
(17.78 – 18.49)
0.152 – 0.202
(3.86 – 5.13)
0.260 – 0.320
(6.60 – 8.13)
0.026 – 0.036
(0.66 – 0.91)
0.095 – 0.115
(2.41 – 2.92)
0.155 – 0.195
(3.94 – 4.95)
0.016 – 0.022
0.045 – 0.055
(1.14 – 1.40)
(0.41 – 0.56)
0.135 – 0.165
(3.43 – 4.19)
Y7 0893
Information furnished by Linear Technology Corporation is believed to be accurate and reliable.
However, no responsibility is assumed for its use. Linear Technology Corporation makes no represen-
tation that the interconnection of circuits as described herein will not infringe on existing patent rights.
15
LT1206
U.S. Area Sales Offices
SOUTHEAST REGION
Linear Technology Corporation
17060 Dallas Parkway
Suite 208
Dallas, TX 75248
Phone: (214) 733-3071
FAX: (214) 380-5138
SOUTHWEST REGION
Linear Technology Corporation
22141 Ventura Blvd.
NORTHEAST REGION
Linear Technology Corporation
One Oxford Valley
2300 E. Lincoln Hwy.,Suite 306
Langhorne, PA 19047
Phone: (215) 757-8578
FAX: (215) 757-5631
Suite 206
Woodland Hills, CA 91364
Phone: (818) 703-0835
FAX: (818) 703-0517
CENTRAL REGION
Linear Technology Corporation
Chesapeake Square
NORTHWEST REGION
Linear Technology Corporation
782 Sycamore Dr.
Linear Technology Corporation
266 Lowell St., Suite B-8
Wilmington, MA 01887
Phone: (508) 658-3881
FAX: (508) 658-2701
229 Mitchell Court, Suite A-25
Addison, IL 60101
Phone: (708) 620-6910
FAX: (708) 620-6977
Milpitas, CA 95035
Phone: (408) 428-2050
FAX: (408) 432-6331
International Sales Offices
FRANCE
KOREA
TAIWAN
Linear Technology S.A.R.L.
Immeuble "Le Quartz"
58 Chemin de la Justice
92290 Chatenay Malabry
France
Linear Technology Korea Branch
Namsong Building, #505
Itaewon-Dong 260-199
Yongsan-Ku, Seoul
Korea
Linear Technology Corporation
Rm. 801, No. 46, Sec. 2
Chung Shan N. Rd.
Taipei, Taiwan, R.O.C.
Phone: 886-2-521-7575
FAX: 886-2-562-2285
Phone: 33-1-41079555
FAX: 33-1-46314613
Phone: 82-2-792-1617
FAX: 82-2-792-1619
UNITED KINGDOM
GERMANY
SINGAPORE
Linear Technology (UK) Ltd.
The Coliseum, Riverside Way
Camberley, Surrey GU15 3YL
United Kingdom
Phone: 44-276-677676
FAX: 44-276-64851
Linear Techonolgy GMBH
Untere Hauptstr. 9
D-85386 Eching
Germany
Phone: 49-89-3197410
FAX: 49-89-3194821
Linear Technology Pte. Ltd.
101 Boon Keng Road
#02-15 Kallang Ind. Estates
Singapore 1233
Phone: 65-293-5322
FAX: 65-292-0398
JAPAN
Linear Technology KK
5F YZ Bldg.
4-4-12 Iidabashi, Chiyoda-Ku
Tokyo, 102 Japan
Phone: 81-3-3237-7891
FAX: 81-3-3237-8010
World Headquarters
Linear Technology Corporation
1630 McCarthy Blvd.
Milpitas, CA 95035-7487
Phone: (408) 432-1900
FAX: (408) 434-0507
06/24/93
LT/GP 0993 10K REV 0 • PRINTED IN USA
LINEAR TECHNOLOGY CORPORATION 1993
Linear Technology Corporation
1630 McCarthy Blvd., Milpitas, CA 95035-7487
16
●
●
(408) 432-1900 FAX: (408) 434-0507 TELEX: 499-3977
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