LT1217CS8 [Linear]
Low Power 10MHz Current Feedback Amplifier; 低功率10MHz的电流反馈放大器
| 型号： | LT1217CS8 |
| 厂家： | 
Linear |
| 描述： | Low Power 10MHz Current Feedback Amplifier |
| 文件： | 总8页 (文件大小：241K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
LT1217
Low Power 10MHz
Current Feedback Amplifier
U
DESCRIPTIO
EATURE
S
F
■
■
■
■
■
■
■
■
■
1mA Quiescent Current
TheLT1217isa10MHzcurrentfeedbackamplifierwithDC
characteristics better than many voltage feedback ampli-
fiers.Thisversatileamplifierisfast,280nssettlingto0.1%
for a 10V step thanks to its 500V/µs slew rate. The LT1217
is manufactured on Linear Technology’s proprietary
complementary bipolar process resulting in a low 1mA
quiescent current. To reduce power dissipation further,
the LT1217 can be turned off, eliminating the load current
and dropping the supply current to 350µA.
50mA Output Current (Minimum)
10MHz Bandwidth
500V/µs Slew Rate
280ns Settling Time to 0.1%
Wide Supply Range, ±5V to ±15V
1mV Input Offset Voltage
100nA Input Bias Current
100MΩ Input Resistance
The LT1217 is excellent for driving cables and other low
impedance loads thanks to a minimum output drive cur-
rentof50mA.Operatingonanysuppliesfrom±5Vto±15V
allows the LT1217 to be used in almost any system. Like
other current feedback amplifiers, the LT1217 has high
gainbandwidthathighgains. Thebandwidthisover1MHz
at a gain of 100.
O U
PPLICATI
Video Amplifiers
Buffers
S
A
■
■
■
■
■
IF and RF Amplification
Cable Drivers
8, 10, 12-Bit Data Acquisition Systems
The LT1217 comes in the industry standard pinout and
can upgrade the performance of many older products.
U
O
TYPICAL APPLICATI
Cable Driver
Voltage Gain vs Frequency
60
V
+
–
IN
50
40
V
R
R
= ±15V
= 3k
= 100Ω
75Ω
S
F
L
LT1217
R
R
R
R
= 30Ω
= 100Ω
= 330Ω
= 1.3k
= ∞
G
G
G
G
75Ω
30
R
CABLE
F
3k
20
V
10
OUT
R
R
G
G
0
3k
75Ω
–10
–20
R
100k
1M
10M
100M
F
A
= 1 +
V
R
G
FREQUENCY (Hz)
AT AMPLIFIER OUTPUT.
6dB LESS AT V
LT1217 • TA02
.
LT1217 • TA01
OUT
1
LT1217
W W W
U
/O
ABSOLUTE AXI U RATI GS
PACKAGE RDER I FOR ATIO
Supply Voltage ...................................................... ±18V
Input Current ...................................................... ±10mA
Input Voltage ............................ Equal to Supply Voltage
Output Short Circuit Duration (Note 1) .........Continuous
Operating Temperature Range ..................... 0°C to 70°C
Storage Temperature Range ................. –65°C to 150°C
Junction Temperature........................................... 150°C
Lead Temperature (Soldering, 10 sec.)................. 300°C
ORDER PART
TOP VIEW
NUMBER
NULL
–IN
1
2
3
4
8
7
6
5
SHUTDOWN
+
V
LT1217CN8
LT1217CS8
+IN
OUT
–
V
NULL
S8 PART MARKING
1217
N8 PACKAGE
8-LEAD PLASTIC DIP 8-LEAD PLASTIC SOIC
S8 PACKAGE
LT1217 • POI01
ELECTRICAL CHARACTERISTICS VS = ±15V, TA = 0°C to 70°C unless otherwise noted.
SYMBOL
PARAMETER
CONDITIONS
MIN
TYP
MAX
±3
UNITS
mV
V
Input Offset Voltage
V
CM
V
CM
V
CM
= 0V
= 0V
= 0V
●
●
●
±1
OS
IN+
IN–
I
I
Non-Inverting Input Current
Inverting Input Current
±100 ±500
nA
±100 ±500
nA
e
Input Noise Voltage Density
Input Noise Current Density
Input Resistance
f = 1kHz, R = 1k, R = 10Ω
6.5
0.7
nV/√Hz
pA/√Hz
MΩ
pF
n
F
G
i
n
f = 1kHz, R = 1k, R = 10Ω
F G
R
V
IN
= ±10V
●
20
100
1.5
IN
C
Input Capacitance
IN
Input Voltage Range
●
●
●
●
●
●
±10
±12
66
V
CMRR
PSRR
Common Mode Rejection Ratio
Inverting Input Current Common Mode Rejection
Power Supply Rejection Ratio
Non-Inverting Input Current Power Supply Rejection
Inverting Input Current Power Supply Rejection
Large Signal Voltage Gain
V
V
= ±10V
= ±10V
60
dB
CM
5
20
nA/V
dB
CM
V = ±4.5V to ±18V
S
68
76
2
V = ±4.5V to ±18V
S
20
50
nA/V
nA/V
V = ±4.5V to ±18V
S
10
105
A
V
R
R
= 2k, V = ±10V
OUT
●
●
90
70
dB
dB
LOAD
LOAD
= 400Ω, V
= ±10V
OUT
R
OL
Transresistance, ∆V /∆I
R
LOAD
R
LOAD
= 2k, V = ±10V
OUT
●
●
5
1.5
45
MΩ
MΩ
OUT IN–
= 400Ω, V
= ±10V
OUT
V
Output Swing
R
R
= 2k
= 200Ω
●
●
±12
±10
±13
V
V
OUT
OUT
LOAD
LOAD
I
Output Current
R
LOAD
= 0Ω
●
●
50
100
500
10
mA
V/µs
MHz
ns
SR
Slew Rate (Note 2, 3)
Bandwidth
R = 3k, R = 3k
F
100
G
BW
R = 3k, R = 3k, V
F
= 100mV
= 1V
G
OUT
OUT
OUT
OUT
OUT
t
t
Rise Time, Fall Time (Note 3)
Propagation Delay
Overshoot
R = 3k, R = 3k, V
F
●
30
40
r
G
R = 3k, R = 3k, V
F
= 1V
25
ns
PD
G
R = 3k, R = 3k, V
F
= 1V
5
%
G
t
I
Settling Time, 0.1%
Supply Current
R = 3k, R = 3k, V
F
= 10V
280
1
ns
s
G
V
IN
= 0V
●
●
2
mA
µA
S
Supply Current, Shutdown
Pin 8 Current = 50µA
350
1000
The
●
denotes specifications which apply over the operating temperature
Note 2: Non-Inverting operation, V
= ±10V, measured at ±5V.
OUT
range.
Note 3: AC parameters are 100% tested on the plastic DIP packaged parts
(N suffix), and are sample tested on every lot of the SO packaged parts
(S suffix).
Note 1: A heat sink may be required.
2
LT1217
U W
TYPICAL PERFOR A CE CHARACTERISTICS
Voltage Gain and Phase vs
Frequency, Gain = 6dB
–3dB Bandwidth vs Supply
–3dB Bandwidth vs Supply
Voltage, Gain = 2, RL = 100Ω
Voltage, Gain = 2, RL = 1kΩ
8
7
0
30
25
30
25
PHASE
45
PEAKING ≤ 0.5dB
PEAKING ≤ 5dB
PEAKING ≤ 0.5dB
PEAKING ≤ 5dB
6
5
90
GAIN
R = 1k
F
135
180
225
20
15
20
15
R = 1k
4
F
R = 2k
F
3
R = 2k
F
R = 3k
F
2
10
5
10
5
R = 3k
1
F
R = 5.1k
F
V
R
R
= ±15V
= 100Ω
= 3k
0
S
L
F
R = 5.1k
F
–1
–2
0
0
0.01
0.1
1.0
10
0
2
4
6
8
10 12 14 16 18
0
2
4
6
8
10 12 14 16 18
FREQUENCY (MHz)
SUPPLY VOLTAGE (±V)
SUPPLY VOLTAGE (±V)
LT1217 • TPC03
LT1217 • TPC01
LT1217 • TPC02
Voltage Gain and Phase vs
Frequency, Gain = 20dB
–3dB Bandwidth vs Supply
–3dB Bandwidth vs Supply
Voltage, Gain = 10, RL = 1kΩ
Voltage, Gain = 10, RL = 100Ω
22
21
0
20
18
16
20
18
16
PHASE
PEAKING ≤ 0.5dB
PEAKING ≤ 5dB
PEAKING ≤ 0.5dB
PEAKING ≤ 5dB
45
20
19
18
17
16
15
14
13
12
90
GAIN
R = 750Ω
F
135
180
225
14
12
14
12
R = 750Ω
F
R = 1k
F
R = 1k
R = 2k
F
F
10
8
10
8
R = 3k
F
R = 2k
F
R = 3k
F
6
6
R = 5.1k
F
V
= ±15V
= 100Ω
4
2
0
4
2
0
S
L
F
R = 5.1k
F
R
R = 3k
0.01
0.1
1.0
10
0
2
4
6
8
10 12 14 16 18
0
2
4
6
8
10 12 14 16 18
FREQUENCY (MHz)
SUPPLY VOLTAGE (±V)
SUPPLY VOLTAGE (±V)
LT1217 • TPC06
LT1217 • TPC04
LT1217 • TPC05
Voltage Gain and Phase vs
Frequency, Gain = 40dB
–3dB Bandwidth vs Supply
Voltage, Gain = 100, RL = 100Ω
–3dB Bandwidth vs Supply
Voltage, Gain = 100, RL = 1kΩ
42
41
0
2.5
2.0
1.5
1.0
0.5
0
2.5
2.0
1.5
1.0
0.5
0
PHASE
R = 1k
45
F
40
39
38
37
36
35
34
33
32
90
GAIN
R
= 250Ω
135
180
225
F
R = 250Ω
R
= 1k
F
F
R = 5.1k
R
= 5.1k
F
F
V
R
R
= ±15V
= 100Ω
= 3k
S
L
F
0.01
0.1
1.0
10
0
2
4
6
8
10 12 14 16 18
0
2
4
6
8
10 12 14 16 18
FREQUENCY (MHz)
SUPPLY VOLTAGE (±V)
SUPPLY VOLTAGE (±V)
LT1217 • TPC09
LT1217 • TPC07
LT1217 • TPC08
3
LT1217
TYPICAL PERFOR A CE CHARACTERISTICS
U W
Maximum Capacitive Load vs
Feedback Resistor
Total Harmonic Distortion vs
Frequency
2nd and 3rd Harmonic
Distortion vs Frequency
–20
–30
–40
–50
–60
0.1
10000
1000
100
V
= ±15V
R = 400Ω
L
V
= ±15V
= 100Ω
= 2Vpp
A
= 2
S
S
L
V
L
R
V
R
= 1k
R = R = 3kΩ
PEAKING ≤ 5dB
F
G
O
R = 3k
F
A
= 10dB
V
3RD
V
= ±5V
S
V
= ±15V
S
0.01
V
= 7V
RMS
O
2ND
V
= 2V
RMS
O
0.001
10
0.1
1
10
10
100
1000
FREQUENCY (Hz)
10000
100000
1
2
3
4
5
6
7
8
9
10
FREQUENCY (MHz)
FEEDBACK RESISTOR (kΩ)
LT1217 • TPC11
LT1217 • TPC12
LT1217 • TPC10
Input Common Mode Limit vs
Temperature
Output Saturation Voltage vs
Temperature
+
Output Short Circuit Current vs
Temperature
+
V
V
120
110
100
90
–0.5
–1.0
–1.5
–2.0
2.0
–1.0
–2.0
–3.0
3.0
+
V
= +5V TO +18V
R
= ∞
L
±5V ≤ V ≤ ±18V
80
S
70
1.5
2.0
–
60
V
= –5V TO –18V
1.0
1.0
50
0.5
–
–
V
V
40
–50 –25
0
25
50
75 100 125
–50 –25
0
25
50
75 100 125
–50 –25
0
25
50
75 100 125
PACKAGE TEMPERATURE (°C)
PACKAGE TEMPERATURE (°C)
PACKAGE TEMPERATURE (°C)
LT1217 • TPC13
LT1217 • TPC14
LT1217 • TPC15
Spot Noise Voltage and Current vs
Frequency
Power Supply Rejection vs
Frequency
Output Impedance vs
Frequency
100
10
1
70
60
50
40
30
20
10
0
10000
1000
100
SHUTDOWN
(PIN 8 AT GND)
i
n–
POSITIVE
NEGATIVE
e
n
10
1
i
n+
NORMAL
V
= ±15V
= 100Ω
G
S
L
F
R
V
= ±15V
G
S
F
R = R =3k
R = R = 3k
0.1
0.1
0.01
0.1
1
10
100
0.01
0.1
1
10
0.01
0.1
1
10
FREQUENCY (kHz)
FREQUENCY (MHz)
FREQUENCY (MHz)
LT1217 • TPC16
LT1217 • TPC17
LT1217 • TPC18
4
LT1217
U W
TYPICAL PERFOR A CE CHARACTERISTICS
Settling Time to 10mV vs
Output Step
Settling Time to 1mV vs
Output Step
Supply Current vs Supply Voltage
10
8
10
8
1.4
1.2
1.0
0.8
V
= ±15V
G
S
F
T = 125°C
V
= ±15V
G
S
F
R = R = 3k
R = R = 3k
6
4
6
4
INVERTING
NON-INVERTING
T = 25°C
INVERTING
2
2
NON-INVERTING
NON-INVERTING
T = –55°C
0
0
0.6
0.4
0.2
0.0
–2
–2
T = –55°C
NON-INVERTING
T = 25°C, 125°C
–4
–6
–4
–6
SHUTDOWN
PIN 8 AT GND
INVERTING
100 150
–8
–8
INVERTING
300
–10
–10
0
50
200
250
300
0
100
200
400
500
0
2
4
6
8
10 12 14 16 18
SETTLING TIME (ns)
SETTLING TIME (ns)
SUPPLY VOLTAGE (±V)
LT1217 • TPC19
LT1217 • TPC20
LT1217 • TPC21
O U
W
U
PPLICATI
A
S I FOR ATIO
Current Feedback Basics
Feedback Resistor Selection
The small signal bandwidth of the LT1217 is set by the
external feedback resistors and the internal junction ca-
pacitors. As a result, the bandwidth is a function of the
supply voltage, the value of the feedback resistor, the
closed loop gain and load resistor. The characteristic
curves of bandwidth versus supply voltage are done with
a heavy load (100Ω) and a light load (1kΩ) to show the
effect of loading. These graphs also show the family of
curves that result from various values of the feedback
resistor. These curves use a solid line when the response
has less than 0.5dB of peaking and a dashed line when the
response has 0.5dB to 5dB of peaking. The curves stop
where the response has more than 5dB of peaking.
The small signal bandwidth of the LT1217, like all current
feedback amplifiers, isn’t a straight inverse function of the
closed loop gain. This is because the feedback resistors
determine the amount of current driving the amplifier’s
internal compensation capacitor. In fact, the amplifier’s
feedback resistor (RF) from output to inverting input
workswithinternaljunctioncapacitancesoftheLT1217to
set the closed loop bandwidth.
Eventhoughthegainsetresistor(RG)frominvertinginput
to ground works with RF to set the voltage gain just like it
does in a voltage feedback op amp, the closed loop
bandwidthdoesnotchange.Thisisbecausetheequivalent
gain bandwidth product of the current feedback amplifier
issetbytheTheveninequivalentresistanceattheinverting
input and the internal compensation capacitor. By keeping
RF constant and changing the gain with RG, the Thevenin
resistance changes by the same amount as the change in
gain. As a result, the net closed loop bandwidth of the
LT1217 remains the same for various closed loop gains.
At a gain of two, on ±15V supplies with a 3kΩ feedback
resistor, the bandwidth into a light load is 13.5MHz with a
little peaking, but into a heavy load the bandwidth is
10MHzwithnopeaking.Atveryhighclosedloopgains,the
bandwidth is limited by the gain bandwidth product of
about 100MHz. The curves show that the bandwidth at a
closed loop gain of 100 is about 1MHz.
The curve on the first page shows the LT1217 voltage gain
versusfrequencywhiledriving100Ω,forfivegainsettings
from 1 to 100. The feedback resistor is a constant 3k and
the gain resistor is varied from infinity to 30Ω. Second
order effects reduce the bandwidth somewhat at the
higher gain settings.
Capacitance on the Inverting Input
Current feedback amplifiers want resistive feedback from
the output to the inverting input for stable operation. Take
5
LT1217
PPLICATI
O U
W
U
A
S I FOR ATIO
care to minimize the stray capacitance between the output
and the inverting input. Capacitance on the inverting input
to ground will cause peaking in the frequency response
(and overshoot in the transient response), but it does not
degrade the stability of the amplifier. The amount of
capacitance that is necessary to cause peaking is a func-
tion of the closed loop gain taken.
same amount. The advantage of resistive isolation is that
the bandwidth is only reduced when the capacitive load is
present. The disadvantage of resistor isolation is that
resistive loading causes gain errors. Because the DC
accuracy is not degraded with resistive loading, the de-
sired way of driving capacitive loads, such as flash
converters, is to increase the feedback resistor. The Maxi-
mum Capacitive Load versus Feedback Resistor curve
shows the value of feedback resistor and capacitive load
that gives 5dB of peaking. For less peaking, use a larger
feedback resistor.
The higher the gain, the more capacitance is required to
cause peaking. We can add capacitance from the inverting
input to ground to increase the bandwidth in high gain
applications. For example, in this gain of 100 application,
the bandwidth can be increased from 1MHz to 2MHz by
adding a 2200pF capacitor.
Power Supplies
The LT1217 may be operated with single or split supplies
as low as ±4.5V (9V total) to as high as ±18V (36V total).
It is not necessary to use equal value split supplies,
however, the offset voltage will degrade about 350µV per
volt of mismatch. The internal compensation capacitor
decreaseswithincreasingsupplyvoltage.The–3dBBand-
width versus Supply Voltage curves show how this affects
the bandwidth for various feedback resistors. Generally,
the bandwidth at ±5V supplies is about half the value it is
at ±15V supplies for a given feedback resistor.
+
V
IN
LT1217
V
OUT
–
R
F
3k
R
G
C
G
30Ω
LT1229 • TA03
Boosting Bandwidth of High Gain Amplifier with
Capacitance on Inverting Input
The LT1217 is very stable even with minimal supply
bypassing, however, the transient response will suffer if
thesupplyrings.Itisrecommendedforgoodslewrateand
settling time that 4.7µF tantalum capacitors be placed
within 0.5 inches of the supply pins.
45
44
43
C
= 4700pF
G
42
41
40
39
38
37
36
35
Input Range
C
= 2200pF
G
The non-inverting input of the LT1217 looks like a 100MΩ
resistor in parallel with a 3pF capacitor until the common
mode range is exceeded. The input impedance drops
somewhat and the input current rises to about 10µA when
the input comes too close to the supplies. Eventually,
when the input exceeds the supply by one diode drop, the
base collector junction of the input transistor forward
biases and the input current rises dramatically. The input
current should be limited to 10mA when exceeding the
supplies. The amplifier will recover quickly when the input
is returned to its normal common mode range unless the
input was over 500mV beyond the supplies, then it will
take an extra 100ns.
C
= 0
G
100k
1M
FREQUENCY (Hz)
10M
LT1217 • TA04
Capacitive Loads
The LT1217 can be isolated from capacitive loads with a
small resistor (10Ω to 20Ω) or it can drive the capacitive
load directly if the feedback resistor is increased. Both
techniques lower the amplifier’s bandwidth about the
6
LT1217
O U
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U
PPLICATI
A
S I FOR ATIO
Large Signal Response, AV = 2, RF = RG = 3k,
Offset Adjust
Slew Rate 500V/µs
Output offset voltage is equal to the input offset voltage
times the gain plus the inverting input bias current times
the feedback resistor. The LT1217 output offset voltage
can be nulled by pulling approximately 30µA from pin 1 or
5. The easy way to do this is to use a 100kΩ pot between
pin1and5witha430kΩ resistorfromthewipertoground
for 15V supply applications. Use a 110k resistor when
operating on a 5V supply.
Shutdown
Pin 8 activates a shutdown control function. Pulling more
than50µA from pin 8 drops thesupply currentto less than
350µA, and puts the output into a high impedance state.
The easy way to force shutdown is to ground pin 8, using
an open collector (drain) logic stage. An internal resistor
limits current, allowing direct interfacing with no addi-
tional parts. When pin 8 is open, the LT1217 operates
normally.
Large Signal Response, AV = –2, RF = 3k, RG = 1.5k,
Slew Rate 850V/µs
Slew Rate
The slew rate of a current feedback amplifier is not
independent of the amplifier gain configuration the way it
is in a traditional op amp. This is because the input stage
and the output stage both have slew rate limitations.
Invertingamplifiersdonotslewtheinputandaretherefore
limited only by the output stage. High gain, non-inverting
amplifiers are similar. The input stage slew rate of the
LT1217 is about 50V/µs before it becomes non-linear and
isenhancedbythenormallyreversebiasedemittersonthe
inputtransistors. Theoutputslewratedependsonthesize
of the feedback resistors. The output slew rate is about
850V/µs with a 3k feedback resistor and drops propor-
tionally for larger values. The photos show the LT1217
with a 20V peak-to-peak output swing for three different
gain configurations.
Large Signal Response, AV = 10, RF = 3k, RG = 330Ω,
Slew Rate 150V/µs
Settling Time
The characteristic curves show that the LT1217 settles to
within10mVoffinalvalueinlessthan300nsforanyoutput
step up to 10V. Settling to 1mV of final value takes less
than 500ns.
Information furnished by Linear Technology Corporation is believed to be accurate and reliable.
However, no responsibility is assumed for its use. Linear Technology Corporation makes no represen-
tationthattheinterconnectionofitscircuitsasdescribedhereinwillnotinfringeonexistingpatentrights.
7
LT1217
W
W
SI PLIFIED SCHE ATIC
7
90k
1
5
BIAS
60k
8
3
6
2
BIAS
4
LT1217 • TA08
U
PACKAGE DESCRIPTIO
Dimensions in inches (millimeters) unless otherwise noted.
0.300 – 0.320
(7.620 – 8.128)
0.130 ± 0.005
(3.302 ± 0.127)
0.400
(10.160)
MAX
0.045 – 0.065
(1.143 – 1.651)
0.065
N8 Package
(1.651)
TYP
8
1
7
6
8-Lead Plastic DIP
5
4
0.009 - 0.015
(0.229 - 0.381)
TJ MAX
θJA
0.250 ± 0.010
(6.350 ± 0.254)
0.125
(3.175)
MIN
0.020
(0.508)
MIN
150°C
100°C/W
+0.025
–0.015
0.045 ± 0.015
(1.143 ± 0.381)
0.325
+0.635
8.255
(
)
3
2
–0.381
0.100 ± 0.010
0.018 ± 0.003
(0.457 ± 0.076)
(2.540 ± 0.254)
N8 1291
0.189 – 0.197
(4.801 – 5.004)
7
5
8
6
0.010 – 0.020
(0.254 – 0.508)
× 45°
S8 Package
8-Lead Plastic SOIC
0.053 – 0.069
(1.346 – 1.753)
0.004 – 0.010
(0.102 – 0.254)
0.008 – 0.010
(0.203 – 0.254)
0.228 – 0.244
(5.791 – 6.198)
0.150 – 0.157
(3.810 – 3.988)
TJ MAX
θJA
0.016 – 0.050
0.406 – 1.270
0.050
(1.270)
BSC
150°C
150°C/W
0.014 – 0.019
(0.356 – 0.483)
0°– 8° TYP
1
2
3
4
S8 1291
BA/GP 0192 10K REV 0
Linear Technology Corporation
1630 McCarthy Blvd., Milpitas, CA 95035-7487
8
●
●
LINEAR TECHNOLOGY CORPORATION 1992
(408) 432-1900 FAX: (408) 434-0507 TELEX: 499-3977
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