TMK325BJ226MM- [INTERSIL]
Dual 15A/Single 30A Step-Down Power Module; 双路15A / 30A单降压型电源模块型号: | TMK325BJ226MM- |
厂家: | Intersil |
描述: | Dual 15A/Single 30A Step-Down Power Module |
文件: | 总28页 (文件大小:1136K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
Dual 15A/Single 30A Step-Down Power Module
ISL8225M
Features
• Fully-encapsulated dual step-down switching power supply
• Up to 100W output from a 17mm square PCB footprint
• Dual 15A or single 30A output
The ISL8225M is a fully-encapsulated step-down switching
power supply that can deliver up to 100W output power from a
small 17mm square PCB footprint. The two 15A outputs may
be used independently or combined to deliver a single 30A
output. Designing a high-performance board-mounted power
supply has never been simpler -- only a few external
components are needed to create a very dense and reliable
power solution.
• Up to 95% conversion efficiency
• 4.5V to 20V input voltage range
• 0.6V to 6V output voltage range
Automatic current sharing and phase interleaving allow up to
six modules to be paralleled for 180A output capability. 1.5%
output voltage accuracy, differential remote voltage sensing
and fast transient response create a very high-performance
power system. Built-in output over-voltage, over-current and
over-temperature protection enhance system reliability.
• 1.5% output voltage accuracy with differential remote
sensing
• Up to six modules may be paralleled to support 180A output
current
• Output over-voltage, over-current and over-temperature
protection
The ISL8225M is available in a thermally-enhanced QFN
package. Excellent efficiency and low thermal resistance
permit full power operation without heat sinks or fans. In
addition, the QFN package with external leads permits easy
probing and visual solder inspection.
• Full power operation without heat sinks or fans
• QFN package with exposed leads permits easy probing and
visual solder inspection
Related Resources
• See AN1789 “ISL8225MEVAL2Z 6-Phase, 90A Evaluation
Board Setup Procedure”
Applications
• Computing, networking and telecom infrastructure
equipment
• See AN1790 “ISL8225MEVAL3Z 30A, Single Output
Evaluation Board Setup Procedure”
• Industrial and medical equipment
• General purpose point-of-load (POL) power
• See AN1793, “ISL8225MEVAL4Z Dual 15A/Optional 30A
Cascadable Evaluation Board”
• See ISL8225M 110A Thermal Performance Video
4.5V TO 20V
4x22µF
1.2V@30A
V
V
VIN1
VIN2
VOUT1
VOUT2
IN
OUT
1kΩ
VSEN1+
R
SET
1kΩ
EN/FF1
EN/FF2
VSEN2-
5x100µF
7.5mm
OFF ON
VSEN1-
VMON1
VMON2
COMP1
COMP2
ISL8225M
VCC
4.7µF
470pF
NOTE: ALL PINS NOT SHOWN ARE FLOATING.
FIGURE 1. COMPLETE 30A STEP-DOWN POWER SUPPLY
FIGURE 2. SMALL FOOTPRINT WITH HIGH POWER DENSITY
January 31, 2013
FN7822.1
CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures.
1-888-INTERSIL or 1-888-468-3774 | Copyright Intersil Americas LLC 2012, 2013. All Rights Reserved
Intersil (and design) is a trademark owned by Intersil Corporation or one of its subsidiaries.
All other trademarks mentioned are the property of their respective owners.
1
ISL8225M
Pinout Internal Circuit
VCC
7
FILTER
2.2µF
VIN1
14
15
LDO
SOFT-START
AND FAULT
LOGIC
EN/FF1
Q1
Q2
12 PHASE1
UGATE1
24
PGOOD
L1
GATE
DRIVER
23
VOUT1
LGATE1
0.32µH
17
19
CLKOUT
ISHARE
ISEN1B
ISEN1A
CURRENT
SENSING/
SHARING
13
PGND
10kΩ
VSEN1+
VSEN1-
22
21
+
DIFF
AMP1
MODE
SYNC
3
5
-
18 VMON1
ZCOMP1
ZCOMP2
-
ERROR
AMP1
20
COMP1
+
INTERNAL
REFERENCE
8
VIN2
SOFT-START
AND FAULT
LOGIC
16
EN/FF2
Q3
10 PHASE2
25 VOUT2
UGATE2
LGATE2
L2
GATE
DRIVER
0.32µH
Q4
ISEN2B
ISEN2A
CURRENT
SENSING/
SHARING
9
PGND
26
1
VSEN2+
VSEN2-
VMON2
+
DIFF
SGND
6
AMP2
-
4
ZCOMP3
7.5kΩ
MODE
ZCOMP4
-
ERROR
COMP2
2
AMP2
+
INTERNAL
REFERENCE
FN7822.1
January 31, 2013
2
ISL8225M
Ordering Information
PART NUMBER
(Notes 2, 3)
PART
MARKING
TEMP. RANGE (°C)
PACKAGE
(Pb-Free)
PKG.
DWG. #
(Note 4)
ISL8225MIRZ
ISL8225M
ISL8225M
-40 to +125
-40 to +125
26 Ld QFN
L26.17x17
L26.17x17
ISL8225MIRZ-T
(Note 1)
26 Ld QFN
(Tape & Reel)
NOTES:
1. Please refer to TB347 for details on reel specifications.
2. These products do contain Pb but they are RoHs compliant by EU exemption 5 (Pb in glass of cathode ray tubes, electronic components, and
fluorescent tubes).
3. For Moisture Sensitivity Level (MSL), please see device information page for ISL8225M. For more information on MSL, please see tech brief TB363
4. The ISL8225M is guaranteed over the full -40°C to +125°C internal junction temperature range. Note that the allowed ambient temperature
consistent with these specifications is determined by specific operating conditions, including board layout, cooling scheme and other environmental
factors.
FN7822.1
January 31, 2013
3
ISL8225M
Pin Configuration
ISL8225M
(26 LD QFN)
TOP VIEW
PIN 1
9
8
7
6
5
4
3
2
1
VSEN2-
26
VSEN2+
PHASE2
10
25
VOUT2
24
23
N/C
PGOOD
VOUT1
11
12
PHASE1
22
21
VSEN1+
VSEN1-
13
14
15 16 17 18
19 20
FN7822.1
January 31, 2013
4
ISL8225M
Pin Descriptions
PIN
PIN
NUMBER
NAME
TYPE
I
PIN DESCRIPTION
21, 1 VSEN1-, VSEN2-
Output voltage negative feedback. Negative input of the differential remote sense for the regulator. Connect to the
negative rail or ground of the load/processor, as shown in Figure 19. The negative feedback pins can be used to
program the module operation conditions. See Table 3 and Table 5 for details.
20, 2 COMP1, COMP2 I/O Error amplifier outputs. Typically floating for dual-output use. For parallel use, a 470pF~1nF capacitor is recommended
on the COMP pins of each SLAVE phase to eliminate the coupling noise. All COMP pins of SLAVE phases need to tie to
MASTER phase COMP1 pin (first phase). Internal compensation networks are implemented for working in the full range
of I/O conditions.
3
MODE
I
Mode setting. Typically floating for dual-output use; tie to SGND for parallel use. See Table 3 and Table 5 for details.
When VSEN2- is pulled within 700mV of VCC, the 2nd channel’s remote sensing amplifier is disabled. The MODE pin,
as well as the VSEN2+ pin, determine relative phase-shift between the two channels and the CLKOUT signal output.
18, 4 VMON1, VMON2 I/O Remote sensing amplifier outputs. These pins are connected internally to OV/UV/PGOOD comparators, so they can’t
be floated when the module works in multi-phase operation. When VSEN1-, VSEN2- are pulled within 700mV of VCC,
the corresponding remote sensing amplifier is disabled; the output (VMON pin) is in high impedance. In this event, the
VMON pins can be used as an additional monitor of the output voltage, with a resistor divider to protect the system
against single point of failure. The default setting voltage is 0.6V. See Table 3 for details.
5
SYNC
I
Signal synchronization. An optional external resistor (R
) connected from this pin to SGND increases oscillator
SYNC
switching frequency (Figure 31 and Table 1). The internal default frequency is 500kHz with this pin floating. Also, the
internal oscillator can lock to an external frequency source or the CLKOUT signal from another ISL8225M. Input voltage
range for external source: 3V to 5V square wave. No capacitor is recommended on this pin.
6
7
SGND
VCC
PWR Control signal ground. Connect to PGND under the module in the quiet inner layer. Make sure to have the single location
for the connection between SGND and PGND to avoid noise coupling. See “Layout Guide” on page 23.
PWR 5V internal linear regulator output. Voltage range: 3V to 5.6V. The decoupling ceramic capacitor for the VCC pin is
recommended to be 4.7µF.
14, 8
VIN1, VIN2
PGND
PWR Power inputs. Input voltage range: 4.5V to 20V. Tie directly to the input rail. VIN1 provides power to the internal linear
drive circuitry. When the input is 4.5V to 5.5V, VIN should be tied directly to VCC.
9, 13
PWR Power ground. Power ground pins for both input and output returns.
12, 10
PHASE1,
PHASE2
PWR Phase node. Use for monitoring switching frequency. Phase pins should be floating or used for snubber connections.To
achieve better thermal performance, the phase planes can also be used for heat removal with thermal vias connected
to large inner layers. See “Layout Guide” on page 23.
11
NC
-
Non-connection pin. This pin is floating with no connection inside.
15, 16
EN/FF1,
EN/FF2
I/O Enable and feed-forward control. Tie a resistor divider to VIN or use the system enable signal for this pin. The voltage
turn-on threshold is 0.8V. With a voltage lower than the threshold, the corresponding channel can be disabled
independently. By connecting to VIN with a resistor divider, the input voltage can be monitored for UVLO (under-voltage
lockout) function. The voltage on each EN/FF pin is also used to adjust the internal control loop gain independently to
realize the feed-forward function. Please set the EN/FF between 1.25V to 5V. A 1nF capacitor is recommended on each
EN/FF pin. Please see Table 1 to select resistor divider and application details in “EN/FF Turn ON/OFF” on page 19.
17
19
CLKOUT
ISHARE
I/O Clock out. Provide the clock signal for the input synchronization signal of other ISL8225Ms. Typically tied to VCC for
dual-output use with 180° phase-shift. See Table 3 and Table 5 when using more than one ISL8225M. When the
module is in dual-output mode, the clock-out signal is disabled. By programming the voltage level of this CLKOUT pin,
the module can work for DDR/tracking or as two independent outputs with selectable phase-shift. See Table 6.
O
Current sharing control. Tie all ISHARE pins together when multiple modules are configured for current sharing and
share a common current output. The ISHARE voltage represents the average current of all active and connected
channels. A 470pF capacitor is recommended for each ISHARE pin for multiple phase applications. Typically, the
ISHARE pin should be floating for dual-output or single module application.
22, 26
VSEN1+,
VSEN2+
I
Output voltage positive feedback. Positive inputs of differential remote sense for the regulator. A resistor divider can
be connected to this pin to program the output voltage. It is recommended to put the resistor divider close to the
module and connect the kelvin sensing traces of VOUT and VSEN- to the sensing points of the load/processor; see
Figure 19. The VSEN2+ pin can be used to program the module operation conditions. See Table 3 and Table 5 for
details.
23, 25 VOUT1, VOUT2 PWR Power Output. Apply output load between these pins and PGND pins. Output voltage range: 0.6V to 6V.
24
PGOOD
O
Power good. Provide open-drain power-good signal when the output is within 9% of the nominal output regulation point
with 4% hysteresis (13%/9%) and soft-start complete. PGOOD monitors the outputs (VMON) of the internal differential
amplifiers.
FN7822.1
January 31, 2013
5
ISL8225M
Absolute Maximum Ratings
Thermal Information
Input Voltage, V . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . -0.3V to +25V
Driver Bias Voltage, V . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . -0.3V to +6.5V
CC
Thermal Resistance (Typical)
QFN Package (Notes 5, 6) . . . . . . . . . . . . . .
θ
(°C/W)
10.0
θ
(°C/W)
0.9
IN
JA
JC
Phase Voltage, V
. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . -0.3V to +30V
Maximum Storage Temperature Range . . . . . . . . . . . . . .-55°C to +150°C
Pb-free Reflow Profile . . . . . . . . . . . . . . . . . . . . . . . . . . . . Refer to Figure 41
PHASE
Input, Output or I/O Control Voltage . . . . . . . . . . . . . . . -0.3V to V + 0.3V
CC
ESD Rating
Human Body Model (Tested per JESD22-A114E). . . . . . . . . . . . . . . . 2kV
Machine Model (Tested per JESD22-A115-A). . . . . . . . . . . . . . . . . 200V
Charge Device Model (Tested per JESD22-C101C). . . . . . . . . . . . . . . 1kV
Latch-up (Tested per JESD-78B; Class 2, Level A) . . . . . . . . . . . . . . 100mA
Recommended Operating Conditions
Input Voltage, V
and V . . . . . . . . . . . . . . . . . . . . . . . . . . . 4.5V to 20.0V
IN1
IN2
Output Voltage, V
and V
. . . . . . . . . . . . . . . . . . . . . . . 0.6V to 6.0V
Junction Temperature Range . . . . . . . . . . . . . . . . . . . . . . .-40°C to +125°C
OUT1
OUT2
CAUTION: Do not operate at or near the maximum ratings listed for extended periods of time. Exposure to such conditions may adversely impact product
reliability and result in failures not covered by warranty.
NOTES:
5. θ is measured in free air with the component mounted on a high effective thermal conductivity test board with “direct attach” features. See Tech
JA
Brief TB379.
6. For θ , the “case temp” location is the center of the phase exposed metal pad on the package underside.
JC
Electrical Specifications
T
= +25°C, V = 12V, unless otherwise noted. Boldface limits apply over the internal junction temperature
IN
A
range, -40°C to +125°C (Note 4).
MIN
TYP
MAX
PARAMETER
SYMBOL
TEST CONDITIONS
(Note 7) (Note 8) (Note 7) UNITS
VCC SUPPLY CURRENT
Nominal Supply V Current
IN
I
V
V
V
V
V
V
V
= 20V; No Load; EN1 = EN2 = high
131
72
mA
mA
mA
mA
mA
mA
mA
Q_VIN
IN
= 20V; No Load; EN1 = high, EN2 = low
= 20V; No Load; EN1 = 0, EN2 = high
= 12V; No Load; EN1 = high, EN2 = high
IN1
IN2
IN1
71
134
136
73
= 4.5V; No Load; EN1 = EN2 = high
IN
= 4.5V; No Load; EN1 = high, EN2 = low
= 4.5V; No Load; EN1 = 0, EN2 = high
IN1
IN2
70
INTERNAL LINEAR REGULATOR (Note 9)
Maximum Current
I
V
= 4V to 5.6V
250
1
mA
Ω
PVCC
CC
Saturated Equivalent Impedance
VCC Voltage Level
R
P-Channel MOSFET (V = 5V)
IN
LDO
VCC
I
= 0mA
5.15
5.4
5.95
V
VCC
POWER-ON RESET (Note 9)
Rising VCC Threshold
0°C to +75°C
2.85
2.85
2.65
384
2.97
3.05
2.75
V
-40°C to +85°C
V
V
Falling VCC Threshold
System Soft-start Delay
t
After PLL and V PORs, and EN above their
CC
Cycles
SS_DLY
thresholds
ENABLE (Note 9)
Turn-On Threshold Voltage
Hysteresis Sink Current
Under-voltage Lockout Hysteresis
0.75
23
0.8
30
0.86
35
V
µA
V
I
EN_HYS
V
V
= 10.6V; V = 9V, R = 53.6kΩ,
EN_FTH UP
1.6
EN_HYS
EN_RTH
R
= 5.23kΩ
DOWN
Sink Current
I
V
= 1V
15.4
mA
EN_SINK
ENFF
Sink Impedance
OSCILLATOR
R
I
= 5mA, V = 1V
ENFF
64
Ω
EN_SINK
EN_SINK
Oscillator Frequency
f
SYNC pin is open
510
kHz
OSC
FN7822.1
January 31, 2013
6
ISL8225M
Electrical Specifications
T
= +25°C, V = 12V, unless otherwise noted. Boldface limits apply over the internal junction temperature
IN
A
range, -40°C to +125°C (Note 4). (Continued)
MIN
TYP
MAX
PARAMETER
SYMBOL
TEST CONDITIONS
= 5V; -40°C < T < +85°C
(Note 7) (Note 8) (Note 7) UNITS
Total Variation (Note 9)
V
-9
+9
1500
90
%
CC
A
FREQUENCY SYNCHRONIZATION AND PHASE LOCK LOOP (Note 9)
Synchronization Frequency
PLL Locking Time
V
= 5V
150
10
kHz
µs
%
CC
CC
V
= 5.4V, f
= 500kHz
130
SW
Input Signal Duty Cycle Range
PWM (Note 9)
Minimum PWM OFF Time
Current Sampling Blanking Time
OUTPUT CHARACTERISTICS
Output Continuous Current Range
t
310
345
175
410
ns
ns
MIN_OFF
t
BLANKING
I
V
V
V
= 12V, V
= 12V, V
= 12V, V
= 1.5V
= 1.5V
0
0
0
15
15
30
A
A
A
OUT(DC)
IN
IN
IN
OUT1
OUT2
= 1.5V, in Parallel mode
OUT
Line Regulation Accuracy
ΔV
/ΔV
V
= 4.5V to 20V
OUT
IN IN
V
= 1.5V, I
= 1.5V, I
= 0A
= 0A
0.0065
0.0065
%
%
OUT1
OUT2
OUT1
OUT2
V
V
= 4.5V to 20V
IN
V
= 1.5V, I
= 1.5V, I
= 15A
= 15A
0.01
0.01
%
%
OUT1
OUT2
OUT1
OUT2
V
Load Regulation Accuracy
Output Ripple Voltage
ΔV
/V
V
= 12V, 5x22µF, 2x4.7µF ceramic capacitor and
OUT OUT IN
1x330µF POSCAP
I
I
= 0A to 15A, V
= 0A to 15A, V
= 1.5V
= 1.5V
1
1
%
%
OUT1
OUT2
OUT1
OUT2
ΔV
OUT
V
= 12V, 3x100µF ceramic capacitor and
IN
1x330µF POSCAP
I
I
I
I
= 0A, V
= 0A, V
= 1.5V
= 1.5V
11
11
14
14
mV
OUT1
OUT2
OUT1
OUT2
OUT1
P-P
P-P
P-P
P-P
mV
mV
mV
OUT2
= 15A, V
= 1.5V
= 1.5V
OUT1
OUT2
= 15A, V
DYNAMIC CHARACTERISTICS
Voltage Change for Positive Load Step
ΔV
Current slew rate = 2.5A/µs
= 12V, V = 1.5V, 2x47µF ceramic capacitor
OUT-DP
V
IN
OUT
and 1x330µF POSCAP
I
I
= 0A to 7.5A
= 0A to 7.5A
75
75
mV
mV
OUT1
OUT2
P-P
P-P
Voltage Change for Negative Load Step
ΔV
Current slew rate = 2.5A/µs
= 12V, V = 1.5V, 2x47µF ceramic capacitor
OUT-DN
V
IN
OUT
and 1x330µF POSCAP
I
I
= 7.5A to 0A
= 7.5A to 0A
70
70
mV
mV
OUT1
OUT2
P-P
P-P
REFERENCE (Note 9)
Reference Voltage (Include Error and
Differential Amplifier Offsets)
V
T
= -40°C to +85°C
0.6
V
REF1
A
-0.7
0.7
%
FN7822.1
January 31, 2013
7
ISL8225M
Electrical Specifications
T
= +25°C, V = 12V, unless otherwise noted. Boldface limits apply over the internal junction temperature
IN
A
range, -40°C to +125°C (Note 4). (Continued)
MIN
TYP
MAX
PARAMETER
SYMBOL
TEST CONDITIONS
= -40°C to +85°C
A
(Note 7) (Note 8) (Note 7) UNITS
Reference Voltage (Include Error and
Differential Amplifier Offsets)
V
T
0.6
V
REF2
-0.75
0.2
0.95
2.5
%
DIFFERENTIAL AMPLIFIER (Note 9)
DC Gain
UG_DA
Unity gain amplifier
0
5
dB
MHz
µA
Unity Gain Bandwidth
VSEN+ Pin Sourcing Current
UGBW_DA
I
1
VSEN+
I
VSEN1- Source Current for Current Sharing when
parallel multiple modules, each of which has its
own voltage loop
350
µA
VSEN1-
Maximum Source Current for Current Sharing
Input Impedance
R
V
/I
, V
= 0.6V
-600
kΩ
VSEN+_to
_VSEN-
VSEN+ VSEN+ VSEN+
Output Voltage Swing
0
V
V
- 1.8
V
V
V
CC
Input Common Mode Range
Disable Threshold
-0.2
- 1.8
CC
V
V
= tri-state
V
- 0.4
VSEN-
MON1,2
IN
CC
OVER-CURRENT PROTECTION (Note 9)
Channel Over-current Limit
I
I
V
V
V
= 12V, V
= 1.5V, R
= Open
= Open
20
20
A
A
V
limit1
limit2
OUT1
SYNC
= 12V, V
= 1.5V, R
IN
OUT2
SYNC
Share Pin OC Threshold
V
= 5V
1.16
1.20
1.22
OC_SET
CC
(comparator offset included)
CURRENT SHARE
Current Share Accuracy
ΔI/IOUT
V
= 12V, V
= 1.5V
= 30A, VSEN2- = high
±10
%
IN
OUT
I
OUT
POWER-GOOD MONITOR (Note 9)
Under-voltage Falling Trip Point
Under-voltage Rising Hysteresis
Over-voltage Rising Trip Point
Over-voltage Falling Hysteresis
PGOOD Low Output Voltage
V
Percentage below reference point
Percentage above UV trip point
Percentage above reference point
Percentage below OV trip point
-15
11
-13
4
-11
15
%
%
UVF
V
V
UVR_HYS
V
13
4
%
OVR
%
OVF_HYS
I
I
= 2mA
= 2mA
< 0.8V
0.35
70
V
PGOOD
Sinking Impedance
Ω
PGOOD
Maximum Sinking Current
V
10
mA
PGOOD
OVER-VOLTAGE PROTECTION (Note 9)
OV Latching-up Trip Point
EN/FF = UGATE = LATCH Low, LGATE = High
EN = Low, UGATE = Low, LGATE = High
EN = Low/HIGH, UGATE = Low, LGATE = Low
118
120
113
87
122
%
%
%
OV Non-Latching-up Trip Point
LGATE Release Trip Point
OVER-TEMPERATURE PROTECTION (Note 9)
Over-Temperature Trip (Controller Junction
Temperature)
150
125
°C
°C
Over-Temperature Release Threshold
(Controller Junction Temperature)
NOTES:
7. Compliance to datasheet limits is assured by one or more methods: production test, characterization and/or design.
8. Parameters with TYP limits are not production tested, unless otherwise specified.
9. Parameters are 100% tested for internal IC prior to module assembly.
FN7822.1
January 31, 2013
8
ISL8225M
Typical Performance Characteristics
Efficiency Performance
T = +25°C, if not specified, as shown in Figure 18 with 2nd phase disabled. The efficiency equation is
A
as follows:
P
(V
xI
)
Output Power
Input Power
OUT
OUT OUT
-----------------------------------------
---------------
--------------------------------------
=
Efficiency =
=
P
(V xI
)
IN
IN IN
100
95
90
85
80
75
70
65
60
55
50
100
95
3.3V
1.8V
2.5V AT 500kHz
3.3V AT 650kHz
1.2V AT 500kHz
2.5V
1.5V
5V AT 850kHz
90
85
1V
1.2V
80
1.5V AT 500kHz
1.8V AT 500kHz
75
70
65
60
55
50
1V AT 500kHz
0
2
4
6
8
10
12
14
16
0
2
4
6
8
10
12
14
16
LOAD CURRENT (A)
LOAD CURRENT (A)
FIGURE 3. EFFICIENCY vs LOAD CURRENT (5V AT 500kHz)
IN
FIGURE 4. EFFICIENCY vs LOAD CURRENT (12V )
IN
100
100
95
90
85
80
75
70
2.5V
OUT
1.8V
2.5V AT 500kHz
95
90
85
80
75
70
65
60
55
50
OUT
3.3V AT 650kHz
5V AT 900kHz
1.5V
OUT
1.2V
OUT
1.8V AT 500kHz
1V
OUT
1.5V AT 500kHz
1.2V AT 500kHz
1V AT 500kHz
0
2
4
6
8
10
12
14
16
0
5
10
15
20
25
30
LOAD CURRENT (A)
LOAD CURRENT (A)
FIGURE 5. EFFICIENCY vs LOAD CURRENT (20V
)
FIGURE 6. EFFICIENCY vs LOAD CURRENT (PARALLEL SINGLE
OUTPUT, AS SHOWN IN FIGURE 19 AT 5V /500kHz)
IN
IN
95
1.8V
1.5V
OUT
2.5V
OUT
90
85
80
75
70
65
60
OUT
1.2V
OUT
1V
OUT
0
5
10
15
20
25
30
LOAD CURRENT (A)
FIGURE 7. EFFICIENCY vs LOAD CURRENT (PARALLEL SINGLE OUTPUT, AS SHOWN IN FIGURE 19 AT 12V /500kHz
IN
FN7822.1
January 31, 2013
9
ISL8225M
Typical Performance Characteristics(Continued)
Transient Response Performance
V
= 12V, COUT = 1x10µF and 3x100µF ceramic capacitors, I
= 0A to 7.5A, current
OUT
IN
slew rate = 2.5A/µs. T = +25°C, if not specified, as shown in Figure 18 with 2nd phase disabled.
A
50mV/DIV
50mV/DIV
2A/DIV
2A/DIV
200µs/DIV
200µs/DIV
FIGURE 8. 1V
FIGURE 10. 1.5V
FIGURE 12. 2.5V
TRANSIENT RESPONSE
FIGURE 9. 1.2V
TRANSIENT RESPONSE
OUT
OUT
50mV/DIV
50mV/DIV
2A/DIV
2A/DIV
200µs/DIV
200µs/DIV
TRANSIENT RESPONSE
FIGURE 11. 1.8V
OUT
TRANSIENT RESPONSE
OUT
50mV/DIV
100mV/DIV
2A/DIV
2A/DIV
200µs/DIV
200µs/DIV
200uS/DIV
TRANSIENT RESPONSE
FIGURE 13. 3.3V TRANSIENT RESPONSE
OUT
OUT
FN7822.1
January 31, 2013
10
ISL8225M
Typical Performance Characteristics(Continued)
Start-up and Short Circuit Performance
V
= 12V, V
= 1.5V, CIN = 1x 180µF, 2x10µF/Ceramic, COUT = 2x47µF and
IN
OUT
1x330µF POSCAP. T = +25°C, if not specified, as shown in Figure 18 with 2nd phase disabled.
A
V
OUT
V
out
OUT
0.5V/DIV
0.5V/DIV
I
in
IN
I
N
0.1A/DIV
0.1A/DIV
1ms/DIV
1ms/DIV
FIGURE 14. START-UP AT 0A
FIGURE 15. START-UP AT 15A
V
OUT
V
out
OUT
0.5V/DIV
0.5V/DIV
I
I
IN
in
IN
0.2A/DIV
V
I
0.5A/DIV
100µs/DIV
100µs/DIV
FIGURE 16. SHORT CIRCUIT AT 0A
FIGURE 17. SHORT CIRCUIT AT 15A
FN7822.1
January 31, 2013
11
ISL8225M
Typical Application Circuits
4.5V TO 20V
14
1.2V@15A
VOUT1
23
22
21
25
26
1
VIN
VIN1
VOUT1
CFF
+
(OPTIONAL)
+
CIN1
330µF
CIN2
4x22µF
COUT2
330µF
8
15
16
7
VIN2
VSEN1+
VSEN1-
VOUT2
VSEN2+
VSEN2-
VMON1
R2*
1kΩ
COUT1
2x47µF
R1*
1kΩ
EN/FF1
EN/FF2
VCC
R5*
1.5V@15A
VOUT2
CFF
(OPTIONAL)
+
COUT4
330µF
COUT3
2x47µF
R4*
665Ω
R3*
1kΩ
R6*
17
3
CLKOUT
MODE
ISHARE
SYNC
C1
4.7µF
ISL8225M
18
4
*SEE TABLE 4 ON PAGE 19, RESISTORS
SET ON VSEN+ AND VSEN- PINS.
19
5
*SEE TABLE 1 ON PAGE 17 FOR R5/R6
VALUES.
VMON2
12
10
24
PHASE1
20
2
COMP1
COMP2
PHASE2
PGOOD
6
9
SEE “LAYOUT GUIDE” ON PAGE 23 FOR SHORTING SGND TO PGND
FIGURE 18. DUAL OUTPUTS FOR 1.2V/15A AND 1.5V/15A
4.5V TO 20V
+
1.5V@30A
14
8
23
22
21
25
26
1
VIN
VOUT
VIN1
VOUT1
VSEN1+
VSEN1-
VOUT2
R1
CIN1
330µF
CIN2
VIN2
4x22µF
1kΩ
COUT
5x100µF
R2
LOAD
665Ω
15
16
7
EN/FF1
EN/FF2
VCC
R3*
KELVIN REMOTE SENSING LINES
VSEN2+
VSEN2-
VMON1
VMON2
PHASE1
PHASE2
PGOOD
VCC
17
3
R4*
CLKOUT
MODE
ISHARE
SYNC
ISL8225M
C1
4.7µF
18
4
19
5
*SEE TABLE 1 ON PAGE 17 FOR R3/R4
VALUES.
2200pF
2Ω
12
SIZE:1210
2Ω
20
2
10
24
COMP1
COMP2
SIZE:1210
2200pF
C2
OPTIONAL SNUBBER FOR NOISE
ATTENUATION. SEE FIGURE 32,
470pF
6
9
“RECOMMENDED LAYOUT,” ON PAGE 23.
SEE “LAYOUT GUIDE” ON PAGE 23 FOR SHORTING SGND TO PGND
FIGURE 19. PARALLEL USE FOR SINGLE 1.5V/30A OUTPUT
FN7822.1
January 31, 2013
12
ISL8225M
Typical Application Circuits(Continued)
2.5V
4.5V TO 20V
14
8
23
22
21
25
26
1
VDDQ
VIN
VIN1
VOUT1
VSEN1+
VSEN1-
VOUT2
+
R1
CIN2
4x22µF
CIN1
330µF
VIN2
1kΩ
R2
COUT1
3x100µF
316Ω
15
16
7
R5*
EN/FF1
EN/FF2
VCC
1.25V VDDQ/2
VTT
*SEE TABLE 1 ON PAGE 17 FOR
R5/R6 VALUES.
R3
1kΩ
VSEN2+
VSEN2-
VMON1
VMON2
PHASE1
PHASE2
PGOOD
R6*
R4
931Ω
COUT2
3x100µF
C1
4.7µF
17
3
CLKOUT
MODE
ISHARE
SYNC
ISL8225M
18
4
VDDQ
19
5
R7
12
10
24
1kΩ
20
2
COMP1
COMP2
R8
C2
1nF
324Ω
6
9
*SET THE CLKOUT VOLTAGE CLOSE TO 0.61V.
SEE DETAILS IN “FUNCTIONAL DESCRIPTION” ON PAGE 20
FIGURE 20. DDR/TRACKING USE
3.3V@10A
VOUT1
8V TO 20V
+
14
8
23
22
21
25
26
1
VIN
VIN1
VOUT1
VSEN1+
VSEN1-
VOUT2
R1
1kΩ
CIN1
CIN2
VIN2
330µF
4x22µF
COUT1
3x100µF
R2
221Ω
R5
15
16
7
EN/FF1
EN/FF2
VCC
7.15kΩ
5V@10A
VOUT2
R3
1kΩ
VSEN2+
VSEN2-
VMON1
VMON2
PHASE1
PHASE2
PGOOD
R4
137Ω
COUT2
3x100µF
R6
2.05kΩ
17
3
C1
4.7µF
CLKOUT
MODE
ISHARE
SYNC
ISL8225M
18
4
*SEE FIGURE 25, “RECOMMENDED
FREQUENCY VS VIN AT VOUT,” ON
PAGE 19 FOR THE FREQUENCY SETTING
FOR I/O CONDITIONS.
19
5
12
10
24
20
2
COMP1
COMP2
R7
88.7kΩ
6
9
*SEE FIGURE 31, “R
VS SWITCHING
SYNC
FREQUENCY,” ON PAGE 22 TO SELECT R7 FOR THE
DESIRED FREQUENCY OPERATION.
FIGURE 21. HIGH OUTPUT VOLTAGE APPLICATION WITH THE FREQUENCY SET AT 900kHz
FN7822.1
January 31, 2013
13
ISL8225M
Typical Application Circuits(Continued)
1.5V/60A
4.5V TO 20V
MASTER PHASE
VIN
VOUT1
VIN1
VIN2
VOUT1
R1
+
CIN1
2x470µF
CIN2
VSEN1+
4x22µF
R2
665Ω
1kΩ
COUT1
4x100µF
R4*
EN/FF1
VSEN1-
VOUT2
SLAVE
VCC1
EN/FF2
VCC
VCC1
*SEE TABLE 1 ON
PAGE 17 FOR R3/R4
VALUES.
R3*
VSEN2+
C1
4.7µF
CLKOUT
VSEN2-
ISL8225M
MODE
VMON1
VMON2
VCC
ISHARE
R8
1kΩ
SYNC
PHASE1
R5
3.3kΩ
COMP1
COMP2
PHASE2
PGOOD
PGOOD
C3
470pF
SLAVE
VIN1
VOUT1
VIN2
VSEN1+
CIN2
4x22µF
COUT2
4x100µF
VCC2
EN/FF1
EN/FF2
VSEN1-
VOUT2
SLAVE
VCC2
VCC
VSEN2+
CLKOUT
MODE
VSEN2-
VMON1
C2
4.7µF
ISL8225M
R6
1kΩ
R7
665Ω
ISHARE
VMON2
R9
1kΩ
SYNC
PHASE1
PHASE2
COMP1
COMP2
PGOOD
C4
470pF
C5
470pF
FIGURE 22. 4-PHASE PARALLELED AT 1.5V/60A WITH 90° INTERLEAVING
FN7822.1
January 31, 2013
14
ISL8225M
Typical Application Circuits(Continued)
4.5V TO 20V
1.5V/40A
14
8
23 MASTER PHASE
VOUT1
VIN
VIN1
VOUT1
VSEN1+
VSEN1-
VOUT2
+
R1
22
CIN1
2x470µF
VIN2
4x22µF
1kΩ
316Ω
R2
COUT1
4x100µF
R4*
15
16
7
21
25
26
1
EN/FF1
EN/FF2
VCC
*SEE TABLE 1
ON PAGE 17
FOR R3/R4
VALUES.
SLAVE
VCC1
VCC1
VSEN2+
VSEN2-
VMON1
VMON2
PHASE1
PHASE2
PGOOD
R3*
C1
4.7µF
17
3
CLKOUT
MODE
ISHARE
SYNC
ISL8225M
VCC
18
4
VCC1
19
5
12
10
24
R6
1kΩ
R5
3.3kΩ
20
2
COMP1
COMP2
R7
100kΩ
PGOOD
6
9
C2
470pF
14
23
22
21
25
26
1
SLAVE
VIN1
VOUT1
VSEN1+
VSEN1-
VOUT2
COUT2
2x100µF
8
15
16
VIN2
VCC2
CIN2
EN/FF1
EN/FF2
VCC
4x22µF
5V/10A
VOUT2
VCC2
7
R8
VSEN2+
VSEN2-
VMON1
VMON2
PHASE1
PHASE2
PGOOD
1kΩ
137Ω
R9
COUT3
3x100µF
17
3
C3
4.7µF
CLKOUT
MODE
ISHARE
SYNC
ISL8225M
R10
1kΩ
18
4
19
5
R11
316Ω
12
10
24
20
2
COMP1
COMP2
C4
470pF
6
9
FIGURE 23. 3-PHASE PARALLELED AT 1.5V/40A AND 1-PHASE AT 5V/10A OUTPUT WITH 90° INTERLEAVING
FN7822.1
January 31, 2013
15
ISL8225M
Typical Application Circuits(Continued)
4.5V TO 20V
1.2V/90A
MASTER PHASE
R1
14
8
23
22
VIN
VIN1
VOUT1
VOUT
+
CIN1
2x470µF
VSEN1+
VIN2
4x22µF
1kΩ
R2
1kΩ
COUT1
4x100µF
15
16
7
21
25
R4*
EN/FF1
EN/FF2
VCC
VSEN1-
VOUT2
*SEE TABLE 1 ON PAGE 17
FOR R3/R4 VALUES.
SLAVE
VCC1
26
1
VCC1
VSEN2+
VSEN2-
VMON1
VMON2
PHASE1
PHASE2
PGOOD
R3*
C1
4.7µF
17
3
CLKOUT
MODE
ISHARE
SYNC
ISL8225M
18
4
VCC1
19
5
12
10
24
R5
3.3kΩ
20
2
COMP1
COMP2
PGOOD
6
9
C8
470pF
14
8
23
22
21
SLAVE
VIN1
VOUT1
VSEN1+
VSEN1-
VOUT2
VIN2
VCC2
COUT2
4x100µF
15
16
7
EN/FF1
EN/FF2
VCC
CIN2
4x22µF
25
26
1
SLAVE
VSEN2+
VSEN2-
VMON1
VMON2
PHASE1
PHASE2
PGOOD
VCC2
17
3
CLKOUT
MODE
ISL8225M
C2
4.7µF
R6*
500Ω
18
4
19
5
R7*
500Ω
ISHARE
SYNC
12
10
24
20
2
*KEEP R6/R7 THE SAME
RATIO AS R1/R2. EACH VMON
PIN CAN HAVE SEPERATE
RESISTOR DIVIDER TO
MONITOR THE OUTPUT
VOLTAGE.
COMP1
COMP2
C3
470pF
6
9
C4
470pF
14
23 SLAVE
VIN1
VOUT1
VSEN1+
VSEN1-
VOUT2
8
15
16
7
22
VIN2
VCC3
COUT3
4x100µF
21
EN/FF1
EN/FF2
VCC
CIN3
4x22µF
25
26
1
SLAVE
VCC3
VSEN2+
VSEN2-
VMON1
VMON2
PHASE1
PHASE2
PGOOD
17
3
CLKOUT
MODE
ISHARE
SYNC
ISL8225M
C5
4.7µF
18
4
19
5
12
10
24
20
2
COMP1
COMP2
C6
470pF
C7
470pF
6
9
FIGURE 24. SIX-PHASE 90A 1.2V OUTPUT CIRCUIT
FN7822.1
January 31, 2013
16
ISL8225M
TABLE 1. ISL8225M DESIGN GUIDE MATRIX (REFER TO FIGURE 18)
CIN1
(BULK)
(NOTE 10)
EN/FF (kΩ)
R5/R6
(NOTE 11)
LOAD
(A)
(NOTE 12)
V
V
R2 or R4
CIN2
(CERAMIC)
COUT1
(CERAMIC)
COUT2
(BULK)
CFF
(nF)
FREQ.
(kHz)
R
SYNC
IN OUT
CASE (V) (V)
(Ω)
(kΩ)
None
None
None
None
None
None
None
None
None
None
None
None
None
None
None
None
None
None
249
1
2
3
4
5
6
7
8
9
5
5
1
1
1.5k
1.5k
1.5k
1.5k
1.0k
1.0k
1.0k
1.0k
1.0k
1.0k
665
665
665
665
665
665
316
316
316
316
316
316
221
221
221
221
221
221
137
137
137
137
1x330µF
1x330µF
1x330µF
1x330µF
1x330µF
1x330µF
1x330µF
1x330µF
1x330µF
1x330µF
1x330µF
1x330µF
1x330µF
1x330µF
1x330µF
1x330µF
1x330µF
1x330µF
1x330µF
1x330µF
1x330µF
1x330µF
1x330µF
1x330µF
1x330µF
1x330µF
1x330µF
1x330µF
1x330µF
1x330µF
1x330µF
1x330µF
1x100µF
1x100µF
2x22µF
2x22µF
1x100µF
1x100µF
2x22µF
2x22µF
2x22µF
2x22µF
1x100µF
1x100µF
2x22µF
2x22µF
2x22µF
2x22µF
1x100µF
1x100µF
2x22µF
2x22µF
2x22µF
2x22µF
1x100µF
1x100µF
2x22µF
2x22µF
2x22µF
2x22µF
2x22µF
2x22µF
2x22µF
2x22µF
1x100µF
3x100µF
1x100µF
3x100µF
1x100µF
3x100µF
1x100µF
3x100µF
1x100µF
3x100µF
1x100µF
3x100µF
1x100µF
3x100µF
1x100µF
3x100µF
1x100µF
3x100µF
1x100µF
3x100µF
1x100µF
3x100µF
1x100µF
3x100µF
1x100µF
3x100µF
1x100µF
3x100µF
1x100µF
3x100µF
1x100µF
3x100µF
1x330µF
None
None
3.3
6.04/3.01
6.04/3.01
6.04/1.50
6.04/1.50
6.04/3.01
6.04/3.01
6.04/1.50
6.04/1.50
6.04/1.50
6.04/1.50
6.04/3.01
6.04/3.01
6.04/1.50
6.04/1.50
6.04/1.50
6.04/1.50
6.04/3.01
6.04/3.01
6.04/1.50
6.04/1.50
6.04/1.50
6.04/1.50
6.04/3.01
6.04/3.01
6.04/1.50
6.04/1.50
6.04/1.50
6.04/1.50
6.04/1.50
6.04/1.50
6.04/1.50
6.04/1.50
500
500
500
500
500
500
500
500
500
500
500
500
500
500
500
500
500
500
650
650
750
750
500
500
800
800
850
850
950
950
950
950
15
15
15
15
15
15
15
15
15
15
15
15
15
15
15
15
15
15
15
15
14
14
15
15
14
14
13
13
12
12
10
10
12
12
5
1
1x330µF
None
None
3.3
1
1.2
1.2
1x330µF
None
None
3.3
5
12 1.2
12 1.2
20 1.2
1x330µF
None
None
3.3
1x330µF
None
3.3
10 20 1.2
4.7
11
12
5
5
1.5
1.5
1x330µF
None
None
3.3
13 12 1.5
14 12 1.5
15 20 1.5
16 20 1.5
1x330µF
None
None
3.3
1x330µF
None
None
3.3
17
18
5
5
2.5
2.5
1x330µF
None
None
3.3
19 12 2.5
20 12 2.5
21 20 2.5
22 20 2.5
1x330µF
None
None
3.3
249
1x330µF
None
None
3.3
147
147
23
24
5
5
3.3
3.3
1x330µF
None
None
None
None
None
None
3.3
None
None
124
25 12 3.3
26 12 3.3
27 20 3.3
28 20 3.3
1x330µF
None
124
1x330µF
None
107
107
29 12
30 12
31 20
32 20
5
5
5
5
1x330µF
None
None
None
None
3.3
82.5
82.5
82.5
82.5
1x330µF
None
NOTES:
10. CIN bulk capacitor is optional only for decoupling noise due to the long input cable. CIN2 and COUT1 ceramic capacitors are listed for one phase only.
Please double the capacitor quantity for dual-phase operations.
11. EN/FF resistor divider is tied directly to VIN. The resistors listed here are for two channels' EN/FF pins tied together. If the separate resistor divider is
used for each channel, the resistor value needs to be doubled.
12. MAX load current listed in the table is for conditions at +25°C and no air flow on a typical Intersil 4-layer evaluation board.
FN7822.1
January 31, 2013
17
ISL8225M
TABLE 2. RECOMMENDED I/O CAPACITOR IN TABLE 1
VALUE
VENDOR
PART NUMBER
C3225X5R0J107M
GRM32ER60J107M
12106D107MAT2A
GRM32ER61E226KE15L
TMK325BJ226MM-T
12103D226KAT2A
10TPB330M
TDK, Input and Output Ceramic
Murata, Input and Output Ceramic
AVX, Input and Output Ceramic
Murata, Input Ceramic
100µF, 6.3V, 1210
100µF, 6.3V, 1210
100µF, 6.3V, 1210
22µF, 25V, 1210
Taiyo Yuden, Input Ceramic
AVX, Input Ceramic
22µF, 25V, 1210
22µF, 25V, 1210
Panasonic POSCAP, Output Bulk
Panasonic SMT, Input Bulk
330µF, 10V
330µF, 25V
EEVHA1E331UP
TABLE 3. ISL8225M OPERATION MODES
1ST MODULE (I = INPUT; O = OUTPUT; I/O = INPUT AND OUTPUT, BI-DIRECTION)
MODES OF OPERATION
OPERATION OPERATION
VMON1
ND
OUTPUT
(SEE
ND
CLKOUT/REFIN
OF 2
2
CHANNEL
ST
MODE
OF 2ND
MODULE
MODE
ST
EN1/FF1 EN2/FF2 VSEN2- MODE VSEN2+
WRT 1
VMON2 MODULE WRT 1 (O)
OF 3RD
DESCRIPTION
FOR DETAILS)
MODE
1
(I)
(I)
(I)
(I)
(I)
(I OR O)
(Note 14) (Note 14)
(NOTE 13)
MODULE
-
0
0
-
-
-
-
-
-
-
-
-
-
-
-
Disabled
2A
0
1
Active Active Active
Active
VMON1 =
VMON2toKeep
PGOOD Valid
Single Phase
2B
1
0
-
-
-
-
-
-
VMON1 =
VMON2toKeep
PGOOD Valid
-
-
Single Phase
3A
3B
1
1
1
1
<V -0.7V Active Active 29% to 45%
CC
Active
Active
-
-
0°
-
-
-
-
Dual Regulator
Dual Regulator
of V (I)
CC
<V -0.7V Active Active 45% to 62%
CC
90°
of V (I)
CC
3C
4
1
1
1
1
1
1
<V -0.7V Active Active >62% of V (I) Active
CC CC
-
-
-
180°
-60°
-
-
-
-
-
-
Dual Regulator
DDR Mode
2-Phase
<V -0.7V Active Active <29% of V (I) Active
CC CC
5A
V
GND
-
60°
VMON1
or
180°
CC
Divider
5B
5C
1
1
1
1
V
V
GND
GND
-
-
60°
60°
Divider Divider
180°
180°
5B
5C
5B
5C
6-Phase
CC
VMON1 Active
3 Outputs
CC
or
Divider
6
1
1
1
1
1
1
V
V
V
V
V
V
GND
120°
90°
1kΩ
1kΩ
1kΩ
Active
Divider
Active
240°
180°
180°
2B
7A
7B
-
-
-
3-Phase
4-Phase
CC
CC
CC
CC
CC
CC
7A
7B
V
V
CC
90°
2 Outputs
CC
st
(1 module in
Mode 7A)
7C
1
1
V
V
V
90°
1kΩ
Active
180°
3, 4
-
3 Outputs
(1 module in
CC
CC
CC
st
Mode 7A)
8
9
Cascaded Module Operation MODEs 5B+5B+7A+5B+5B+5B/7A, No External Clock Required
External Clock or External Logic Circuits Required for Equal Phase Interval
12-Phase
5, 7, 8, 9, 10, 11,
or
(PHASE >12)
NOTE:
ND
13. “2 CHANNEL WRT 1ST” means “second channel with respect to first;” in other words, Channel 2 lags Channel 1 by the degrees specified in this
column. For example, 90° means Channel 2 lags Channel 1 by 90°; -60° means Channel 2 leads Channel 1 by 60°.
14. “VMON1” means that the pin is tied to the VMON1 pin of the same module.
“Divider” means that there is a resistor divider from VOUT to SGND; refer to Figure 24.
“1kΩ” means that there is a 1kΩ resistor connecting the pin to SGND; refer to Figure 22.
FN7822.1
January 31, 2013
18
ISL8225M
recommended to increase the frequency to lower the inductor
ripple. Please refer to Figure 25 for frequency selection at different
Application Information
Programming the Output Voltage
operating conditions, then refer to Figure 31 to choose R
.
SYNC
The ISL8225M has an internal 0.6V ±0.7% reference voltage.
Programming the output voltage requires a resistor divider (R1
and R2) between the VOUT, VSEN+, and VSEN- pins, as shown in
Figure 18. Please note that the output voltage accuracy is also
dependent on the resistor accuracy of R1 and R2. The user needs
to select a high accuracy resistor (i.e. 0.5%) in order to achieve
the overall output accuracy. The output voltage can be calculated
as shown in Equation 1:
Selection of Input Capacitor
Selection of the input filter capacitor is based on how much
ripple the supply can tolerate on the DC input line. The larger the
capacitor, the less ripple expected, however, consideration
should be given to the higher surge current during power-up. The
ISL8225M provides a soft-start function that controls and limits
the current surge. The value of the input capacitor can be
calculated as shown in Equation 2:
R1
R2
(EQ. 1)
⎛
⎞
⎠
-------
V
= 0.6 × 1 +
I
• D(1 – D)
OUT
⎝
O
V
(EQ. 2)
----------------------------------
=
C
IN(MIN)
• f
P-P SW
Note: It is recommended to use a 1kΩ value for the top resistor,
R1. The value of the bottom resistor for different output voltages
is shown in Table 4.
where:
• C
is the minimum required input capacitance (µF)
IN(MIN)
TABLE 4. VALUE OF BOTTOM RESISTOR FOR DIFFERENT OUTPUT
• I is the output current (A)
O
VOLTAGES (V
vs R2)
OUT
• D is the duty cycle
R1
V
R2
OUT
• V
is the allowable peak-to-peak voltage (V)
is the switching frequency (Hz)
P-P
(Ω)
(V)
(Ω)
• f
1k
1k
1k
1k
1k
1k
1k
1k
1k
1k
1k
0.6
0.8
1.0
1.2
1.5
1.8
2.0
2.5
3.3
5.0
6.0
Open
3.01k
1.50k
1.00k
665
SW
In addition to the bulk capacitance, some low Equivalent Series
Resistance (ESR) ceramic capacitance is recommended to
decouple between the VIN and PGND of each channel. See Table 2
for some recommended capacitors. This capacitance reduces
voltage ringing created by the switching current across parasitic
circuit elements. All these ceramic capacitors should be placed as
closely as possible to the module pins. The estimated RMS current
should be considered in choosing ceramic capacitors.
Io D(1 – D)
491
422
316
--------------------------------
=
(EQ. 3)
I
IN(RMS)
221
η
137
Each 10µF X5R or X7R ceramic capacitor is typically good for 2A
to 3A of RMS ripple current. Refer to the capacitor vendor to
check the RMS current ratings. In a typical 15A output
application for one channel, if the duty cycle is 0.5, it needs at
least three 10µF X5R or X7R ceramic input capacitors.
110
Due to the minimum off-time limit of 410ns, the module has a
maximum output voltage, depending on input voltage. Refer to
Figure 25 for the 5V input voltage limitation.
Selection of Output Capacitors
1100
20V
IN
The ISL8225M is designed for low-output voltage ripple. The
output voltage ripple and transient requirements can be met with
bulk output capacitors (COUT) that have adequately low ESR.
COUT can be a low ESR tantalum capacitor, a low ESR polymer
capacitor, or a ceramic capacitor. The typical capacitance is
330µF, and decoupled ceramic output capacitors are used for
each phase. See Table 1 and Table 2 for more capacitor
information. Internally optimized loop compensation provides
sufficient stability margins for all ceramic capacitor applications,
with a recommended total value of 300µF per phase. Additional
output filtering may be needed if further reduction of output
ripple or dynamic transient spike is required.
1000
15V
IN
900
800
700
600
500
12V
IN
10V
IN
8V
IN
5V
IN
0
1
2
3
4
5
EN/FF Turn ON/OFF
V
(V)
OUT
Each output of the ISL8225M can be turned on/off independently
through the EN/FF pins. For parallel use, tie all EN/FF pins together.
Since this pin has the feed-forward function, the voltage on this pin
can actively adjust the loop gain to be constant for variable input
voltage. Please refer to Table 1 to select the resistor divider for
FIGURE 25. RECOMMENDED FREQUENCY vs V AT V
IN OUT
At higher output voltage, the inductor ripple increases, which makes
both output ripple and inductor power loss higher. Therefore, it is
FN7822.1
January 31, 2013
19
ISL8225M
commonly used conditions. Otherwise, use the following procedures
to finish the EN/FF design:
Functional Description
Initialization
1. A resistor divider from V to GND is recommended to set the
IN
EN/FF voltage between 1.25V to 5.0V. The resistor divider
ratio is recommended to be between 3/1 to 4/1 (as shown in
Figure 21) with a resistor divider at 7.15kΩ/2.05kΩ.
Initially, the Power-On Reset (POR) circuits continuously monitor
bias voltages (V ) and voltage at the EN/FF pin. The POR
CC
function initiates soft-start operation 384 clock cycles
after: (1) the EN pin voltage is pulled above 0.8V, (2) all input
supplies exceed their POR thresholds, and (3) the PLL locking
time expires. The Enable pin can be used as a voltage monitor
and to set the desired hysteresis, with an internal 30µA sinking
current going through an external resistor divider. The sinking
current is disengaged after the system is enabled. This feature is
specially designed for applications that require higher input rail
POR for better under-voltage protection. For example, in 12V
2. Check EN turn-on hysteresis (Recommend V
> 0.3V) :
(EQ. 4)
EN_HYS
–5
V
= N • R • 3x10
UP
EN – HYS
where:
• R is the top resistor of the resistor divider
UP
• N is the total number of the EN/FF pins tied to the resistor divider
3. Set the maximum current flowing through the top pull-up
applications, R = 53.6kΩ and R
turn-on threshold (V
EN_RTH
= 5.23kΩ sets the
UP
DOWN
) to 10.6V and the turn-off threshold
).
resistor R to below 7mA (considering EN/FF is pulled to
UP
ground (V
= 0)). Refer to Figure 23; a 3.01kΩ/1kΩ
EN/FF
(V
) to 9V, with 1.6V hysteresis (V
EN_FTH EN_HYS
resistor is used to allow for the input voltage from 5V to 20V
operation. In addition, the maximum current flowing through
R5 is 6.6mA (<7mA).
During shutdown or fault conditions, soft-start is quickly reset,
and the gate driver immediately changes state (<100ns) when
input drops below POR.
4. If the EN/FF is controlled by system EN signal instead of the
input voltage, we recommend setting the fixed EN/FF voltage
to about 1/3.5 of the input voltage. If the input voltage is 12V,
a 3.3V system EN signal can be tied to EN/FF pin directly.
Enable and Voltage Feed-forward
Voltage applied to the EN/FF pin is fed to adjust the sawtooth
amplitude of the channel. Sawtooth amplitude is set to 1.25 times
the corresponding FF voltage when the module is enabled. This
configuration helps maintain a constant gain. This configuration
also helps maintain input voltage to achieve optimum loop response
over a wide input voltage range.
5. If the input voltage is below 5.5V, it is recommended to have
EN/FF voltage >1.5V to have better stability. The input voltage
can be directly tied to the VCC pin to disable the internal LDO.
6. A 1nF capacitor is recommended on the EN/FF pin to avoid
the noise injecting into the feed-forward loop.
A 384-cycle delay is added after the system reaches its rising
POR and prior to soft-start. The RC timing at the FF pin should be
small enough to ensure that the input bus reaches its static state
and that the internal ramp circuitry stabilizes before soft-start. A
large RC could cause the internal ramp amplitude not to
synchronize with the input bus voltage during output start-up or
when recovering from faults. A 1nF capacitor is recommended as
a starting value for typical applications.
Thermal Considerations
The ISL8225M QFN package offers typical junction to ambient
thermal resistance θ of approximately 10°C/W at natural
JA
convection (~5.8°C/W at 400LFM) with a typical 4-layer PCB.
Therefore, use Equation 5 to estimate the module junction
temperature:
(EQ. 5)
T
= P × Θ + T
junction
jA ambient
In a multi-module system, with the EN pins are wired together, all
modules can immediately turn off, at one time, when a fault
condition occurs in one or more modules. A fault pulls the EN pin
low, disabling all modules, and does not create current bounce;
thus, no single channel is overstressed when a fault occurs.
where:
• T
is the module internal maximum temperature (°C)
is the system ambient temperature (°C)
junction
• T
ambient
• P is the total power loss of the module package (W)
Because the EN pins are pulled down under fault conditions, the
• θ is the thermal resistance of module junction to ambient
JA
pull-up resistor (R ) should be scaled to sink no more than 7mA
UP
current from the EN pin. Essentially, the EN pins cannot be
directly connected to VCC.
If the calculated temperature, T
design target, the extra cooling scheme is required. Please refer
to “Current Derating” on page 24 for adding air flow.
, is over the required
junction
VIN
R
² V
V
EN_HYS
UP
= --------------------------------------------------------------
EN_REF
– V
R
V
= ----------------------------
R
UP
DOWN
I
V
R
EN_HYS
UP
EN_FTH
EN_REF
384
0.8V
CLOCK
EN
SOFT-START
= V
– V
CYCLES
EN_FTH
EN_RTH
EN_HYS
ON/OFF
R
DOWN
I
= 30µA
EN_HYS
OV, OT, OC, AND PLL LOCKING FAULTS
FIGURE 26. SIMPLIFIED ENABLE AND VOLTAGE FEED-FORWARD CIRCUIT
FN7822.1
January 31, 2013
20
ISL8225M
Soft-Start
Power-Good
The ISL8225M has an internal, digital, pre-charged soft-start
circuitry (Figures 27 to 29). The circuitry has a rise time inversely
proportional to the switching frequency. Rise time is determined
by a digital counter that increments with every pulse of the phase
clock. The full soft-start time from 0V to 0.6V can be estimated
as shown in Equation 6. The typical soft-start time is ~2.5ms.
1280
Power-good comparators monitor voltage on the VMON pin. Trip
points are shown in Figure 30. PGOOD is not asserted until the
soft-start cycle is complete. PGOOD pulls low upon both ENs
disabling it or when the VMON voltage is out of the threshold
window. PGOOD does not pull low until the fault presents for
three consecutive clock cycles.
------------
t
=
(EQ. 6)
UV indication is not enabled until the end of soft-start. In a UV
event, if the output drops below -13% of the target level due to a
reason other than OV, OC, OT, or PLL faults (cases when EN is not
pulled low), PGOOD is pulled low.
SS
f
SW
The ISL8225M is able to work under a pre-charged output. The
PWM outputs do not feed to the drivers until the first PWM pulse
is seen. The low-side MOSFET is on for the first clock cycle, to
provide charge for the bootstrap capacitor. If the pre-charged
output voltage is greater than the final target level but less than
the 113% set point, switching does not start until the output
voltage is reduced to the target voltage and the first PWM pulse
is generated. The maximum allowable pre-charged level is 113%.
If the pre-charged level is above 113% but below 120%, the
output hiccups between 113% (LGATE turns on) and 87% (LGATE
turns off), while EN is pulled low. If the pre-charged load voltage
is above 120% of the targeted output voltage, then the controller
is latched off and cannot power up.
CHANNEL 1 UV/OV
CHANNEL 2 UV/OV
PGOOD
AND
END OF SS1
END OF SS2
OR
SS1_PERIOD
SS2_PERIOD
AND
+20%
SS SETTLING AT VREF + 100mV
FIRST PWM PULSE
+13%
+9%
VMON1, 2
V
TARGET VOLTAGE
OUT
0.0V
-100mV
V
REF
1280
t
= ------------
SS
f
SW
-9%
-13%
384
-----------
t
=
SS_DLY
f
SW
PGOOD LATCH OFF
AFTER 120% OV
PGOOD
FIGURE 27. SOFT-START WITH V
OUT
= 0V
FIGURE 30. POWER-GOOD THRESHOLD WINDOW
Current Share
In parallel operations, the share bus voltages (I
SS SETTLING AT VREF + 100mV
VOUT TARGET VOLTAGE
FIRST PWM PULSE
) of
SHARE
different modules must tie together. The ISHARE pin voltage is
set by an internal resistor and represents the average current of
all active modules. The average current signal is compared with
the local module current, and the current share error signal is fed
into the current correction block to adjust each module’s PWM
pulse accordingly. The current share function provides at least
10% overall accuracy between modules. The current share bus
works for up to 12 phases without requiring an external clock. A
470pF ~1nF capacitor is recommended for each ISHARE pin.
INIT. V
OUT
-100mV
FIGURE 28. SOFT-START WITH V
< TARGET VOLTAGE
OUT
In current sharing scheme, all slave channels have the feedback
loops disabled with the VSEN- pin tied to VCC. The master
channel can control all modules with COMP and ISHARE pins tied
together. For phase-shift setting, all VMON pins of slave channels
are needed to set 0.6V for monitoring use only. Typically, the
slaved VMON pins can be tied together with a resistor divider to
VOUT. However, if the MODE pin is tied to VCC for mode setting,
the related VMON2 pin is needed to tie to SGND with a 1.0kΩ
resistor, as shown in Figure 23 on page 15. If there are multiple
OV = 113%
FIRST PWM PULSE
V
TARGET VOLTAGE
OUT
FIGURE 29. SOFT-START WITH V
TARGET VOLTAGE
BELOW 113% BUT ABOVE FINAL
OUT
FN7822.1
January 31, 2013
21
ISL8225M
modules paralleled with the MODE pins tied to VCC, each VMON2
disturbance. After the delay time, the controller initiates a
soft-start interval. If the output voltage comes up and returns to
regulation, PGOOD transitions high. If the OC trip is exceeded
during the soft-start interval, the controller pulls EN low again.
The PGOOD signal remains low, and the soft-start interval is
allowed to expire. Another soft-start interval is initiated after the
delay interval. If an over-current trip occurs again, this same cycle
repeats until the fault is removed. Since the output voltage may
trigger the OVP if the output current changes too fast, the module
can go into latch-off mode. In this case, the module needs to be
restarted.
pin of the slave module needs to have a 1.0kΩ resistor to GND
while all VMON1 pins of the slave modules can be tied together
with a resistor divider from VOUT to GND, as shown in Figure 24
on page 16. Also see Table 3 for VMON settings.
Over-voltage Protection (OVP)
The over-voltage (OV) protection indication circuitry monitors
voltage on the VMON pin. OV protection is active from the
beginning of soft-start. An OV condition (>120%) would latch the
IC off. In this condition, the high-side MOSFET (Q1 or Q3) latches
off permanently. The low-side MOSFET (Q2 or Q4) turns on
immediately at the time of OV trip and then turns off
Frequency Synchronization and Phase Lock
Loop
The SYNC pin has two primary capabilities: fixed frequency
operation and synchronized frequency operation. ISL8225M has
an internally set fixed frequency of 500kHz. By tying a resistor
permanently after the output voltage drops below 87%. EN and
PGOOD are also latched low in an OV event. The latch condition
can be reset only by recycling V
.
CC
There is another non-latch OV protection (113% of target level).
When EN is low and output is over 113% OV, the low-side
MOSFET turns on until output drops below 87%. This action
protects the power trains when even a single channel of a
multi-module system detects OV. The low-side MOSFET always
turns on when EN = LOW and the output voltage rises above
113% (all EN pins are tied together) and turns off after the output
drops below 87%. Thus, in a high phase count application
(multi-module mode), all cascaded modules can latch off
simultaneously via the EN pins (EN pins are tied together in
multi-phase mode). Each channel shares the same sink current
to reduce stress and eliminate bouncing among phases.
(R
) to SGND from the SYNC pin, the switching frequency can
SYNC
be set to be more than 500kHz. To increase the switching
frequency, select an externally connected resistor, R , from
SYNC
SYNC to SGND according to the frequency setting curve shown in
Figure 31. See Table 1 for R
at commonly used frequency.
SYNC
800
700
600
500
400
300
200
100
0
Over-Temperature Protection (OTP)
When the junction temperature of the internal controller is
greater than +150°C (typically), the EN pin is pulled low to inform
other cascaded channels via their EN pins. All connected ENs
stay low and then release after the module’s junction
temperature drops below +125°C (typically), a +25°C hysteresis
(typically).
500
600 700 800 900 1000 1100 1200 1300 1400 1500
FREQUENCY (kHz)
FIGURE 31. R
vs SWITCHING FREQUENCY
SYNC
Over-current Protection (OCP)
The OCP peak level is set to about 20A for each channel, but the OC
Connecting the SYNC pin to an external square-pulse waveform
(such as the CLKOUT signal, typically 50% duty cycle from
another ISL8225M) synchronizes the ISL8225M switching
frequency to the fundamental frequency of the input waveform.
The synchronized frequency can be from 150kHz to 1500kHz.
The applied square-pulse recommended high level voltage range
trip point can vary, due mainly to MOSFET r
variations (over
DS(ON)
process, current, and temperature). The OCP can be increased by
increasing the switching frequency since the inductor ripple is
reduced. However, the module efficiency drops accordingly with
more switching loss. When OCP is triggered, the controller pulls
EN low immediately to turn off all switches. The OCP function is
enabled at start-up and has a 7-cycle delay before it triggers.
is 3V to V +0.3V. The frequency synchronization feature
CC
synchronizes the leading edge of the CLKOUT signal with the
falling edge of Channel 1’s PWM signal. CLKOUT is not available
until PLL locks. No capacitor is recommended on the SYNC pin.
In multi-module operation, ISHARE pins can be connected to
create V
, which represents the average current of all
ISHARE
Locking time is typically 130µs. EN is not released for a soft-start
cycle until SYNC is stabilized and PLL is locking. Connecting all
EN pins together in a multi-phase configuration is recommended.
active channels. Total system currents are compared with a
precision threshold to determine the over-current condition. Each
channel also has an additional over-current set point with a
7-cycle delay. This scheme helps protect modules from damage
in multi-module mode by having each module carry less current
than the set point.
Loss of a synchronization signal for 13 clock cycles causes the
module to be disabled until PLL returns locking, at which point, a
soft-start cycle is initiated and normal operation resumes.
Holding SYNC low disables the module. Please note that the
quick change of the synchronization signal can cause module
shutdown.
For overload and hard short conditions, over-current protection
reduces the regulator RMS output current to much less than full
load by putting the controller into hiccup mode. A delay equal to
three soft-start intervals is entered to allow time to clear the
FN7822.1
January 31, 2013
22
ISL8225M
Tracking Function
Layout Guide
If CLKOUT is less than 800mV, an external soft-start ramp (0.6V)
can be in parallel with the Channel 2 internal soft-start ramp for
tracking applications. Therefore, the Channel 2’s output voltage
can track the output voltage of Channel 1.
To achieve stable operation, low losses, and good thermal
performance, some layout considerations are necessary
(Figure 32).
• VOUT1, VOUT2, PHASE1, PHASE2, PGND, VIN1 and VIN2
should have large, solid planes. Place enough thermal vias to
connect the power planes in different layers under or around
the module.
The tracking function can be applied to a typical Double Data
Rate (DDR) memory application, as shown in Figure 20 on
page 13. The output voltage (typical VTT output) of Channel 2
tracks with the input voltage [typical VDDQ*(1+k) from
Channel 1] at the CLKOUT pin. As for the external input signal
and the internal reference signal (ramp and 0.6V), the one with
the lowest voltage is used as the reference for comparing with
the FB signal. In DDR configuration, VTT channel should start up
later, after its internal soft-start ramp, such that VTT tracks the
voltage on the CLKOUT pin derived from VDDQ. This configuration
can be achieved by adding more filtering at EN/FF1 than at
EN/FF2.
• Place high-frequency ceramic capacitors between VIN, VOUT,
and PGND, as closely to the module as possible in order to
minimize high-frequency noise.
• Use remote sensed traces to the regulation point to achieve
tight output voltage regulation, and keep the sensing traces
close to each other in parallel.
• PHASE1 and PHASE2 pads are switching nodes that generate
switching noise. Keep these pads under the module. For
noise-sensitive applications, it is recommended to keep phase
pads only on the top and inner layers of the PCB. Also, do not
place phase pads exposed to the outside on the bottom layer
of the PCB.
The resistor divider ratio (k) of R7/R8 in Figure 20 is calculated
as shown in Equation 7:
V
TT
(EQ. 7)
------------
k =
– 1
0.6V
• Avoid routing any noise-sensitive signal traces, such as the
VSEN+, VSEN-, ISHARE, COMP and VMON sensing points, near
the PHASE pins.
Mode Programming
ISL8225M can be programmed for dual-output, paralleled
single-output or mixed outputs (Channel 1 in parallel and
Channel 2 in dual-output). With multiple ISL8225Ms, up to 6
modules using its internal cascaded clock signal control, the
modules can supply large current up to 180A. For complete
operation, please refer to Table 3 on page 18. Commonly used
settings are listed in Table 5.
• Use a separated SGND ground copper area for components
connected to signal ground pins. Connect SGND to PGND with
multiple vias underneath the unit in one location to avoid the
noise coupling, as shown in Figure 32. Don't ground vias
surrounded by the noisy planes of VIN, PHASE and VOUT. For
dual output applications, the SGND to PGND vias are preferred
to be as close as possible to SGND pin.
TABLE 5. PHASE-SHIFT SETTING
• Optional snubbers can be put on the bottom side of the board
layout, connecting the PHASE to PGND planes, as shown in
Figure 32.
PHASE-SHIFT
OPERATION
BETWEEN PHASES VSEN2- VSEN2+ CLKOUT MODE
Dual Output
(Figure 18)
180°
180°
90°
N/C
VCC
VCC
VCC
N/C
N/C
VCC
N/C
VCC
N/C
N/C
N/C
N/C
SGND
VCC
COUT2
COUT1
PGND
R3
PGND
R1
30A
(Figure 19)
VOUT2
VOUT1
+
-
+
-
TO LOAD
R4
TO LOAD
R2
60A
(Figure 22)
KELVIN CONNECTIONS
FOR THE VSENS LINES
KELVIN CONNECTIONS
FOR THE VSENS LINES
PIN 1
90A
60°
SGND
(Figure 24)
SGND
VIN2
VIN1
When the module is in the dual-output condition, depending
upon the voltage level at CLKOUT (which is set by the VCC resistor
divider output), ISL8225M operates with phase shifted as the
CLKOUT voltage shown in Table 6. The phase shift is latched as
CIN2
CIN1
PHASE2
PHASE1
V
rises above POR; it cannot be changed on the fly.
CC
OPTIONAL SNUBBER
OPTIONAL SNUBBER
TABLE 6. CLKOUT TO PROGRAM PHASE SHIFT AT DUAL-OUTPUT
CLKOUT
VOLTAGE SETTING
PHASE FOR CLKOUT WRT RECOMMENDED
PGND
CHANNEL 1
CLKOUT VOLTAGE
<29% of V
CC
-60°
15% V
37% V
53% V
CC
CC
CC
FIGURE 32. RECOMMENDED LAYOUT
29% to 45% of V
90°
CC
CC
45% to 62% of V
120°
62% of V
CC
180°
V
CC
FN7822.1
January 31, 2013
23
ISL8225M
pad and the I/O termination dimensions, except that the PCB
Current Derating
Experimental power loss curves (Figures 33 and 34), along with
lands are slightly longer than the QFN terminations by about
0.2mm (0.4mm max). This extension allows for solder filleting
around the package periphery and ensures a more complete and
inspectable solder joint. The thermal lands on the PCB layout
should match 1:1 with the package exposed die pads.
θ
from thermal modeling analysis, can be used to evaluate the
JA
thermal consideration for the module. Derating curves are
derived from the maximum power allowed while maintaining
temperature below the maximum junction temperature of
+120°C (Figures 35 through 40). The maximum +120°C
junction temperature is considered for the module to load the
current consistently and it provides the 5°C margin of safety
from the rated junction temperature of +125°C. If necessary,
customers can adjust the margin of safety according to the real
applications. All derating curves are obtained from the tests on
the ISL8225MEVAL4Z evaluation board. In the actual
application, other heat sources and design margins should be
considered.
Thermal Vias
A grid of 1.0mm to 1.2mm pitched thermal vias, which drops
down and connects to buried copper planes, should be placed
under the thermal land. The vias should be about 0.3mm to
0.33mm in diameter, with the barrel plated to about 2.0 ounce
copper. Although adding more vias (by decreasing pitch)
improves thermal performance, it also diminishes results as
more vias are added. Use only as many vias as are needed for
the thermal land size and as your board design rules allow.
Package Description
Stencil Pattern Design
The ISL8225M is integrated into a quad flat-pack no-lead
package (QFN). This package has such advantages as good
thermal and electrical conductivity, low weight, and small size.
The QFN package is applicable for surface mounting technology
and is becoming more common in the industry. The ISL8225M
contains several types of devices, including resistors, capacitors,
inductors, and control ICs. The ISL8225M is a copper lead-frame
based package with exposed copper thermal pads, which have
good electrical and thermal conductivity. The copper lead frame
and multi-component assembly are over-molded with polymer
mold compound to protect these devices.
Reflowed solder joints on the perimeter I/O lands should have
about a 50µm to 75µm (2mil to 3mil) standoff height. The solder
paste stencil design is the first step in developing optimized,
reliable solder joins. The stencil aperture size to land size ratio
should typically be 1:1. Aperture width may be reduced slightly to
help prevent solder bridging between adjacent I/O lands.
To reduce solder paste volume on the larger thermal lands, an
array of smaller apertures instead of one large aperture is
recommended. The stencil printing area should cover 50% to
80% of the PCB layout pattern. A typical solder stencil pattern is
shown in the L26.17x17 package outline drawing on page 28.
The gap width between pads is 0.6mm. Consider the symmetry
of the whole stencil pattern when designing the pads.
The package outline, typical PCB layout pattern, and typical
stencil pattern design are shown in the L26.17x17 package
outline drawing on page 27. Figure 41 shows typical reflow
profile parameters. These guidelines are general design rules.
Users can modify parameters according to specific applications.
A laser-cut, stainless-steel stencil with electropolished
trapezoidal walls is recommended. Electropolishing smooths the
aperture walls, resulting in reduced surface friction and better
paste release, which reduces voids. Using a trapezoidal section
aperture (TSA) also promotes paste release and forms a
brick-like paste deposit, which assists in firm component
placement. A 0.1mm to 0.15mm stencil thickness is
recommended for this large-pitch (1.0mm) QFN.
PCB Layout Pattern Design
The bottom of ISL8225M is a lead-frame footprint, which is
attached to the PCB by surface mounting. The PCB layout pattern
is shown in the L26.17x17 package outline drawing on page 28.
The PCB layout pattern is essentially 1:1 with the QFN exposed
7
6
5
4
3
8
7
6
5
12V TO 2.5V
IN
OUT
4
3
2
1
0
5V TO 2.5V
IN
OUT
2
1
0
5V TO 1V
IN
OUT
12V TO 1V
IN
OUT
20
12V TO 1.5V
IN
OUT
5V TO 1.5V
IN
OUT
0
5
10
15
20
25
30
0
5
10
15
25
30
LOAD CURRENT (A)
LOAD CURRENT (A)
FIGURE 33. POWER LOSS CURVES OF 5V
FIGURE 34. POWER LOSS CURVES OF 12V
IN
IN
FN7822.1
January 31, 2013
24
ISL8225M
Derating Curves All of the following curves were plotted at T = +120°C.
J
30
25
20
15
10
5
30
25
20
15
10
5
400LFM
200LFM
200LFM
400LFM
0LFM
0LFM
0
25
0
45
65
85
105
125
25
45
65
85
105
125
TEMPERATURE (°C)
TEMPERATURE (°C)
FIGURE 35. DERATING CURVE 5V TO 1V
IN
FIGURE 36. DERATING CURVE 12V TO 1V
IN
OUT
OUT
30
25
20
15
10
5
30
25
20
15
10
5
400LFM
200LFM
0LFM
400LFM
200LFM
0LFM
0
25
0
25
45
65
85
105
125
45
65
85
105
125
TEMPERATURE (°C)
TEMPERATURE (°C)
FIGURE 37. DERATING CURVE 5V TO 1.5V
IN
FIGURE 38. DERATING CURVE 12V TO 1.5V
IN
OUT
OUT
30
30
25
20
15
10
5
400LFM
25
20
15
10
5
400LFM
200LFM
0LFM
0LFM
200LFM
0
25
0
25
45
65
85
105
125
45
65
85
105
125
TEMPERATURE (°C)
TEMPERATURE (°C)
FIGURE 39. DERATING CURVE 5V TO 2.5V
IN
FIGURE 40. DERATING CURVE 12V TO 2.5V
IN OUT
OUT
FN7822.1
January 31, 2013
25
ISL8225M
Reflow Parameters
300
250
200
150
100
50
PEAK TEMPERATURE +230°C~+245°C;
TYPICALLY 60s-70s ABOVE +220°C
KEEP LESS THAN 30s WITHIN 5°C OF PEAK TEMP.
Due to the low mount height of the QFN, "No Clean" Type 3 solder
paste, per ANSI/J-STD-005, is recommended. Nitrogen purge is
also recommended during reflow. A system board reflow profile
depends on the thermal mass of the entire populated board, so it
is not practical to define a specific soldering profile just for the
QFN. The profile given in Figure 41 is provided as a guideline to
customize for varying manufacturing practices and applications.
SLOW RAMP (3°C/s MAX)
AND SOAK FROM +100°C
TO +180°C FOR 90s~120s
RAMP RATE ≤1.5°C FROM +70°C TO +90°C
0
0
100
150
200
250
300
350
DURATION (s)
FIGURE 41. TYPICAL REFLOW PROFILE
Revision History
The revision history provided is for informational purposes only and is believed to be accurate, but not warranted. Please go to web to make sure you
have the latest revision.
DATE
REVISION
FN7822.1
CHANGE
January 4, 2013
“Thermal Information” on page 6:
Changed “Maximum Storage Temperature Range” from "-40°C to +150°C" to "-55°C to +150°C"
“Selection of Input Capacitor” on page 19:
Added "f " to Equation 2. Added "f
SW
is the switching frequency (Hz)"
SW
December 3, 2012
FN7822.0
Initial Release
About Intersil
Intersil Corporation is a leader in the design and manufacture of high-performance analog, mixed-signal and power management
semiconductors. The company's products address some of the fastest growing markets within the industrial and infrastructure,
personal computing and high-end consumer markets. For more information about Intersil or to find out how to become a member of
our winning team, visit our website and career page at www.intersil.com.
For a complete listing of Applications, Related Documentation and Related Parts, please see the respective product information page.
Also, please check the product information page to ensure that you have the most updated datasheet: ISL8225M
To report errors or suggestions for this datasheet, please go to: www.intersil.com/askourstaff
Reliability reports are available from our website at: http://rel.intersil.com/reports/search.php
For additional products, see www.intersil.com/en/products.html
Intersil products are manufactured, assembled and tested utilizing ISO9000 quality systems as noted
in the quality certifications found at www.intersil.com/en/support/qualandreliability.html
Intersil products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design, software and/or specifications at any time
without notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be
accurate and reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third
parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of Intersil or its subsidiaries.
For information regarding Intersil Corporation and its products, see www.intersil.com
FN7822.1
January 31, 2013
26
ISL8225M
Package Outline Drawing
L26.17x17
26 LEAD QUAD FLAT NO-LEAD PLASTIC PACKAGE (PUNCH QFN)
Rev 4, 10/12
17.8±0.2
17.0±0.2
9
8
7 6 5 4 3 2
9
8
7 6 5 4 3 2
1
26
1
26
10
11
12
10
11
12
25
24
23
25
24
23
22
21
22
21
13
14
1516171819 20
13
14
151617181920
PIN NO. DEFINITION (TOP VIEW)
TOP VIEW
X4
0.2 S AB
16X 0.70 (FULL LEAD)
3.66
4.00
3.50
A A A A A A A A A A A A A
3.50
0.80
8.95
12
10
12
B
8.95
10
1
1
A:1.0±0.1
3.35
14x 0.75
3.35
2.97
A A A A A A A A A A A A A
16x 1.75±0.05 (FULL LEAD)
PIN-TO-PIN DISTANCE (BOTTOM VIEW)
0.05 S AB
A
BOTTOM VIEW
S 0.2
SIDE VIEW
S
FN7822.1
January 31, 2013
27
ISL8225M
9.30
7.83
6.53
6.50
6.13
5.73
5.33
0.75
0.65
0.40
0.25
9.30
7.15
6.35
5.65
5.35
4.65
4.35
1
10
12
0.75
0.35
0
0.35
0.75
0.25
0.40
0.65
0.75
4.35
4.65
5.35
5.65
6.35
7.15
9.30
5.33
5.73
6.13
6.50
6.53
7.83
9.30
TYPICAL RECOMMENDED LAND PATTERN (TOP VIEW)
7.25
6.25
5.75
5.25
4.75
9.20
7.93
5.25
4.75
4.25
3.75
3.25
2.75
2.25
1.75
1.25
0.85
0.15
4.25
3.75
7.38
6.83
3.25 6.43
2.75 5.43
2.25 5.03
1.75 3.36
1.25 2.76
0.95 0.95
7.38
6.60
4.05
2.70
2.40
0.25
1.05
0.00
1.05
0.70
0
0.15
0.85
1.25
1.75
0
0
0.70
0.95
0.25
0.95
2.40
2.70
4.05
1.25
1.75
3.36
2.25
2.75
3.25
3.75
4.25
4.75
2.25
2.75
3.25
3.75
4.25
4.75
5.25
5.75
6.25
7.25
5.03
5.43
6.43
6.83
7.38
6.60
7.38
5.25
7.93
SOLDER STENCIL PATTERN WITH SQUARE PADS 2 OF 2 (TOP VIEW)
SOLDER STENCIL PATTERN WITH SQUARE PADS 1 OF 2 (TOP VIEW)
FN7822.1
January 31, 2013
28
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