EL5166IS-T7 [INTERSIL]
1.4GHz Current Feedback Amplifiers with Enable; 1.4GHz的电流反馈放大器与启用
| 型号： | EL5166IS-T7 |
| 厂家： | 
Intersil |
| 描述： | 1.4GHz Current Feedback Amplifiers with Enable |
| 文件： | 总15页 (文件大小：1113K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
EL5166, EL5167
®
Data Sheet
December 13, 2004
FN7365.3
1.4GHz Current Feedback Amplifiers with
Enable
Features
• Gain-of-1 bandwidth = 1.4GHz/gain-of-2
bandwidth = 800MHz
The EL5166 and EL5167 amplifiers are of the current
feedback variety and exhibit a very high bandwidth of
• 6000V/µs slew rate
1.4GHz at A = +1 and 800MHz at A = +2. This makes
V
V
• Single and dual supply operation from 5V to 12V
• Low noise = 1.5nV/√Hz
these amplifiers ideal for today's high speed video and
monitor applications, as well as a number of RF and IF
frequency designs.
• 8.5mA supply current
With a supply current of just 8.5mA and the ability to run
from a single supply voltage from 5V to 12V, these amplifiers
offer very high performance for little power consumption.
• Fast enable/disable (EL5166 only)
• 600MHz family - (EL5164 and EL5165)
• 400MHz family - (EL5162 and EL5163)
• 200MHz family - (EL5160 and EL5161)
• Pb-Free Available (RoHS Compliant)
The EL5166 also incorporates an enable and disable
function to reduce the supply current to 13µA typical per
amplifier. Allowing the CE pin to float or applying a low logic
level will enable the amplifier.
The EL5167 is offered in the 5-pin SOT-23 package and the
EL5166 is available in the 6-pin SOT-23 as well as the
industry-standard 8-pin SO packages. Both operate over the
industrial temperature range of -40°C to +85°C.
Applications
• Video amplifiers
• Cable drivers
• RGB amplifiers
Ordering Information
• Test equipment
TAPE &
• Instrumentation
• Current to voltage converters
PART NUMBER
EL5166IS
PACKAGE
8-Pin SO
8-Pin SO
8-Pin SO
REEL
PKG. DWG. #
MDP0027
MDP0027
MDP0027
MDP0027
-
7”
13”
-
EL5166IS-T7
EL5166IS-T13
Pinouts
EL5166
EL5166ISZ
(See Note)
8-Pin SO
(Pb-free)
(8-PIN SO)
TOP VIEW
EL5166ISZ-T7
(See Note)
8-Pin SO
(Pb-free)
7”
MDP0027
MDP0027
NC
IN-
1
2
3
4
8
7
6
5
CE
EL5166ISZ-T13
(See Note)
8-Pin SO
(Pb-free)
13”
VS+
OUT
NC
-
+
IN+
VS-
EL5166IW-T7
EL5167IC-T7
EL5167IW-T7
EL5166IW-T7A
EL5167IC-T7A
EL5167IW-T7A
6-Pin SOT-23
5-Pin SC-70
5-Pin SOT-23
6-Pin SOT-23
5-Pin SC-70
5-Pin SOT-23
7”
7”
7”
7”
7”
7”
MDP0038
P5.049
MDP0038
MDP0038
P5.049
EL5166
EL5167
(6-PIN SOT-23)
(5-PIN SOT-23, SC-70)
TOP VIEW
TOP VIEW
MDP0038
NOTE: Intersil Pb-free products employ special Pb-free material sets;
molding compounds/die attach materials and 100% matte tin plate
termination finish, which are RoHS compliant and compatible with
both SnPb and Pb-free soldering operations. Intersil Pb-free products
are MSL classified at Pb-free peak reflow temperatures that meet or
exceed the Pb-free requirements of IPC/JEDEC J STD-020C.
OUT
VS-
IN+
1
2
3
6
5
4
VS+
CE
OUT
VS-
IN+
1
2
3
5
4
VS+
IN-
+
-
+
-
IN-
CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures.
1
1-888-INTERSIL or 321-724-7143 | Intersil (and design) is a registered trademark of Intersil Americas Inc.
Copyright © Intersil Americas Inc. 2003-2004. All Rights Reserved. Elantec is a registered trademark of Elantec Semiconductor, Inc.
All other trademarks mentioned are the property of their respective owners.
EL5166, EL5167
Absolute Maximum Ratings (T = 25°C)
A
Supply Voltage between V + and V -. . . . . . . . . . . . . . . . . . . 12.6V
Power Dissipation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . See Curves
S
S
Maximum Continuous Output Current . . . . . . . . . . . . . . . . . . . 50mA
. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . ±200mA
Pin Voltages. . . . . . . . . . . . . . . . . . . . . . . . . V - -0.5V to V + +0.5V
S S
I
Storage Temperature . . . . . . . . . . . . . . . . . . . . . . . .-65°C to +150°C
Ambient Operating Temperature . . . . . . . . . . . . . . . .-40°C to +85°C
Die Junction Temperature . . . . . . . . . . . . . . . . . . . . . . . . . . . . 125°C
OUT
I into V +, V -, Enable Pins . . . . . . . . . . . . . . . . . . . . . . . . . ±4mA
IN IN
CAUTION: Stresses above those listed in “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress only rating and operation of the
device at these or any other conditions above those indicated in the operational sections of this specification is not implied.
IMPORTANT NOTE: All parameters having Min/Max specifications are guaranteed. Typical values are for information purposes only. Unless otherwise noted, all tests
are at the specified temperature and are pulsed tests, therefore: T = T = T
A
J
C
Electrical Specifications V + = +5V, V - = -5V, R = 392Ω for A = 1, R = 250Ω for A = 2, R = 150Ω, T = 25°C
S
S
F
V
F
V
L
A
Unless Otherwise Specified.
PARAMETER
DESCRIPTION
CONDITIONS
MIN
TYP
MAX
UNIT
AC PERFORMANCE
BW
-3dB Bandwidth
A
= +1
= +2
= +2
1400
800
100
6000
8
MHz
MHz
MHz
V/µs
ns
V
A
V
BW1
SR
0.1dB Bandwidth
A
V
Slew Rate
V
V
= -2.5V to +2.5V, A = +2
4000
O
V
t
0.1% Settling Time
= -2.5V to +2.5V, A = -1
OUT V
S
e
Input Voltage Noise
1.7
nV/√Hz
pA/√Hz
pA/√Hz
%
N
i -
IN- Input Current Noise
IN+ Input Current Noise
Differential Gain Error (Note 1)
Differential Phase Error (Note 1)
19
N
i +
N
50
dG
dP
A
= +2
0.01
0.03
V
A
= +2
°
V
DC PERFORMANCE
V
Offset Voltage
-5
-0.5
5
mV
OS
T V
Input Offset Voltage Temperature
Coefficient
Measured from T
MIN
to T
MAX
3.52
µV/°C
C
OS
R
Transimpedance
0.5
±3
1.1
2.5
MΩ
OL
INPUT CHARACTERISTICS
CMIR
Common Mode Input Range
±3.3
V
(guaranteed by CMRR test)
Common Mode Rejection Ratio
- Input Current Common Mode Rejection
+ Input Current
CMRR
-ICMR
52
-1
57
0.7
0.7
8.5
130
1.5
66
1
dB
µA/V
µA
+I
-25
-25
50
25
25
250
IN
-I
- Input Current
µA
IN
R
Input Resistance
kΩ
IN
IN
C
Input Capacitance
pF
OUTPUT CHARACTERISTICS
V
Output Voltage Swing
Output Current
R = 150Ω to GND
±3.6
±3.8
±110
±3.8
±4.0
±160
±4.1
±4.2
±200
V
V
O
L
R = 1kΩ to GND
L
I
R = 10Ω to GND
mA
OUT
L
FN7365.3
2
December 13, 2004
EL5166, EL5167
Electrical Specifications V + = +5V, V - = -5V, R = 392Ω for A = 1, R = 250Ω for A = 2, R = 150Ω, T = 25°C
S
S
F
V
F
V
L
A
Unless Otherwise Specified. (Continued)
PARAMETER
SUPPLY
DESCRIPTION
CONDITIONS
MIN
TYP
MAX
UNIT
I
I
I
Supply Current - Enabled
No load, V = 0V
IN
7.5
1
8.5
4
9.3
25
-1
mA
µA
SON
Supply Current - Disabled
No load, V = 0V
IN
SOFF+
SOFF-
Supply Current - Disabled
No load, V = 0V
IN
-25
70
-14
50
0.2
µA
PSRR
-IPSR
Power Supply Rejection Ratio
- Input Current Power Supply Rejection
DC, V = ±4.75V to ±5.25V
dB
S
DC, V = ±4.75V to ±5.25V
-0.5
1
µA/V
S
ENABLE (EL5166 ONLY)
t
t
I
I
Enable Time
170
1.25
0
ns
µs
µA
µA
V
EN
Disable Time
DIS
CE Pin Input High Current
CE Pin Input Low Current
CE Input High Voltage for Power-down
CE Input Low Voltage for Power-down
CE = V +
-1
IHCE
ILCE
S
CE = V -
1
13
25
S
V
V
V + -1
S
IHCE
ILCE
V + -3
V
S
NOTE:
1. Standard NTSC test, AC signal amplitude = 286mV, f = 3.58MHz.
FN7365.3
3
December 13, 2004
EL5166, EL5167
Typical Performance Curves
5
4
3
4
3
2
V
V
=5V
CC
=-5V
EE
R =150Ω
L
R =368
F
R =392
F
2
1
R
=392
=93
R =186
G
G
R =662
0
1
0
F
-1
-2
-3
-4
-5
-6
R =511
F
-1
-2
-3
-4
-5
R =608
F
R
G
V
V
=5V
CC
=-5V
R =698
F
EE
R =150Ω
R =806
L
F
R
=43
G
R =392Ω
F
R =900
R =1K
F
F
100K
10M
FREQUENCY (Hz)
100M
1G
1M
100K
1M
10M
100M
1G
FREQUENCY (Hz)
FIGURE 2. FREQUENCY RESPONSE AS THE FUNCTION OF
THE GAIN
FIGURE 1. FREQUENCY RESPONSE AS THE FUNCTION OF
R
F
5
4
V
=+5V
CC
C=4.7p
V
=-5V
EE
C=4.7p
R =150Ω
L
3
C=2.5p
C=1.5p
R =R =392Ω
F
G
C=2.5p
C=1.5p
2
1
0
C=1p
-1
-2
-3
-4
-5
C=1p
C=0p
C=0
100K
1M
10M
100M
1G
100K
1M
10M
100M
1G
FREQUENCY (Hz)
FREQUENCY (Hz)
FIGURE 4. NON-INVERTING FREQUENCY RESPONSE FOR
FIGURE 3. FREQENCY RESPONSE vs C
IN
VARIOUS C - (6-PIN SOT-23)
IN
V
, V =5V
CC EE
R =220
F
G
R
=220
R =220
F
G
R
=100
1M
10M
100M
1G
2ns/DIV
FREQUENCY (Hz)
FIGURE 6. RISE AND FALL TIME (6-PIN SOT-23)
FIGURE 5. INVERTING FREQUENCY RESPONSE FOR GAIN
OF 1 AND 2
FN7365.3
December 13, 2004
4
EL5166, EL5167
Typical Performance Curves (Continued)
R =150Ω
R =150Ω
L
L
R =220Ω
2.5V
3.5V
R =300Ω
F
F
R
=220Ω
R
=300Ω
G
6.0V
3.0V
G
5.0V
2.5V
6.0V
5.0V
1M
10M
100M
1K
100K
1M
10M
100M
1G
FREQUENCY (Hz)
FREQUENCY (Hz)
FIGURE 8. INVERTING AMPLIFIER, FREQUENCY
RESPONSE AS THE FUNCTION OF V , V
FIGURE 7. FREQUENCY RESPONSE AS THE FUNCTION OF
THE POWER SUPPLY VOLTAGE
CC EE
GAIN - 1
2.5V
V
, V =2.5V
CC EE
V
, V =5V
CC EE
5.0V
5.0V
GAIN=2
6.0V
0
100K
90
10Ω
1Ω
10K
180
1K
2.5V
100mΩ
270
100
10mΩ
10K
100K
1M
10M
100M
100K
1M
10M
100M
1G
FREQUENCY (Hz)
FREQUENCY (Hz)
FIGURE 10. CLOSED LOOP OUTPUT IMPEDANCE vs
FREQUENCY (6-PIN SOT-23)
FIGURE9. TRANSIMPEDANCEMAGNITUDE AND PHASEAS
THE FUNCTION OF THE FREQUENCY
0
0
V
V
=5V
CC
V
V
=5V
CC
=-5V
10
EE
=-5V
EE
10
20
30
40
50
60
70
80
R =150Ω
R =150Ω
L
L
20 R =402Ω
F
R =402Ω
F
R
=402Ω
G
R
=402Ω
G
30
40
50
60
70
80
100
1K
10K 100K
1M
10M 100M
100
10K
1M
10M 100M
1K
100K
FREQUENCY (Hz)
FREQUENCY (Hz)
FIGURE 12. PSRR -5V
FIGURE 11. PSRR +5V
FN7365.3
December 13, 2004
5
EL5166, EL5167
Typical Performance Curves (Continued)
3
2
R =R =250Ω
F
G
1
0
-10
-20
-30
-40
-50
-60
-70
-80
0
-1
-2
-3
-4
-5
-6
-7
V
V
=5V
CC
=-5V
2.5V
EE
6.0V 5.0V
R =150Ω
L
GAIN=2
LOAD=150Ω
INPUT LEVEL=3V
3.5V
10M 100M 300M
P-P
1K
10K
100K
1M
100K
1M
10M
100M
1G
FREQUENCY (Hz)
FREQUENCY (Hz)
FIGURE 13. COMMON MODE REJECTION AS THE FUNCTION
OF THE FREQUENCY AND POWER SUPPLY
VOLTAGE
FIGURE 14. LARGE SIGNAL RESPONSE
-50
-55
-60
-65
-70
-75
-80
-85
2
V
, V =5V,
CC EE
V
, V
CC EE =
R =150Ω, A =2
L
V
±6V
1.5
1
±5V
±3V
THD
SECOND
±2.5V
THIRD
HARMONIC
HARMONIC
0.5
0
1
6
11
16
21
26
31
36
100 200 300 400 500 600 700 800 900 1000
FREQUENCY (Hz)
FREQUENCY (MHz)
FIGURE 15. T
OUT
vs FREQUENCY AND V , V
CC EE
FIGURE 16. DISTORTION vs FREQUENCY
10
-74
-76
-78
-80
-82
-84
-86
f=5MHz, R =150Ω,
f=1MHz, R =150Ω,
L
L
OP-P
0
-10
-20
-30
-40
-50
-60
-70
-80
-90
A =2, V =2V
A =2, V
V
=2V
V
O
P-P
THD
HD2
HD3
THD
HD2
HD3
7
5
6
8
9
10
11
12
5
6
7
8
9
10
11
12
TOTAL SUPPLY VOLTAGE (V)
TOTAL SUPPLY VOLTAGE (V)
FIGURE 17. HARMONIC DISTORTION vs SUPPLY VOLTAGE
FIGURE 18. HARMONIC DISTORTION vs SUPPLY VOLTAGE
FN7365.3
6
December 13, 2004
EL5166, EL5167
Typical Performance Curves (Continued)
-50
-55
-60
-65
-70
-75
-80
-50
f=20MHz,
R =150Ω,
f=10MHz,
L
-55
-60
-65
-70
-75
-80
-85
-90
R =150Ω,
L
A =2
V
A =2
V
O
V
=2V
P-P
O
V
=2V
P-P
THD
SECOND
THD
SECOND
HARMONIC
THIRD
HARMONIC
HARMONIC
THIRD
HARMONIC
5
6
7
8
9
10
11
12
5
6
7
8
9
10
11
12
TOTAL SUPPLY VOLTAGE (V)
TOTAL SUPPLY VOLTAGE (V)
FIGURE 20. DISTORTION vs POWER SUPPLY VOLTAGE (EL5166)
FIGURE 19. DISTORTION vs POWER SUPPLY VOLTAGE
FIGURE 21. TURN ON TIME (EL5166)
FIGURE 22. TURN OFF TIME (EL5166)
JEDEC JESD51-7 HIGH EFFECTIVE THERMAL
CONDUCTIVITY TEST BOARD
1.4
8.5
8.4
8.3
8.2
8.1
8
1.2
1
0.8
0.6
0.4
0.2
0
909mW
435mW
I
S
SO8
=110°C/W
θ
JA
7.9
7.8
7.7
7.6
7.5
7.4
I -
S
SOT23-5/6
=230°C/W
θ
JA
25
AMBIENT TEMPERATURE (°C)
2.5
3
3.5
4
4.5
5
5.5
6
0
50
75 85 100
125
150
SUPPLY VOLTAGE (V)
FIGURE 23. SUPPLY CURRENT vs SUPPLY VOLTAGE (EL5166)
FIGURE 24. PACKAGE POWER DISSIPATION vs AMBIENT
TEMPERATURE
FN7365.3
December 13, 2004
7
EL5166, EL5167
Typical Performance Curves (Continued)
JEDEC JESD51-3 LOW EFFECTIVE THERMAL
CONDUCTIVITY TEST BOARD
1
0.9
0.8
0.7
0.6
0.5
0.4
0.3
0.2
0.1
0
625mW
SO8
=160°C/W
θ
JA
391mW
SOT23-5/6
=256°C/W
θ
JA
0
25
50
75 85 100
125
150
AMBIENT TEMPERATURE (°C)
FIGURE 25. PACKAGE POWER DISSIPATION vs AMBIENT TEMPERATURE
FN7365.3
8
December 13, 2004
EL5166, EL5167
Pin Descriptions
PIN
8-PIN SO
6-PIN SOT-23 5-PIN SOT-23
NAME
FUNCTION
Not connected
EQUIVALENT CIRCUIT
1, 5
2
NC
V +
S
4
4
IN-
Inverting input
IN+
IN-
V -
S
CIRCUIT 1
3
4
6
3
2
1
3
2
1
IN+
VS-
Non-inverting input
Negative supply
Output
(See circuit 1)
OUT
V +
S
OUT
V -
S
CIRCUIT 2
7
8
6
5
5
VS+
CE
Positive supply
Chip enable
V +
S
CE
V -
S
CIRCUIT 3
Power Supply Bypassing and Printed Circuit
Board Layout
Applications Information
Product Description
As with any high frequency device, good printed circuit
board layout is necessary for optimum performance. Low
impedance ground plane construction is essential. Surface
mount components are recommended, but if leaded
components are used, lead lengths should be as short as
possible. The power supply pins must be well bypassed to
reduce the risk of oscillation. The combination of a 4.7µF
tantalum capacitor in parallel with a 0.01µF capacitor has
been shown to work well when placed at each supply pin.
The EL5166 and EL5167 are current-feedback operational
amplifiers that offers a wide -3dB bandwidth of 1.4GHz and a
low supply current of 8.5mA per amplifier. The EL5166 and
EL5167 work with supply voltages ranging from a single 5V
to 10V and they are also capable of swinging to within 1V of
either supply on the output. Because of their current-
feedback topology, the EL5166 and EL5167 do not have the
normal gain-bandwidth product associated with voltage-
feedback operational amplifiers. Instead, their -3dB
bandwidth remains relatively constant as closed-loop gain is
increased. This combination of high bandwidth and low
power, together with aggressive pricing make the EL5166
and EL5167 ideal choices for many low-power/high-
bandwidth applications such as portable, handheld, or
battery-powered equipment.
For good AC performance, parasitic capacitance should be
kept to a minimum, especially at the inverting input. (See the
Capacitance at the Inverting Input section) Even when
ground plane construction is used, it should be removed
from the area near the inverting input to minimize any stray
capacitance at that node. Carbon or Metal-Film resistors are
acceptable with the Metal-Film resistors giving slightly less
peaking and bandwidth because of additional series
FN7365.3
9
December 13, 2004
EL5166, EL5167
inductance. Use of sockets, particularly for the SO package,
should be avoided if possible. Sockets add parasitic
inductance and capacitance which will result in additional
peaking and overshoot.
it becomes possible to reduce the value of R below the
F
specified 250Ω and still retain stability, resulting in only a
slight loss of bandwidth with increased closed-loop gain.
Supply Voltage Range and Single-Supply
Operation
Disable/Power-Down
The EL5166 amplifier can be disabled placing its output in a
high impedance state. When disabled, the amplifier supply
current is reduced to 13µA. The EL5166 is disabled when its
CE pin is pulled up to within 1V of the positive supply.
Similarly, the amplifier is enabled by floating or pulling its CE
pin to at least 3V below the positive supply. For ±5V supply,
this means that an EL5166 amplifier will be enabled when
CE is 2V or less, and disabled when CE is above 4V.
Although the logic levels are not standard TTL, this choice of
logic voltages allows the EL5166 to be enabled by tying CE
to ground, even in 5V single supply applications. The CE pin
can be driven from CMOS outputs.
The EL5166 and EL5167 have been designed to operate
with supply voltages having a span of greater than 5V and
less than 10V. In practical terms, this means that the EL5166
and EL5167 will operate on dual supplies ranging from
±2.5V to ±5V. With single-supply, they will operate from 5V to
10V.
As supply voltages continue to decrease, it becomes
necessary to provide input and output voltage ranges that
can get as close as possible to the supply voltages. The
EL5166 and EL5167 have an input range which extends to
within 1.8V of either supply. So, for example, on ±5V
supplies, the EL5166 and EL5167 have an input range
which spans ±3.2V. The output range of the EL5166 and
EL5167 is also quite large, extending to within 1V of the
supply rail. On a ±5V supply, the output is therefore capable
of swinging from -4V to +4V.
Capacitance at the Inverting Input
Any manufacturer’s high-speed voltage- or current-feedback
amplifier can be affected by stray capacitance at the
inverting input. For inverting gains, this parasitic capacitance
has little effect because the inverting input is a virtual
ground. But for non-inverting gains, this capacitance (in
conjunction with the feedback and gain resistors) creates a
pole in the feedback path of the amplifier. This pole, if low
enough in frequency, has the same destabilizing effect as a
zero in the forward open-loop response. The use of large
value feedback and gain resistors exacerbates the problem
by further lowering the pole frequency (increasing the
possibility of oscillation).
Video Performance
For good video performance, an amplifier is required to
maintain the same output impedance and the same
frequency response as DC levels are changed at the
output. This is especially difficult when driving a standard
video load of 150Ω, because of the change in output
current with DC level. Previously, good differential gain
could only be achieved by running high idle currents
through the output transistors (to reduce variations in
output impedance.) These currents were typically
comparable to the entire 8.5mA supply current of each
EL5166 and EL5167 amplifier. Special circuitry has been
incorporated in the EL5166 and EL5167 to reduce the
variation of output impedance with current output. This
results in dG and dP specifications of 0.01% and 0.03°,
while driving 150Ω at a gain of 2.
The EL5166 and EL5167 frequency responses are
optimized with the resistor values in Figure 3. With the high
bandwidth of these amplifiers, these resistor values might
cause stability problems when combined with parasitic
capacitance, thus ground plane is not recommended around
the inverting input pin of the amplifier.
Feedback Resistor Values
Output Drive Capability
The EL5166 and EL5167 have been designed and specified
at a gain of +2 with R approximately 392Ω. This value of
In spite of their low 8.5mA of supply current, the EL5166 and
EL5167 are capable of providing a minimum of ±110mA of
output current. With so much output drive, the EL5166 and
EL5167 are capable of driving 50Ω loads to both rails,
making them an excellent choice for driving isolation
transformers in telecommunications applications.
F
feedback resistor gives 800MHz of -3dB bandwidth at A = 2
V
with about 0.5dB of peaking. Since the EL5166 and EL5167
are current-feedback amplifiers, it is also possible to change
the value of R to get more bandwidth. As seen in the curve
F
of Frequency Response for Various R and R , bandwidth
F
G
and peaking can be easily modified by varying the value of
the feedback resistor.
Driving Cables and Capacitive Loads
When used as a cable driver, double termination is always
recommended for reflection-free performance. For those
applications, the back-termination series resistor will
decouple the EL5166 and EL5167 from the cable and allow
extensive capacitive drive. However, other applications may
have high capacitive loads without a back-termination
resistor. In these applications, a small series resistor (usually
Because the EL5166 and EL5167 are current-feedback
amplifiers, their gain-bandwidth product is not a constant for
different closed-loop gains. This feature actually allows the
EL5166 and EL5167 to maintain reasonable constant -3dB
bandwidth for different gains. As gain is increased,
bandwidth decreases slightly while stability increases. Since
the loop stability is improving with higher closed-loop gains,
FN7365.3
10
December 13, 2004
EL5166, EL5167
between 5Ω and 50Ω) can be placed in series with the
output to eliminate most peaking. The gain resistor (R ) can
G
then be chosen to make up for any gain loss which may be
created by this additional resistor at the output. In many
cases it is also possible to simply increase the value of the
feedback resistor (R ) to reduce the peaking.
F
Current Limiting
The EL5166 and EL5167 have no internal current-limiting
circuitry. If the output is shorted, it is possible to exceed the
Absolute Maximum Rating for output current or power
dissipation, potentially resulting in the destruction of the
device.
Power Dissipation
With the high output drive capability of the EL5166 and
EL5167, it is possible to exceed the 125°C Absolute
Maximum junction temperature under certain very high load
current conditions. Generally speaking when R falls below
L
about 25Ω, it is important to calculate the maximum junction
temperature (T
) for the application to determine if
JMAX
power supply voltages, load conditions, or package type
need to be modified for the EL5166 and EL5167 to remain in
the safe operating area. These parameters are calculated as
follows:
T
= T
+ (θ × n × PD
)
MAX
JMAX
MAX
JA
where:
T
= Maximum ambient temperature
MAX
= Thermal resistance of the package
θ
JA
n = Number of amplifiers in the package
PD = Maximum power dissipation of each amplifier in
MAX
the package
PD for each amplifier can be calculated as follows:
MAX
V
OUTMAX
R
L
----------------------------
PD
= (2 × V × I
) + (V – V ) ×
OUTMAX
MAX
S
SMAX
S
where:
V = Supply voltage
S
I
= Maximum supply current of 1A
SMAX
V
= Maximum output voltage (required)
OUTMAX
R = Load resistance
L
FN7365.3
11
December 13, 2004
EL5166, EL5167
Typical Application Circuits
0.1µF
+5V
250Ω
250Ω
IN+
V +
S
0.1µF
OUT
EL5166
V -
+5V
IN+
IN-
S
0.1µF
V +
S
OUT
-5V
EL5166
IN-
250Ω
5Ω
5Ω
V -
S
0.1µF
250Ω
250Ω
-5V
0.1µF
V
OUT
+5V
IN+
0.1µF
+5V
IN+
V +
S
OUT
EL5166
V +
S
V
IN-
IN
OUT
V -
V
EL5166
S
OUT
IN-
0.1µF
V -
S
-5V
0.1µF
250Ω
250Ω
-5V
V
IN
FIGURE 26. INVERTING 200mA OUTPUT CURRENT
DISTRIBUTION AMPLIFIER
FIGURE 27. FAST-SETTLING PRECISION AMPLIFIER
0.1µF
+5V
0.1µF
+5V
IN+
IN+
V +
V +
S
S
OUT
OUT
EL5166
V -
EL5166
V -
IN-
IN-
S
S
0.1µF
0.1µF
-5V
-5V
0.1µF
250Ω
120Ω
120Ω
250Ω
250Ω
V
V
+
OUT
0.1µF
1kΩ
1kΩ
0.1µF
+5V
IN+
240Ω
+5V
IN+
V +
0.1µF
S
OUT
V +
S
-
EL5166
V -
OUT
IN-
OUT
V
EL5166
OUT
S
IN-
0.1µF
V -
S
-5V
0.1µF
-5V
250Ω
250Ω
V
IN
250Ω
250Ω
RECEIVER
TRANSMITTER
FIGURE 28. DIFFERENTIAL LINE DRIVER/RECEIVER
FN7365.3
December 13, 2004
12
EL5166, EL5167
SO Package Outline Drawing
FN7365.3
13
December 13, 2004
EL5166, EL5167
SOT-23 Package Outline Drawing
FN7365.3
14
December 13, 2004
EL5166, EL5167
SC-70 Package Outline Drawing
D
P5.049
VIEW C
5 LEAD SMALL OUTLINE TRANSISTOR PLASTIC PACKAGE
INCHES MILLIMETERS
MIN
e1
SYMBOL
MAX
0.043
0.004
0.039
0.012
0.010
0.009
0.009
0.085
0.094
0.053
MIN
0.80
0.00
0.80
0.15
0.15
0.08
0.08
1.85
1.80
1.15
MAX
1.10
0.10
1.00
0.30
0.25
0.22
0.20
2.15
2.40
1.35
NOTES
5
1
4
A
A1
A2
b
0.031
0.000
0.031
0.006
0.006
0.003
0.003
0.073
0.071
0.045
-
-
-
-
E
C
L
C
L
E1
2
3
b
b1
c
e
6
6
3
-
C
L
c1
D
0.20 (0.008) M
C
C
C
L
E
E1
e
3
-
SEATING
PLANE
0.0256 Ref
0.0512 Ref
0.010 0.018
0.65 Ref
1.30 Ref
0.26 0.46
A2
A1
A
e1
L
-
-C-
4
-
L1
L2
0.017 Ref.
0.420 Ref.
0.15 BSC
0.10 (0.004)
C
0.006 BSC
o
o
o
o
0
8
0
8
-
α
N
b
WITH
5
5
5
PLATING
b1
R
0.004
0.004
-
0.10
0.15
-
R1
0.010
0.25
c
c1
Rev. 2 9/03
NOTES:
BASE METAL
1. Dimensioning and tolerances per ASME Y14.5M-1994.
2. Package conforms to EIAJ SC70 and JEDEC MO-203AA.
4X θ1
3. Dimensions D and E1 are exclusive of mold flash, protrusions,
or gate burrs.
R1
4. Footlength L measured at reference to gauge plane.
5. “N” is the number of terminal positions.
R
6. These Dimensions apply to the flat section of the lead between
0.08mm and 0.15mm from the lead tip.
GAUGE PLANE
SEATING
PLANE
7. Controlling dimension: MILLIMETER. Converted inch dimen-
sions are for reference only.
L
C
α
L2
L1
4X θ1
VIEW C
NOTE: The package drawing shown here may not be the latest version. To check the latest revision, please refer to the Intersil website at
<http://www.intersil.com/design/packages/index.asp>
All Intersil U.S. products are manufactured, assembled and tested utilizing ISO9000 quality systems.
Intersil Corporation’s quality certifications can be viewed at www.intersil.com/design/quality
Intersil products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design, software and/or specifications at any time without
notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be accurate and
reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result
from its use. No license is granted by implication or otherwise under any patent or patent rights of Intersil or its subsidiaries.
For information regarding Intersil Corporation and its products, see www.intersil.com
FN7365.3
15
December 13, 2004
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