ILC7080AIM5285X [FAIRCHILD]
Fixed Positive LDO Regulator, 2.85V, 0.15V Dropout, CMOS, PDSO5, PLASTIC, SOT-23, 5 PIN;型号: | ILC7080AIM5285X |
厂家: | FAIRCHILD SEMICONDUCTOR |
描述: | Fixed Positive LDO Regulator, 2.85V, 0.15V Dropout, CMOS, PDSO5, PLASTIC, SOT-23, 5 PIN 光电二极管 输出元件 调节器 |
文件: | 总16页 (文件大小:569K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
www.fairchildsemi.com
ILC7080/81
50/100mA SOT-23 CMOS RF LDO™ Regulators
Features
Description
• Ultra low 1mV dropout per 1mA load
• 1% output voltage accuracy
• Uses low ESR ceramic output capacitor to minimize noise
and output ripple
The ILC7080/81 are 50 or 100mA low dropout (LDO)
voltage regulators designed to provide a high performance
solution to low power systems.
• Only 100µA ground current at 100mA load
• Ripple rejection up to 85dB at 1kHz, 60dB at 1MHz
• Less than 80µVRMS noise at BW = 100Hz to 100kHz
• Excellent line and load transient response
• Over current / over temperature protection
• Guaranteed up to 80/150mA output current
• Industry standard five lead SOT-23 package
• Fixed 2.5V, 2.6V, 2.7V, 2.8V, 2.85V, 2.9V, 3.0, 3.1V, 3.3V,
3.6V, 4.7V, 5.0V and adjustable output (ILC7081 only)
voltage options
The devices offer a typical combination of low dropout and
low quiescent current expected of CMOS parts, while
uniquely providing the low noise and high ripple rejection
characteristics usually only associated with bipolar LDO
regulators.
The devices have been optimized to meet the needs of
modern wireless communications design; Low noise, low
dropout, small size, high peak current, high noise immunity.
• Metal mask option available for custom voltages between
2.5 to 5.1V
The ILC7080/81 are designed to make use of low cost
ceramic capacitors while outperforming other devices that
require tantalum capacitors.
Applications
• Cellular phones
• Wireless communicators
• PDAs / palmtops / organizers
• Battery powered portable electronics
Typical Applications
VOUT
5
1
4
3
SOT-23-5
COUT
CNOISE
ILC7080
ILC7081
2
VIN
ON
OFF
REV. 1.0.7 4/3/03
ILC7080/81
Pin Assignments
CNOISE
4
VADJ
4
VOUT
VOUT
5
5
SOT23-5
SOT23-5
ILC7080-xx
ILC7081-xx
ILC7081-ADJ
1
2
3
1
2
3
VIN
VIN
GND
ON
GND
ON
OFF
OFF
Adjustable Voltage Option
Fixed Voltage Option
Pin Description ILC7080/81-xx (fixed voltage version)
Pin Number Pin Name
Pin Description
1
2
3
4
VIN
Connect direct to supply
GND
Ground pin. Local ground for CNOISE and COUT.
ON/OFF
CNOISE
By applying less than 0.4V to this pin the device will be turned off.
Optional noise bypass capacitor may be connected between this pin and GND (pin
2). Do not connect CNOISE directly to the main power ground plane.
5
VOUT
Output Voltage. Connect COUT between this pin and GND (pin 2).
Pin Description ILC7081-ADJ (adjustable voltage version)
Pin Number Pin Name
Pin Description
1
2
3
4
VIN
GND
Connect direct to supply
Ground pin. Local ground for CNOISE and COUT
.
ON/OFF
VADJ
By applying less than 0.4V to this pin the device will be turned off.
Voltage feedback pin to set the adjustable output voltage. Do not connect a
capacitor to this pin.
5
VOUT
Output Voltage. Connect COUT between this pin and GND (pin 2).
Absolute Maximum Ratings (Note 1)
Parameter
Symbol
Ratings
Units
Input voltage
On/Off Input voltage
VIN
VON/OFF
-0.3 to +13.5
-0.3 to VIN
V
Output Current
Output voltage
IOUT
VOUT
PD
Short circuit protected
-0.3 to VIN+0.3
mA
V
Package Power Dissipation
(SOT-23-5)
250
mW
(Internally Limited)
Maximum Junction Temp Range
Storage Temperature
TJ(max)
TSTG
TA
-40 to +150
-40 to +125
-40 to +85
333
°C
°C
Operating Ambient Temperature
Package Thermal Resistance
°C
qJA
°C/W
Recommended Operating Conditions
Parameter
Min.
Typ.
Max.
13
Units
Input Voltage
VOUT+VDO
-40
VOUT+1
V
Operating Ambient Temperature
+85
°C
2
REV. 1.0.7 4/3/03
ILC7080/81
Electrical Characteristics ILC7080/81AIM5
Unless otherwise specified, all limits are at TA=25°C; VIN = VOUT(NOM) +1V, IOUT = 1mA, COUT = 1µF, VON/OFF = 2V.
Boldface type denotes specifications which apply over the specified operating temperature range.
Parameter
Symbol
Conditions
Min.
Typ.
Max. Units
Input voltage Range
VIN
2
13
V
Output voltage
IOUT = 1mA
1mA < IOUT < 100mA
1mA < IOUT < 100mA
-1
-1.5
-3.5
VOUT(NOM)
+1
1.5
+3.5
%
VOUT
Feedback Voltage
(ADJ version)
1.215
1.202
1.240
0.007
1.265
1.278
0.014
0.032
V
VADJ
∆VOUT
Line Regulation
/
VOUT(NOM) +1V < VIN < 12V
%/V
(VOUT*∆VIN)
Dropout voltage
(Note 3)
7080/81
IOUT= 0mA
(Note 4)
OUT = 10mA
0.1
10
1
2
25
mV
I
35
7080 only
7081 only
IOUT = 50mA
IOUT = 50mA
IOUT = 100mA
IOUT = 150mA
IOUT = 0mA
110
50
125
150
75
100
150
200
225
300
VIN - VOUT
100
150
95
Ground Pin Current
7080/81
200
µA
220
I
OUT = 10mA
100
100
100
115
0.1
220
240
220
240
IOUT = 50mA
IOUT = 100mA
IOUT = 150mA
IGND
7081 only
240
260
260
280
Shutdown (OFF)
Current
VON/OFF = 0V
2
µA
V
ION/OFF
VON/OFF
IIN( ON/OFF)
IOUT(peak)
eN
ON/OFF Input
Voltage
High = Regulator On
Low = Regulator Off
2.0
0.6
ON/OFF Pin Input
Current
VON/OFF = 0.6V, regulator OFF
VON/OFF = 2V, regulator ON
0.3
1
µA
Peak Output
Current (Note 4)
VOUT > 0.95VOUT(NOM), tpw=2ms
400
500
mA
µVRMS
dB
Output Noise
Voltage (RMS)
BW=300Hz to 50kHz, CNOISE=0.01µF
80
Ripple Rejection
COUT = 4.7µF,
IOUT = 100mA
Freq. = 1kHz
Freq. = 10kHz
Freq. = 1MHz
85
70
60
4
∆VOUT/∆VIN
∆VOUT(line)
Dynamic Line
Regulation
VIN: VOUT(NOM)+1V to VOUT(NOM)+2V,
tr/tf = 2µs; IOUT = 100mA
mV
Dynamic Load
Regulation
IOUT: 0 to 100mA;
d(IOUT)/dt = 100mA/µs with
COUT = 0.47µF with
COUT = 2.2µF
50
∆VOUT(load)
mV
mA
25
Short Circuit Current
REV. 1.0.7 4/3/03
ISC
VOUT = 0V
600
3
ILC7080/81
Notes:
1. Absolute maximum ratings indicate limits which when exceeded may result in damage to the component. Electrical
specifications do not apply when operating the device outside of its rated operating conditions.
2. Specified Min/Max limits are production tested or guaranteed through correlation based on statistical control methods.
Measurements are taken at constant junction temperature as close to ambient as possible using low duty pulse testing.
3. Dropout voltage is defined as the input to output differential voltage at which the output voltage drops 2% below the nominal
value measured with a 1V differential.
4. Guaranteed by design.
Operations
The ILC7080/81 LDO design is based on an advanced cir-
cuit configuration for which patent protection has been
applied. Typically it is very difficult to drive a capacitive out-
put with an amplifier. The output capacitance produces a
pole in the feedback path, which upsets the carefully tailored
dominant pole of the internal amplifier. Traditionally the
pole of the output capacitor has been “eliminated” by reduc-
ing the output impedance of the regulator such that the pole
of the output capacitor is moved well beyond the gain band-
width product of the regulator. In practice, this is difficult to
do and still maintain high frequency operation. Typically the
output impedance of the regulator is not simply resistive,
such that the reactive output impedance interacts with the
reactive impedance of the load resistance and capacitance.
In addition, it is necessary to place the dominant pole of the
circuit at a sufficiently low frequency such that the gain of
the regulator has fallen below unity before any of the com-
plex interactions between the output and the load occur. The
ILC7080/81 does not try to eliminate the output pole, but
incorporates it into the stability scheme. The load and output
capacitor forms a pole, which rolls off the gain of the regula-
tor below unity. In order to do this the output impedance of
the regulator must be high, looking like a current source.
The output stage of the regulator becomes a transconduc-
tance amplifier, which converts a voltage to a current with a
substantial output impedance. The circuit which drives the
transconductance amplifier is the error amplifier, which
compares the regulator output to the band gap reference and
produces an error voltage as the input to the transconduc-
tance amplifier. The error amplifier has a dominant pole at
low frequency and a “zero” which cancels out the effects of
the pole. The zero allows the regulator to have gain out to the
frequency where the output pole continues to reduce the gain
to unity. The configuration of the poles and zero are shown in
figure 1.
A block diagram of the regulator circuit used in the
ILC7080/81 is shown in figure 2, which shows the input-to-
output isolation and the cascaded sequence of amplifiers that
implement the pole-zero scheme outlined above.
The ILC7080/81 were designed in a CMOS process with
some minor additions, which allow the circuit to be used at
input voltages up to 13V. The resulting circuit exceeds the
frequency response of traditional bipolar circuits. The
ILC7080/81 is very tolerant of output load conditions with
the inclusion of both short circuit and thermal overload
protection. The device has a very low dropout voltage,
typically a linear response of 1mV per milliamp of load
current, and none of the quasi-saturation characteristics of a
bipolar output device. All the good features of the frequency
response and regulation are valid right to the point where the
regulator goes out of regulation in a 4mV transition region.
Because there is no base drive, the regulator is capable of
providing high current surges while remaining in regulation.
This is shown in the high peak current of 500mA which
allows for the ILC7080/81 to be used in systems that require
short burst mode operation.
DOMINANT POLE
85 dB
OUTPUT POLE
COMPENSATING
ZERO
UNITY GAIN
Instead of powering the critical circuits from the unregulated
input voltage, the CMOS RF LDO powers the internal
circuits such as the bandgap, the error amplifier and most of
the transconductance amplifier from the boot strapped regu-
lated output voltage of the regulator. This technique offers
extremely high ripple rejection and excellent line transient
response.
FREQUENCY
Figure 1. LC7080/81 RF LDO frequency response
4
REV. 1.0.7 4/3/03
ILC7080/81
INTERNAL VDD
VIN
CNOISE
BANDGAP
REFERENCE
VREF
ERROR
AMPLIFIER
TRANS-
CONDUCTANCE
AMPLIFIER
VOUT
FEEDBACK
GND
ON/OFF
Figure 2. ILC7080/81 RF LDO regulator block diagram
Shutdown (ON/OFF) Operation
Adjustable Output Voltage
The ILC7080/81 output can be turned off by applying 0.4V
or less to the device’s ON/OFF pin (pin 3). In shutdown
mode, the ILC7080/81 draws less than 1µA quiescent cur-
rent. The output of the ILC7081 is enabled by applying 2V to
13V at the ON/OFF pin. In applications where the ILC7080/
81 output will always remain enabled, the ON/OFF pin may
be connected to VIN (pin 1). The ILC7080/81’s shutdown
circuitry includes hysteresis, as such the device will operate
properly even if a slow moving signal is applied to the ON/
OFF pin.
Figure 3 shows how an adjustable output voltage can be
easily achieved using ILC7081-ADJ. The output voltage,
VOUT is given by the following equation:
VOUT = 1.24V x (R1/R2 + 1)
R2
R1
VOUT
VADJ
SOT23-5
ILC7081-ADJ
2
5
1
4
3
Short Circuit Protection
COUT
VIN
CIN
The ILC7080/81 output can withstand momentary short
circuit to ground. Moreover, the regulator can deliver very
high output peak current due to its 1A instantaneous short
circuit current capability.
ON
Thermal Protection
OFF
The ILC7080/81 also includes a thermal protection circuit
which shuts down the regulator when die temperature
exceeds 150˚C due to overheating. In thermal shutdown,
once the die temperature cools to below 140˚C, the regulator
is enabled. If the die temperature is excessive due to high
package power dissipation, the regulator’s thermal circuit
will continue to pulse the regulator on and off. This is called
thermal cycling.
Figure 3. Application circuit for adjustable output voltage
For best results, a resistor value of 470kΩ or less may be
used for R2. The output voltage can be programmed from
2.5V to 12V.
Note: An external capacitor should not be connected to the
adjustable feedback pin (pin 4). Connecting an external
capacitor to pin 4 may cause regulator instability and lead to
oscillations.
Excessively high die temperature may occur due to high
differential voltage across the regulator or high load current
or high ambient temperature or a combination of all three.
Thermal protection protects the regulator from such fault
conditions and is a necessary requirement in today’s designs.
In normal operation, the die temperature should be limited to
under 150˚C.
REV. 1.0.7 4/3/03
5
ILC7080/81
output voltage by a couple of hundred milivolts then the regula-
tor may be damaged. This condition must be avoided. In many
applications a large value input capacitor, CIN, will hold VIN
higher thanVOUT and decay slower thanVOUT when the LDO is
powered off.
Maximum Output Current
The maximum output current available from the ILC7080/81
is limited by the maximum package power dissipation as
well as the device’s internal current limit. For a given ambi-
ent temperature, TA, the maximum package power dissipa-
tion is given by:
Output Capacitor Selection
PD(max) = (TJ(max) - TA) / θJA
Fairchild strongly recommends the use of low ESR (equivalent
series resistance) ceramic capacitors for COUT and CNOISE. The
ILC7080/81 is stable with low ESR capacitor (as low as zero
Ω). The value of the output capacitor should be 1µF or higher.
Either ceramic chip or a tantalum capacitor may be used at the
output.
where TJ(max) = 150˚C is the maximum junction temperature
and θJA = 333˚C/W is the package thermal resistance. For
example at TA = 85˚C ambient temperature, the maximum
package power dissipation is;
PD(max) = 195mW.
Use of ceramic chip capacitors offer significant advantages over
tantalum capacitors. A ceramic capacitor is typically consider-
ably cheaper than a tantalum capacitor, it usually has a smaller
footprint, lower height, and lighter weight than a tantalum
capacitor. Furthermore, unlike tantalum capacitors which are
polarized and can be damaged if connected incorrectly, ceramic
capacitors are non-polarized. Low value ceramic chip capacitors
with X7R dielectric are available in the 100pF to 4.7µF range,
while high value capacitors withY5V dielectric are available in
the 2200pF to 22µF range. Evaluate carefully before using
capacitors withY5V dielectric because their ESR increases sig-
nificantly at cold temperatures. Figure 10 shows a list of recom-
mended ceramic capacitors for use at the output of ILC7080/81.
The maximum output current can be calculated from the fol-
lowing equation:
IOUT(max) < PD(max) / (VIN - VOUT)
For example at VIN = 6V, VOUT = 5V and TA = 85˚C, the
maximum output current is IOUT(max) < 195mA. At higher
output current, the die temperature will rise and cause the
thermal protection circuit to be enabled.
Application Hints
Figure 4 shows the typical application circuit for the
ILC7080/81.
Note: If a tantalum output capacitor is used then for stable
operation we recommend a low ESR tantalum capacitor with
maximum rated ESR at or below 0.4Ω. Low ESR tantalum
capacitors, such as the TPS series from AVX Corporation
(www.avxcorp.com) or the T495 series from Kemet
(www.kemet.com) may be used.
VOUT
SOT23-5
5
1
4
3
CNOISE
In applications where a high output surge current can be
expected, use a high value but low ESR output capacitor for
superior load transient response. The ILC7080/81 is stable with
no load.
ILC7080
ILC7081
COUT
VIN
2
Noise Bypass Capacitor
ON
In low noise applications, the self noise of the ILC7080/81 can
be decreased further by connecting a capacitor from the noise
bypass pin (pin 4) to ground (pin 2). The noise bypass pin is a
high impedance node as such, care should be taken in printed
circuit board layout to avoid noise pick-up from external
sources. Moreover, the noise bypass capacitor should have low
leakage.
OFF
Figure 4. Basic application circuit for fixed output voltage
Input Capacitor
An input capacitor CIN of value 1µF or larger should be con-
nected from VIN to the main ground plane. This will help to fil-
ter supply noise from entering the LDO. The input capacitor
should be connected as close to the LDO regulator input pin as
is practical. Using a high-value input capacitor will offer supe-
rior line transient response as well as better power supply ripple
rejection. A ceramic or tantalum capacitor may be used at the
input of the LDO regulator.
Noise bypass capacitors with a value as low as 470pF may be
used. However, for optimum performance, use a 0.01µF or
larger, ceramic chip capacitor. Note that the turn on and turn off
response of the ILC7080/81 is inversely proportional to the
value of the noise bypass capacitor. For fast turn on and turn off,
use a small value noise bypass capacitor. In applications were
exceptionally low output noise is not required, consider omit-
ting the noise bypass capacitor altogether.
Note that there is a parasitic diode from the LDO regulator out-
put to the input. If the input voltage swings below the regulator’s
6
REV. 1.0.7 4/3/03
ILC7080/81
The Effects of ESR (Equivalent
Series Resistance)
Printed Circuit Board Layout
Guidelines
The ESR of a capacitor is a measure of the resistance due to the
leads and the internal connections of the component. Typically
measured in mΩ (milli-ohms) it can increase to ohms in some
cases.
As was mentioned in the previous section, to take full advan-
tage of any high performance LDO regulator requires paying
careful attention to grounding and printed circuit board
(PCB) layout.
Wherever there is a combination of resistance and current, volt-
ages will be present. The control functions of LDOs use two
voltages in order to maintain the output precisely; VOUT and
IOUT
VOUT
I2
RPCB
RPCB
ESR
RPCB
SOT-23-5
VREF
.
I1
5
1
4
3
CNOISE
COUT
With reference to the block diagram in figure 2, VOUT is fed
back to the error amplifier and is used as the supply voltage for
the internal components of the 7080/81. So any change in VOUT
will cause the error amplifier to try to compensate to maintain
VOUT at the set level and noise on VOUT will be reflected into
ILC7080
ILC7081
VIN
VIN
2
RPCB
the supply of each internal circuit. The reference voltage, VREF
,
RPCB
ON
is influenced by the CNOISE pin. Noise into this pin will add to
the reference voltage and be fed through the circuit. These fac-
tors will not cause a problem if some simple steps are taken.
Figure 5 shows where these added ESR resistances are present
in the typical LDO circuit.
OFF
Figure 6. Inherent PCB resistance
Figure 7 shows the effects of poor grounding and PCB
layout caused by the ESR and PCB resistances and the
accumulation of current flows.
IOUT
VOUT
R*
Note particularly that during high output load current, the
LDO regulator’s ground pin and the ground return for COUT
and CNOISE are not at the same potential as the system
ground. This is due to high frequency impedance caused by
PCB’s trace inductance and DC resistance. The current loop
between COUT, CNOISE and the LDO regulator’s ground pin
will degrade performance of the LDO.
IC
RC
SOT-23-5
5
1
4
3
COUT
CNOISE
ILC7080
ILC7081
VIN
2
RF LDOTM
Regulator
ON
R*
VOUT
CIN
OFF
5
4
ILC7080/81
Figure 5. ESR in COUT and CNOISE
SOT23-5
COUT
1
2
3
With this in mind low ESR components will offer better perfor-
mance as LDOs may be exposed to large transients of output
voltage, and current flows through the capacitors in order to fil-
ter these transient swings. ESR is less of a problem with CIN as
the voltage fluctuations at the input will be filtered by the LDO.
VIN
CIN
ON/OFF
GND2
GND1
GND3
ILOAD
ILOAD
True GND
(0V)
+I
C
OUT
However, being aware of these current flows, there is also
another potential source of induced voltage noise from the resis-
tance inherent in the PCB trace. Figure 6 shows where the addi-
tive resistance of the PCB can manifest itself. Again these
resistances may be very small, but a summation of several cur-
rents can develop detectable voltage ripple and will be amplified
by the LDO. Particularly the accumulation of current flows in
the ground plane can develop significant voltages unless care is
taken.
+I
+I
C
NOISE
GND
Figure 7. Effects of poor circuit layout
Figure 8 shows an optimum schematic. In this schematic,
high output surge current has little effect on the ground cur-
rent and noise bypass current return of the LDO regulator.
Note that the key difference here is that COUT and CNOISE are
directly connected to the LDO regulator’s ground pin. The
LDO is then separately connected to the main ground plane
and returned to a single point system ground.
With a degree of care, the ILC7080/81 will yield outstanding
performance.
REV. 1.0.7 4/3/03
7
ILC7080/81
The layout of the LDO and its external components are also
based on some simple rules to minimize EMI and output
voltage ripple.
VOUT
CNOISE
0.01µF
COUT
4.7µF
5
1
4
3
L
O
A
D
ILC7080
SOT23-5
ESR<0.5Ω
2
VIN
ON/OFF
DC/DC
Converter
VBATT
CIN
+
1µF
GND
Ground Plane
Ground Plane Ground Plane
Ground Plane
Figure 9. Recommended application circuit layout
(not drawn to scale).
Figure 8. Recommended application circuit schematic
Note: ground plane is bottom layer of PCB and connects to
top layer ground connections through vias.
Evaluation Board Parts List For Printed Circuit Board Shown Above
Label
U1
Part Number
ILC7081AIM5-30
69190-405
Manufacturer
Fairchild Semi.
Berg
Description
100mA RF LDOTM regulator
J1
Connector, four position header
CIN
GRM40 Y5V 105Z16
ECU-V1H103KBV
GRM42-6X5R475K10
muRata
Ceramic capacitor, 1µF,16V, SMT (size 0805)
Ceramic capacitor, 0.01µF,16V, SMT (size 0603)
Ceramic capacitor, 4.7µF,16V, SMT (size 1206)
CNOISE
COUT
Panasonic
muRata
Grounding Recommendations
1. Connect CIN between VIN of the ILC7080/81 and the “GROUND PLANE”.
2. Keep the ground side of COUT and CNOISE connected to the “LOCAL GROUND” and not directly to the “GROUND
PLANE”.
3. On multilayer boards use component side copper for grounding around the ILC7080/81 and connect back to a “GROUND
PLANE” using vias.
4. If using a DC-DC converter in your design, use a star grounding system with separate traces for the power ground and the
control signals. The star should radiate from where the power supply enters the PCB.
Layout Considerations
1. Place all RF LDO related components; ILC7080/81, input capacitor CIN, noise bypass capacitor CNOISE and output capac-
itor COUT as close together as possible.
2. Keep the output capacitor COUT as close to the ILC7080/81 as possible with very short traces to the VOUT and GND pins.
3. The traces for the related components; ILC7080/81, input capacitor CIN, noise bypass capacitor CNOISE and output capac-
itor COUT can be run with minimum trace widths close to the LDO.
4. Maintain a separate “LOCAL GROUND” remote from the “GROUND PLANE” to ensure a quiet ground near the LDO.
Figure 9 shows how this circuit can be translated into a PCB layout.
8
REV. 1.0.7 4/3/03
ILC7080/81
Recommended Ceramic Output Capacitors
COUT
Capacitor Size
0805
IOUT
Dielectric
X5R
Part Number
C2012X5R1A105KT
GRM40X7R105K010
LMK212BJ105KG
GRM42-6X7R105K016
EMK316BJ105KL
TMK316BJ105KL
Capacitor Vendor
1µF
0 to 100mA
TDK
“
“
“
“
“
0805
“
“
“
“
“
X7R
muRata
0805
X7R
Taiyo-Yuden
muRata
1206
X7R
1206
X7R
Taiyo-Yuden
Taiyo-Yuden
1206
X5R
2.2µF
0805
0805
1206
0 to 150mA
X5R
X5R
X5R
GRM40X5R225K 6.3
C2012X5R0J225KT
EMK316BJ225ML
muRata
TDK
“
“
“
“
Taiyo-Yuden
4.7µF
1206
1206
0 to 150mA
“
X5R
X7R
GRM42-6X5R475K010
LMK316BJ475ML
muRata
“
Taiyo-Yuden
REV. 1.0.7 4/3/03
9
ILC7080/81
Typical Performance Characteristics
Unless otherwise specified TA =25˚C, VIN =VOUT(NOM), + 1V, ON/OFF pin tied to VIN.
Characterization at output currents above 50mA applies to ILC7081.
Dropout Characteristics
Output voltage vsTemperature
3.4
3.015
VOUT = 3.3V
VOUT = 3.0V
COUT = 0.47 µF (Ceramic)
COUT = 0.47 µF (Ceramic)
3.01
3.005
3
IOUT = 0mA
IOUT = 10mA
IOUT = 50mA
3.3
3.2
3.1
7081 only
2.995
2.99
IOUT = 100mA
IOUT = 150mA
3
2.985
3
3.2
3.4
3.6
-50
0
50
100
150
VIN (V)
Temperature (°C)
Dropout voltage vsTemperature
Dropout voltage vs IOUT
250
200
250
200
IOUT = 150mA
VOUT = 3.0V
VOUT = 3.0V
TA = 85°C
TA = 25°C
IOUT = 100mA
IOUT = 50mA
150
100
50
150
100
50
TA = –40°C
IOUT = 0mA
0
0
–40
25
85
0
50
100
150
Temperature (°C)
Output Current (mA)
Line Transient Response
Ground Current vs Input voltage
6
5
150
VIN: tr/tf < 1 µs
VOUT = 3.0 V
COUT = 0.47 µF (Ceramic)
IOUT = 50mA
IOUT = 10mA
VOUT = 3.0V
COUT = 2.2 µF (Ceramic)
125
100
75
IOUT = 150mA
IOUT = 100 mA
IOUT = 0mA
4
3.01
3.00
2.99
2.98
IOUT = 100mA
50
2
4
6
8
10
12
14
5µs/div
VIN (V)
10
REV. 1.0.7 4/3/03
ILC7080/81
Typical Performance Characteristics
Unless otherwise specified TA =25˚C, VIN =VOUT(NOM), + 1V, ON/OFF pin tied to VIN.
Characterization at output currents above 50mA applies to ILC7081.
Line Transient Response ILC7081
Line Transient Response
V
V
: tr/tf = 2 µs
= 3.0V
= 100 mA
IN
OUT
VIN: tr/tf = 2 µs
VOUT = 3.0V
5
4
5
4
I
OUT
IOUT = 50 mA
C
= 0.47 µF (Ceramic)
COUT = 0.47 µF (Ceramic)
OUT
3.01
3.00
2.99
2.98
3.01
3.00
2.99
2.98
2.97
5µs/div
5µs/div
Load Transient Response
Load Transient Response ILC7081
3.06
3.15
VOUT = 3.0 V
VOUT = 3.0V
3.04
3.10
COUT = 0.47 µF (Ceramic)
COUT = 0.47 µF (Ceramic)
3.02
3.00
3.05
3.00
2.98
50
1
100
1
100µs/div
100µs/div
Load Transient Response ILC7081
Short Circuit Current
3.15
3.10
VOUT = 3.0V
Thermal Cycling
VIN = 4V
COUT = 1 µF || 0.47 µF (Ceramic)
Output Shorted to Gnd
at time,
t = 0
1.5
1.0
3.05
3.00
2.95
0.5
0
100
1
100µs/div
t = 0
5ms/div
REV. 1.0.7 4/3/03
11
ILC7080/81
Typical Performance Characteristics
Unless otherwise specified TA =25˚C, VIN =VOUT(NOM), + 1V, ON/OFF pin tied to VIN.
Characterization at output currents above 50mA applies to ILC7081.
On/Off Transient Response
On/Off Transient Response
4
3
2
1
0
VOUT = 3.0V
IOUT = 10mA
VOUT = 3.0 V
IOUT = 50mA
3
2
COUT = 0.47 µF (Ceramic)
COUT = 0.47 µF (Ceramic)
1
0
1
5
0
5
0
500µs/div
200µs/div
On/Off Transient Response ILC7081
Spectral Noise Density
4
32.0
17.8
10.0
VOUT = 3.0V
IOUT = 100mA
VOUT = 3.0 V
IOUT = 50mA
3
2
CNOISE = 0.01 µF (ceramic)
5.6
3.2
1.8
1.0
0.6
1
0
COUT = 0.47 µF (Ceramic)
COUT = 1 µF (Ceramic)
COUT = 0.47 µF (Ceramic)
5
0
0.3
0.2
0.1
COUT = 2.2 µF (Ceramic)
COUT = 4.7 µF (Ceramic)
100
1K
10K
100K
1M
200µs/div
Freq (Hz)
Spectral Noise Density
with COUT = 10µF (Ceramic)
(For Ultra Low Noise)
Spectral Noise Density
6.0
32.0
17.8
10.0
VOUT = 3.0 V
VOUT = 3.0 V
CNOISE = 1 µF (Ceramic)
5.4
4.8
4.2
3.6
3.0
2.4
1.8
1.2
0.6
0
COUT = 0.47µF (Ceramic)
CNOISE = 0.01 µF (Ceramic)
5.6
3.2
1.8
1.0
0.6
VIN = 3.5V
IOUT = 1mA
VIN = 4V
VIN = 6V
IOUT = 10 mA
0.3
0.2
0.1
IOUT = 50mA
V
= 8V
IN
IOUT = 100 mA
100
1K
10K
100K
1M
100
1K
10K
100K
Freq (Hz)
Freq (Hz)
12
REV. 1.0.7 4/3/03
ILC7080/81
Typical Performance Characteristics
Unless otherwise specified TA =25˚C, VIN =VOUT(NOM), + 1V, ON/OFF pin tied to VIN.
Characterization at output currents above 50mA applies to ILC7081.
Ripple Rejection vs Frequency
Ripple Rejection vs Frequency
100
90
100
90
VOUT = 3.0V
IOUT = 100mA
VOUT = 3.0V
IOUT = 10mA
80
80
COUT = 4.7 µF (Ceramic)
COUT = 4.7 µF (Ceramic)
70
60
50
40
70
60
50
40
30
20
30
20
COUT = 2.2 µF (Ceramic)
COUT = 2.2 µF (Ceramic)
10
0
10
0
1K
10K
100K
Frequency (Hz)
1M
10M
1K
10K
100K
1M
10M
Frequency (Hz)
REV. 1.0.7 4/3/03
13
ILC7080/81
Package Outline Dimensions
Dimensions shown in inches and (mm).
5-Lead plastic surface mount (SOT-23-5)
0.122 (3.10)
0.106 (2.70)
0.071 (1.80)
0.055 (1.40)
0.118 (3.00)
0.102 (2.60)
PIN 1
0.037 (0.95) BSC
0.055 (1.40)
0.0393 (1.0)
0.057 (1.45)
0.035 (0.90)
10°
0°
0.0217 (0.55)
0.0138 (0.35)
0.0078 (0.2)
0.0031 (0.08)
SEATING
PLANE
0.0059 (0.15)
0.0019 (0.05)
0.019 (0.50)
0.0138 (0.35)
14
REV. 1.0.7 4/3/03
ILC7080/81
Ordering Information (TA = -40°C to +85°C)
ILC7080AIM5-xx
Output voltage (V) Grade
Order Information
ILC7080AIM526x
ILC7080AIM527x
ILC7080AIM528x
ILC7080AIM5285x
ILC7080AIM529x
ILC7080AIM530x
ILC7080AIM531x
ILC7080AIM533x
ILC7080AIM550x
*Package Marking
Supplied as:
2.6
2.7
2.8
2.85
2.9
3.0
3.1
3.3
5.0
A
A
A
A
A
A
A
A
A
CIx
CMx
CJ0x
CFx
CKx
CAx
CLx
CBx
CCx
3k Units on Tape and Reel
3k Units on Tape and Reel
3k Units on Tape and Reel
3k Units on Tape and Reel
3k Units on Tape and Reel
3k Units on Tape and Reel
3k Units on Tape and Reel
3k Units on Tape and Reel
3k Units on Tape and Reel
* Note: First two characters identify the product and the last character identifies the lot code
ILC7081AIM5-xx
Output voltage (V) Grade
Order Information
ILC7081AIM525x
ILC7081AIM526x
ILC7081AIM527x
ILC7081AIM528x
ILC7081AIM5285x
ILC7081AIM529x
ILC7081AIM530x
ILC7081AIM531x
ILC7081AIM533x
ILC7081AIM536x
ILC7081AIM547x
ILC7081AIM550x
ILC7081AIM5ADJx
*Package Marking
Supplied as:
2.5
2.6
2.7
2.8
2.85
2.9
3.0
3.1
3.3
3.6
4.7
5.0
ADJ
A
A
A
A
A
A
A
A
A
A
A
A
A
CXx
CPx
CNx
CJx
3k Units on Tape and Reel
3k Units on Tape and Reel
3k Units on Tape and Reel
3k Units on Tape and Reel
3k Units on Tape and Reel
3k Units on Tape and Reel
3k Units on Tape and Reel
3k Units on Tape and Reel
3k Units on Tape and Reel
3k Units on Tape and Reel
3k Units on Tape and Reel
3k Units on Tape and Reel
3k Units on Tape and Reel
CVx
COx
CQx
CYx
CRx
CTx
CWx
CSx
CUx
* Note: First two characters identify the product and the last character identifies the lot code
Summary
ILC7080AIM5xx
ILC7081AIM5xx
ILC7081AIM5ADJ
50mA, fixed voltage
100mA, fixed voltage
100mA, adjustable voltage
REV. 1.0.7 4/3/03
15
ILC7080/81
DISCLAIMER
FAIRCHILD SEMICONDUCTOR RESERVES THE RIGHT TO MAKE CHANGES WITHOUT FURTHER NOTICE TO
ANY PRODUCTS HEREIN TO IMPROVE RELIABILITY, FUNCTION OR DESIGN. FAIRCHILD DOES NOT ASSUME
ANY LIABILITY ARISING OUT OF THE APPLICATION OR USE OF ANY PRODUCT OR CIRCUIT DESCRIBED HEREIN;
NEITHER DOES IT CONVEY ANY LICENSE UNDER ITS PATENT RIGHTS, NOR THE RIGHTS OF OTHERS.
LIFE SUPPORT POLICY
FAIRCHILD’S PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT DEVICES
OR SYSTEMS WITHOUT THE EXPRESS WRITTEN APPROVAL OF THE PRESIDENT OF FAIRCHILD SEMICONDUCTOR
CORPORATION. As used herein:
1. Life support devices or systems are devices or systems
which, (a) are intended for surgical implant into the body,
or (b) support or sustain life, and (c) whose failure to
perform when properly used in accordance with
instructions for use provided in the labeling, can be
reasonably expected to result in a significant injury of the
user.
2. A critical component in any component of a life support
device or system whose failure to perform can be
reasonably expected to cause the failure of the life support
device or system, or to affect its safety or effectiveness.
www.fairchildsemi.com
4/3/03 0.0m 001
Stock#DS30007080
2002 Fairchild Semiconductor Corporation
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