ADP5003CP-EVALZ [ADI]
Low Noise Micro PMU, 3 A Buck Regulator with 3 A LDO;型号: | ADP5003CP-EVALZ |
厂家: | ADI |
描述: | Low Noise Micro PMU, 3 A Buck Regulator with 3 A LDO |
文件: | 总31页 (文件大小:1013K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
Low Noise Micro PMU,
3 A Buck Regulator with 3 A LDO
ADP5003
Data Sheet
FEATURES
Low noise, dc power supply system
FUNCTIONAL BLOCK DIAGRAM
V
:
PVIN1
4.2V TO 15V
PVIN1
PVIN1
High efficiency buck for first stage conversion
High PSRR, low noise LDO regulator to remove switching
ripple
Adaptive LDO regulator headroom control option for
optimal efficiency and PSRR across full load range
3 A, low noise, buck regulator
C
EN1
PVIN1
VOUT1
V
:
SW1
SW1
SW1
COMP1
PVOUT1
BUCK
REGULATOR
3A
L1
0.6V TO 5.0V
R
C
C
R
C
C
PVOUT1
R
BOT1
VSET1
PGND1
PGND1
PGND1
TOP1
Wide input voltage range: 4.2 V to 15 V
Programmable output voltage range: 0.6 V to 5.0 V
0.3 MHz to 2.5 MHz internal oscillator
VREG
R
RT
RT
C
VREG
V
:
PVINSYS
4.2V TO 15V
PVINSYS
PWRGD
SYSTEM
0.3 MHz to 2.5 MHz SYNC frequency range
3 A, low noise, NFET LDO regulator (active filter)
Wide input voltage range: 0.65 V to 5 V
Programmable output voltage range: 0.6 V to 3.3 V
Differential point of load remote sensing
3 µV rms output noise (independent of output voltage)
PSRR > 50 dB (to 100 kHz) with 400 mV headroom at 3 A
Ultrafast transient response
C
PVINSYS
SYNC
REFOUT
C
REFOUT
PVIN2
PVIN2
PVIN2
C
PVIN2
VSET2
VBUF
V
:
PVOUT2
PVOUT2
PVOUT2
PVOUT2
0.6V TO 3.3V
LOW NOISE
LDO ACTIVE
FILTER
C
VBUF
Power-good output
3A
C
VREG_LDO
PVOUT2
LOAD
Precision enable inputs for both the buck regulator and LDO
−40°C to +125°C operating junction temperature range
32-lead, 5 mm × 5 mm, LFCSP
C
VREG_LDO
VFB2P
VFB2N
EN2
AGND1
AGND2
APPLICATIONS
Low noise power for high speed analog-to-digital converter
(ADC) and digital-to-analog converter (DAC) designs
Powering RF transceivers and clocking ICs
Figure 1.
GENERAL DESCRIPTION
The ADP5003 integrates a high voltage buck regulator and an
ultralow noise low dropout (LDO) regulator in a small, 5 mm ×
5 mm, 32-lead LFCSP package to provide highly efficient and
quiet regulated supplies.
programmed using resistor dividers.
The LDO regulator output can be accurately controlled at the
point of load (POL) using remote sensing that compensates for the
printed circuit board (PCB) trace impedance while delivering
high output currents.
The buck regulator is optimized to operate at high output
currents up to 3 A. The LDO is capable of a maximum output
current of 3 A and operates efficiently with low headroom
voltage while maintaining high power supply rejection.
Each regulator is activated via a dedicated precision enable
input. The buck switching frequency can be synchronized to
an external signal, or programmed with an external resistor.
The ADP5003 can operate in one of two modes. Adaptive mode
allows the LDO to operate with an optimized headroom by
adjusting the buck output voltage internally in response to the
LDO load current. Alternatively, the ADP5003 can operate in
independent mode, where both regulators operate separately
from each other, and where the output voltages are
Safety features in the ADP5003 include thermal shutdown (TSD),
input undervoltage lockout (UVLO) and independent current
limits for each regulator. The ADP5003 is rated for a −40°C to
+125°C operating junction temperature range.
Rev. A
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Tel: 781.329.4700 ©2017–2019 Analog Devices, Inc. All rights reserved.
Technical Support
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ADP5003
Data Sheet
TABLE OF CONTENTS
Features .............................................................................................. 1
Setting the Switching Frequency for the Buck Regulator ....... 22
Setting the Output Voltage for the Buck Regulator ................. 22
Selecting the Inductor for the Buck Regulator ......................... 22
Selecting the Output Capacitor for the Buck Regulator.......... 22
Applications....................................................................................... 1
Functional Block Diagram .............................................................. 1
General Description......................................................................... 1
Revision History ............................................................................... 3
Specifications..................................................................................... 4
Buck Regulator Specifications .................................................... 5
LDO Specifications ...................................................................... 6
Adaptive Headroom Controller Specifications ........................ 6
Absolute Maximum Ratings............................................................ 7
Thermal Resistance ...................................................................... 7
ESD Caution.................................................................................. 7
Pin Configuration and Function Descriptions............................. 8
Typical Performance Characteristics ............................................. 9
Theory of Operation ...................................................................... 15
Power Management Unit........................................................... 15
Buck Regulator............................................................................ 15
LDO Regulator............................................................................ 17
Power-Good ................................................................................ 18
Output Voltage of the Buck Regulator..................................... 18
Output Voltage of the LDO Regulator..................................... 18
Voltage Conversion Limitations ............................................... 18
Component Selection................................................................. 19
Compensation Components Design........................................ 21
Junction Temperature ................................................................ 21
Buck Regulator Design Example .................................................. 22
Designing the Compensation Network for the Buck Regulator
....................................................................................................... 23
Selecting the Input Capacitor for the Buck Regulator............. 23
Adaptive Headroom Control Design Example .......................... 24
Setting the Switching Frequency for the Buck Regulator Using
Adaptive Headroom Control.................................................... 24
Setting the Output Voltage for the LDO Regulator Using
Adaptive Headroom Control.................................................... 24
Selecting the Inductor for the Buck Regulator Using Adaptive
Headroom Control..................................................................... 24
Selecting the Output Capacitors for the Buck Regulator Using
Adaptive Headroom Control.................................................... 24
Designing the Compensation Network for the Buck
Regulator Using Adaptive Headroom Control....................... 25
Selecting the Input Capacitor for the Buck Regulator Using
Adaptive Headroom Control.................................................... 25
Recommended External Components for the Buck Regulator
....................................................................................................... 26
Buck Configurations ...................................................................... 28
Independent................................................................................ 28
Adaptive Headroom................................................................... 29
Layout Considerations................................................................... 30
Outline Dimensions....................................................................... 31
Ordering Guide .......................................................................... 31
Rev. A | Page 2 of 31
Data Sheet
ADP5003
REVISION HISTORY
Changes to Compensation Components Design Section,
3/2019—Rev. 0 to Rev. A
Figure 46 and Junction Temperature Section..............................21
Changes to Table 10, Setting the Switching Frequency for the
Buck Regulator Section, Setting the Output Voltage for the
Buck Regulator Section, Selecting the Inductor for the Buck
Regulator Section, and Selecting the Output Capacitor for the
Buck Regulator Section ..................................................................22
Deleted Figure 44; Renumbered Sequentially.............................22
Changes Figure 47...........................................................................23
Changes to Table 11, Setting the Output Voltage for the LDO
Regulator Using Adaptive Headroom Control Section, and
Selecting the Inductor for the Buck Regulator Using Adaptive
Headroom Control Section ...........................................................24
Changes Figure 48...........................................................................25
Changes to Recommended External Components for the Buck
Regulator Section and Table 12 Title............................................26
Changes to Figure 49 Caption and Figure 50..............................28
Changes to Adaptive Headroom Section and Figure 52............29
Changes to Layout Considerations Section and Figure 53........30
Updated Outline Dimensions........................................................31
Changes to Applications Section, General Description, and
Figure 1 ...............................................................................................1
Changes to Table 1 ............................................................................4
Changes to Table 2 ............................................................................5
Changes to Table 3 ............................................................................6
Changes to Table 5 ............................................................................7
Changes to Table 7 ............................................................................8
Updated Typical Performance Characteristics Section;
Renumbered Sequentially ................................................................9
Changes to Adaptive Headroom Control Section, Active Pull
Down Section, and Power-Good Section ....................................15
Changes to Oscillator Frequency Control Section .....................16
Add Figure 38 and Figure 39 .........................................................16
Changes to Current-Limit and Short-Circuit Protection
Section and Current Limit Section ...............................................17
Changes to Output Voltage of the Buck Regulator Section,
Figure 44, Output Voltage of the LDO Regulator Section,
Figure 45, and Voltage Conversion Limitations Section............18
Changes to Input Capacitor Section, Inductor Section, and
Table 9...............................................................................................20
11/2017—Revision 0: Initial Version
Rev. A | Page 3 of 31
ADP5003
Data Sheet
SPECIFICATIONS
VPVIN1 = VPVINSYS = 4.2 V to 15 V, VPVIN2 = 0.65 V to 5 V, TJ = −40°C to +125°C for minimum/maximum specifications, and TA = 25°C for
typical specifications, unless otherwise noted.
Table 1.
Parameter
Symbol
Min Typ Max Unit Test Conditions/Comments
INPUT VOLTAGE RANGE
VPVIN1, VPVINSYS 4.2
15
5
V
V
VPVIN2
0.65
THERMAL SHUTDOWN
Threshold
Hysteresis
TSD
TSD-HYS
155
15
°C
°C
TJ rising
SYNC INPUT
Input Logic
High
VIH
1.1
V
Low
VIL
VI-LEAKAGE
0.4
1
V
µA
Input Leakage Current
ADAPTIVE MODE INPUT (VSET1)
Input Rising Threshold
Input Hysteresis
VADPR
VADPH
2.5
16
V
mV
PRECISION ENABLING
High Level Threshold
Low Level Threshold
Shutdown Mode
EN1, EN2 Pull-Down Resistance
INPUT CURRENT
VTH_H
VTH_L
VTH_S
RENPD
1.125 1.15 1.175 V
1.025 1.05 1.075 V
0.4
V
1.5
MΩ
Both Channels Enabled
Both Channels Disabled
REFOUT CHARACTERISTICS
Output Voltage
ISTBY-NOSW
ISHUTDOWN
0.5
5
1
10
mA No load, not switching
µA TJ = −40°C to +125°C
VREFOUT
2.0
5
V
%
Accuracy
−0.5
+0.5
+2
VREG AND VREG_LDO CHARACTERISTICS
Output Voltage
Accuracy
Current Limit1
VREG, VREG_LDO
V
%
mA
−2
10
POWER-GOOD PIN (PWRGD)
Power Good Threshold
Hysteresis
Output Voltage Level
Deglitch Time
PWRGDF
PWRGDFH
VOL
80
85 90
2.5
25 50
60
%
%
Applies to VOUT1 and VFB2P to VFB2N
mV PWRGD pin sink current = 1 mA
µs
tPWRGDD
PVINSYS UNDERVOLTAGE LOCKOUT (UVLO)
Input Voltage
Rising
Falling
UVLOPVINSYSRISE
UVLOPVINSYSFALL 3.9
4.2
V
V
1 Do not use VREG and VREG_LDO to supply the external loads. This current limit protects against a pin short to ground.
Rev. A | Page 4 of 31
Data Sheet
ADP5003
BUCK REGULATOR SPECIFICATIONS
VPVIN1 = VPVINSYS = 4.2 V to 15 V, VPVIN2 = 0.65 V to 5 V, TJ = −40°C to +125°C for minimum/maximum specifications, and TA = 25°C for typical
specifications, unless otherwise noted.
Table 2.
Parameter
Symbol
Min Typ
Max Unit Test Conditions/Comments
OUTPUT CHARACTERISTICS
Programmable Output Voltage Range1
Buck Regulator Gain
Error Amplifier Transconductance
Buck Output Voltage Accuracy2
Regulation
VPVOUT1
ABUCK
gm1
0.6
5.0
V
2.5
509 600
−1
VPVOUT1/VVSET1
661
+1
µS
%
VOUT1 load current (ILOAD1) = 10 mA
Line
Load
(ΔVPVOUT1/VPVOUT1)/ΔVPVIN1
(ΔVPVOUT1/VPVOUT1)/ΔILOAD1
0.004
0.04
1.5
%/V ILOAD1 = 10 mA
%/A 0 mA ≤ ILOAD1 ≤ 3 A, VPVIN1 = 12 V
Total Output Voltage Accuracy
OPERATING SUPPLY CURRENT
%
4.2 V ≤ VPVIN1 ≤ 15 V, 1 mA ≤ ILOAD1 ≤ 3 A
IIN
3.8
mA
ILOAD1 = 0 mA, LDO disabled, buck
switching
SW1 CHARACTERISTICS
SW1 On Resistance
RPFET
RNFET
ILIMIT1
130
60
200
100
mΩ
mΩ
A
VPVIN1 = 15 V (PVIN1 to SW1)
VPVIN1 = 15 V (SW1 to PGND1)
Negative channel field effect
transistor (NFET) switch valley
current limit
Current Limit Threshold
3.5
−1
A
Negative current limit
Slew Rate
SLEWSW1
tMIN_ON
tMIN_OFF
RPDWN-B
tSSBUCK
1.6
35
100
90
2
V/ns VPVIN1 = 15 V, ILOAD1 = 1 A
ns
ns
Minimum On Time3
Minimum Off Time
128
BUCK REGULATOR ACTIVE PULL DOWN
BUCK REGULATOR SOFT START (SS)
HICCUP TIME
Ω
Channel disabled
ms
ms
nA
tHICCUP
33
10
VSETx ADJUSTABLE INPUT BIAS CURRENT
OSCILLATOR
IVSET1, IVSET2
150
Internal Switching Frequency 1
Internal Switching Frequency 2
SYNC
fSW1
fSW2
2.25 2.5
0.26 0.3
2.75 MHz RRT ≤ 71.2 kΩ
0.34 MHz RRT = 600 kΩ
Frequency Range
fSYNC
0.3
2.5
MHz
Minimum Pulse Width
Positive
Negative
20
10
ns
ns
1 The switching frequency, minimum on time, and minimum off time may limit the output voltage range.
2 The buck output voltage accuracy is relative to the nominal output voltage and accounts for reference voltage, gain, and offset error.
3 The minimum on time indicates the minimum high-side turn on time to ensure fixed frequency switching.
Rev. A | Page 5 of 31
ADP5003
Data Sheet
LDO SPECIFICATIONS
VPVIN1 = VPVINSYS = 4.2 V to 15 V, VPVIN2 = 0.65 V to 5 V, LDO headroom voltage (VHR) = 300 mV, TJ = −40°C to +125°C for
minimum/maximum specifications, and TA = 25°C for typical specifications, unless otherwise noted.
Table 3.
Parameter
Symbol
Min Typ
Max Unit
Test Conditions/Comments
OUTPUT CHARACTERISTICS
Programmable Output Voltage Range1
LDO Gain
VLDO
ALDO
0.6
1.65
−1
3.3
+1
V
VVFB2P-VFB2N
VLDO/VVSET2
VOUT2 load current (ILOAD2) =
150 mA
Output Voltage Accuracy2
%
Regulation
Line
(ΔVLDO/VLDO)/ΔVPVIN2
(ΔVLDO/VLDO)/ΔILOAD2
0.007
%/V
(VPVOUT2 + VHR) ≤ VPVIN2 ≤ 6 V,
I
LOAD2 = 100 mA
Load
0.08
1.5
%/A
%
10 mA ≤ ILOAD2 ≤ 3 A
(VPVOUT2 + VHR) ≤ VPVIN2 ≤ 6 V,
10 mA ≤ ILOAD2 ≤ 3 A
Total Output Voltage Accuracy
OPERATING SUPPLY CURRENT
IGND
1.8
2.3
2.5
4.5
mA
mA
ILOAD2 = 0 μA
ILOAD2 = 3 A
ILOAD2 = 3 A
MINIMUM VOLTAGE REQUIREMENTS
PVINSYS to PVOUT23
VREG_LDO to PVOUT24
Dropout5
CURRENT-LIMIT THRESHOLD6
LDO SOFT START (SS) TIME
LDO ACTIVE PULL-DOWN
OUTPUT NOISE
VPVINSYS-PVOUT2
VVREG_LDO-PVOUT2
VDROPOUT
ILIMIT2
1.5
1.35
100
V
V
mV
A
Required to drive NFET
3.1
tSSLDO
400
µs
Ω
RPDWNLDO
NPVOUT2
300
Channel disabled
3
µV rms 10 Hz to 100 kHz, ILOAD2 = 1 A
VPVIN2 = VPVOUT2 + 0.3 V, ILOAD2 = 1A
LDO POWER SUPPLY REJECTION RATIO
VPVOUT2 = 1.3 V
PSRRLDO
87
82
61
38
89
83
61
37
dB
dB
dB
dB
dB
dB
dB
dB
1 kHz
10 kHz
100 kHz
1000 kHz
1 kHz
10 kHz
100 kHz
1000 kHz
VPVOUT2 = 3.3 V
1 Limited by minimum PVINSYS to PVOUT2 and VREG_LDO to PVOUT2 voltage.
2 The LDO output voltage accuracy is relative to the nominal output voltage and accounts for reference voltage, gain, and offset error.
3 PVINSYS must be higher than PVOUT2 by at least VPVINSYS-PVOUT2 to keep the LDO regulating.
4 PVOUT2 must be lower than VREG_LDO by at least VVREG_LDO-PVOUT2 to keep the LDO regulating.
5 The dropout voltage is the input to output voltage differential when the input voltage is set to the nominal output voltage.
6 The current-limit threshold is the current at which the output voltage drops to 90% of the specified typical value. For example, the current limit for a 1.0 V output
voltage is the current that causes the output voltage to drop to 90% of 1.0 V or 0.9 V.
ADAPTIVE HEADROOM CONTROLLER SPECIFICATIONS
VPVIN1 = VPVINSYS = 4.2 V to 15 V, VPVIN2 = 0.65 V to 5 V, TJ = −40°C to +125°C for minimum/maximum specifications, and TA = 25°C for typical
specifications, unless otherwise noted.
Table 4.
Parameter
HEADROOM VOLTAGE (PVIN2 − PVOUT2)
Symbol
VHR
Min
Typ
160
280
400
Max
Unit
mV
mV
mV
Test Conditions/Comments
ILOAD2 = 1 mA
ILOAD2 = 1.5 A
ILOAD2 = 3 A
Rev. A | Page 6 of 31
Data Sheet
ADP5003
ABSOLUTE MAXIMUM RATINGS
Table 5.
THERMAL RESISTANCE
Thermal performance is directly linked to PCB design and
operating environment. Careful attention to PCB thermal
design is required.
Parameter
Rating
PVIN1/PVINSYS to AGND1/AGND2
PVIN2 to AGND1/AGND2
AGND1 to AGND2
PGND1 to AGND1/AGND2
PVOUT2 to AGND1/AGND2
−0.3 V to +16 V
−0.3 V to +6.0 V
−0.3 V to +0.3 V
−0.3 V to +0.3 V
−0.3 V to the lower of
(PVIN2 + 0.3 V) or +6.0 V
Table 6. Thermal Resistance
1
1
Package Type
θJA
θJC
20.95
Unit
°C/W
CP-32-7
46.91
1 θJA and θJC are based on a 4-layer PCB (two signal and two power planes)
with nine thermal vias connecting the exposed pad to the ground plane as
recommended in the Layout Considerations section.
VFB2N to AGND1/AGND2/PGND1
−0.3 V to +0.3 V
−0.3 V to the lower of (VREG
+ 0.3 V) or +6.0 V
VOUT1, VFB2P, EN1, EN2, SYNC, RT,
REFOUT, VBUF, VSET1, VSET2,
COMP1 to AGND1/AGND2
SW1 to PGND1
VREG, VREG_LDO to
−0.3 V to (PVIN1 + 0.3 V)
−0.3 V to the lower of
ESD CAUTION
AGND1/AGND2/PGND1/VFB2N
(PVINSYS + 0.3 V) or +6.0 V
VREG to VREG_LDO
Storage Temperature Range
Operating Junction Temperature
Range
−0.3 V to +0.3 V
−65°C to +150°C
−40°C to +125°C
Soldering Conditions
JEDEC J-STD-020
Stresses at or above those listed under Absolute Maximum
Ratings may cause permanent damage to the product. This is a
stress rating only; functional operation of the product at these
or any other conditions above those indicated in the operational
section of this specification is not implied. Operation beyond
the maximum operating conditions for extended periods may
affect product reliability.
Rev. A | Page 7 of 31
ADP5003
Data Sheet
PIN CONFIGURATION AND FUNCTION DESCRIPTIONS
24 AGND1
23
22 RT
PGND1
VOUT1
EN1
1
2
3
4
5
6
7
8
VREG
ADP5003
21 COMP1
EN2
TOP VIEW
20
19
18
PWRGD
VSET1
REFOUT
SYNC
PVIN2
PVIN2
PVIN2
(Not to Scale)
17 VSET2
NOTES
1. EXPOSED THERMAL PAD. CONNECT THE
EXPOSED THERMAL PAD TO AGND1.
Figure 2. Pin Configuration
Table 7. Pin Function Descriptions
Pin No.
Mnemonic Description
1, 31, 32
2
3
PGND1
VOUT1
EN1
Buck Regulator Dedicated Power Ground.
Buck Regulator Feedback Input. Connect a short sense trace to the buck output capacitor.
Buck Regulator Precision Enable Pin. Drive the EN1 pin high to turn on the buck regulator, and drive the EN1 pin
low to turn off the buck regulator.
4
5
EN2
LDO Precision Enable Pin. Drive the EN2 pin high to turn on the LDO regulator, and drive the EN2 pin low to turn
off the LDO regulator.
Synchronization Input. To synchronize the switching frequency of the device to an external clock, connect this
pin to an external clock with a frequency from 300 kHz to 2.5 MHz.
SYNC
6 to 8
9 to 11
12
PVIN2
PVOUT2
VFB2P
LDO Regulator Power Input. Connect a 10 µF ceramic capacitor between this pin and AGND2.
LDO Regulator Power Output. Connect a 10 µF ceramic capacitor between this pin and AGND2.
LDO Regulator Positive Sense Feedback Input. Connect a sense trace to the LDO output at the load. Route this
pin alongside the VFB2N pin on the PCB.
13
VFB2N
LDO Regulator Ground Sense Feedback Input. Connect a sense trace to ground at the load. Route this pin
alongside the VFB2P pin on the PCB.
14
15
16
VBUF
AGND2
VREG_LDO
Output of the LDO Reference Buffer. Connect a 0.1 µF ceramic capacitor between this pin and VFB2N.
LDO Dedicated Analog Ground.
Internal Regulator Output for the LDO. Connect a 1 µF ceramic decoupling capacitor between this pin and
AGND2. Do not use this pin to power external devices.
17
18
VSET2
REFOUT
LDO Regulator Output Voltage Configuration Input.
Internal Reference Output Required for Driving the External Resistor Dividers for VSET1 and VSET2. Connect a
0.22 µF ceramic capacitor between this pin and AGND2.
19
VSET1
Buck Regulator Output Voltage Configuration Input. Connect this pin to VREG to enable adaptive headroom
control.
20
21
22
23
PWRGD
COMP1
RT
Power-Good Digital Output (Open-Drain NFET Pull-Down Driver).
Buck Regulator External Compensation Pin.
Resistor Adjustable Frequency Programming Input.
Internal Regulator Output. Connect a 1 µF ceramic decoupling capacitor between this pin and AGND1. Do not
use this pin to power external devices.
VREG
24
25
26, 27
28 to 30
AGND1
PVINSYS
PVIN1
SW1
Analog Ground.
System Power Supply for the ADP5003. Connect a 10 µF ceramic capacitor between this pin and AGND1.
Buck Regulator Power Input. Connect a 10 µF ceramic capacitor between this pin and PGND1.
Buck Regulator Switching Output.
EPAD
Exposed Thermal Pad. Connect the exposed thermal pad to AGND1.
Rev. A | Page 8 of 31
Data Sheet
ADP5003
TYPICAL PERFORMANCE CHARACTERISTICS
100
100
90
80
70
60
50
40
30
20
10
0
90
80
70
60
50
40
30
3.3V
2.5V
1.8V
1.3V
1.1V
20
10
0
3.3V
2.5V
1.8V
1.3V
1.1V
0
0.5
1.0
1.5
2.0
2.5
3.0
0
0.5
1.0
1.5
2.0
2.5
3.0
LOAD CURRENT (A)
LOAD CURRENT (A)
Figure 6. Adaptive Mode Efficiency vs. Load Current, VPVIN1 = 5 V,
fSW = 600 kHz at Various LDO Output Voltages
Figure 3. Buck Efficiency vs. Load Current, VPVIN1 = 5 V, fSW = 600 kHz at
Various Buck Output Voltages
100
90
80
70
60
50
40
30
90
80
70
60
50
40
30
20
3.3V
2.5V
1.8V
1.3V
1.1V
20
10
0
3.3V
2.5V
1.8V
1.3V
1.1V
10
0
0
0.5
1.0
1.5
2.0
2.5
3.0
0
0.5
1.0
1.5
2.0
2.5
3.0
LOAD CURRENT (A)
LOAD CURRENT (A)
Figure 7. Adaptive Mode Efficiency vs. Load Current, VPVIN1 = 12 V,
fSW = 600 kHz at Various LDO Output Voltages
Figure 4. Buck Efficiency vs. Load Current, VPVIN1 = 12 V, fSW = 600 kHz at
Various Buck Output Voltages
90
80
70
60
50
40
30
20
100
90
80
70
60
50
40
30
20
300kHz
300kHz
10
0
10
0
600kHz
600kHz
1MHz
1MHz
0
0.5
1.0
1.5
2.0
2.5
3.0
0
0.5
1.0
1.5
2.0
2.5
3.0
LOAD CURRENT (A)
LOAD CURRENT (A)
Figure 5. Buck Efficiency vs. Load Current, VPVIN1 = 12 V, VPVOUT1 = 3.3 V at
Various Buck Switching Frequencies
Figure 8. Adaptive Mode Efficiency vs. Load Current, VPVIN1 = 12 V,
VPVOUT2 = 3.3 V at Various Buck Switching Frequencies
Rev. A | Page 9 of 31
ADP5003
Data Sheet
0
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
–100
0.1A
0.1A
1A
1A
2A
3A
–10
–20
–30
–40
–50
–60
–70
–80
–90
–100
2A
3A
1
10
100
1k
10k
100k
1M
10M
1
10
100
1k
10k
100k
1M
10M
FREQUENCY (Hz)
FREQUENCY (Hz)
Figure 9. LDO PSRR vs. Frequency, VHR = 0.3 V, VPVOUT2 = 1.3 V at
Various LDO Load Currents
Figure 12. LDO PSRR vs. Frequency, VHR = 0.3 V, VPVOUT2 = 3.3 V at
Various LDO Load Currents
0
0
0.2V
0.2V
0.3V
0.4V
0.5V
0.3V
–10
–10
0.4V
0.5V
–20
–20
–30
–40
–50
–60
–70
–80
–90
–100
–30
–40
–50
–60
–70
–80
–90
–100
1
10
100
1k
10k
100k
1M
10M
1
10
100
1k
10k
100k
1M
10M
FREQUENCY (Hz)
FREQUENCY (Hz)
Figure 13. LDO PSRR vs. Frequency, VPVOUT2 = 3.3 V, ILOAD2 = 1 A at Various LDO
Headroom Voltages
Figure 10. LDO PSRR vs. Frequency, VPVOUT2 = 1.3 V, ILOAD2 = 1 A at Various LDO
Headroom Voltages
1000
0.1A
1A
1000
0.9V
3.3V
3A
100
10
1
100
10
1
V
= 3.3V
PVOUT2
I
= 1A
PVOUT2
0.1
0.1
1
10
100
1k
10k
100k
1M
10M
1
10
100
1k
10k
100k
1M
10M
FREQUENCY (Hz)
FREQUENCY (Hz)
Figure 14. LDO Noise Spectral Density vs. Frequency, VPVOUT2 = 3.3 V at
Various LDO Load Currents
Figure 11. LDO Noise Spectral Density vs. Frequency at Various LDO Output
Voltages
Rev. A | Page 10 of 31
Data Sheet
ADP5003
0.5
0.4
100000
10000
1000
100
0.3
0.2
0.1
0
–0.1
–0.2
–0.3
–0.4
–0.5
10
1
3A
2A
1A
0.1
10
100
1k
10k
100k
1M
10M
0
0.5
1.0
1.5
2.0
2.5
3.0
FREQUENCY (Hz)
LOAD CURRENT (A)
Figure 15. Adaptive Mode Noise Spectral Density vs. Frequency at various
Load Currents, VPVOUT1 = VPVIN2 =3.7 V, VPVOUT2 = 3.3 V, fSW = 2 MHz, L = 1.5 μH,
RC = 23.7 kΩ, CC = 1 nF, CCP = 10 pF, CPVOUT1 = 22 μF
Figure 18. Buck Load Regulation, VPVIN1 = 12 V, VPVOUT1 = 3.3 V, fSW = 600 kHz
0.5
0.4
0.5
0.4
0.3
0.3
0.2
0.2
0.1
0.1
0
0
–0.1
–0.2
–0.3
–0.4
–0.5
–0.1
–0.2
–0.3
–0.4
–0.5
0
0.5
1.0
1.5
2.0
2.5
3.0
4.2 5.0 6.0 7.0 8.0 9.0 10.0 11.0 12.0 13.0 14.0 15.0
LOAD CURRENT (A)
INPUT VOLTAGE (V)
Figure 16. Buck Line Regulation, VPVOUT1 = 3.3 V, ILOAD1 = 1 A, fSW = 600 kHz
Figure 19. LDO Load Regulation, VPVOUT2 = 3.3 V, VHR = 0.3 V
0.5
0.4
0.5
0.4
0.3
0.3
0.2
0.2
0.1
0.1
0
0
–0.1
–0.2
–0.3
–0.4
–0.5
–0.1
–0.2
–0.3
–0.4
–0.5
0.3
0.4
0.5
0.6
0.7
0.8
0.9
1.0
–50
–20
10
40
70
100
130
HEADROOM (V)
TEMPERATURE (°C)
Figure 17. LDO Line Regulation, VPVOUT2 = 3.3 V, ILOAD2 = 1 A
Figure 20. REFOUT Voltage (VREFOUT) vs. Temperature
Rev. A | Page 11 of 31
ADP5003
Data Sheet
3
3.0
2.5
2.0
1.5
1.0
0.5
0
2
1
0
–1
–2
–3
–50
4
6
8
10
12
14
–20
10
40
70
100
130
INPUT VOLTAGE (V)
TEMPERATURE (°C)
Figure 21. Switching Frequency vs. Temperature
Figure 24. Buck Quiescent Current vs. Input Voltage
0.50
0.45
0.40
0.35
0.30
0.25
0.20
0.15
0.10
0.05
0
4.0
3.5
3.0
2.5
2.0
1.5
1,0
0.5
0
0
0.5
1.0
1.5
2.0
2.5
3.0
0
0.5
1.0
1.5
2.0
2.5
3.0
LOAD CURRENT (A)
LOAD CURRENT( A)
Figure 25. Adaptive Mode Headroom vs. Load Current
Figure 22. LDO Quiescent Current vs. Load Current
I
L
I
L
1
V
SW1
V
SW1
2
3
1
V
PVOUT1
4
3
V
PVOUT1
CH1 5.00V
CH3 500mA B
M400ns
A CH1
5.70V
CH1 500mA
CH3 10mV Ω B
CH2 5V
M200ns
94ns
A CH2
8V
CH4 10.0mV ΩB
T
0.000µs
W
W
W
T
Figure 23 SW1 Waveform, VPVOUT1 = 5 V, ILOAD1 = 100 mA, fSW = 2 MHz,
L = 2.2 μH, RC = 2.7 kΩ, CC = 22 nF, CCP = 22 pF, CPVOUT1 = 22 μF
Figure 26. SW1 Waveform, VPVOUT1 = 5 V, ILOAD1 = 3 A, fSW = 2 MHz, L = 2.2 μH,
RC = 2.7 kΩ, CC = 22 nF, CCP = 22 pF, CPVOUT1 = 22 μF
Rev. A | Page 12 of 31
Data Sheet
ADP5003
V
PVOUT1
V
V
PVOUT1
2
2
V
SW1
SW1
3
1
3
1
I
I
L
L
B
CH1 5.00AB CH2 500mV
M20.0ms
40.0080ms
A CH2
510mV
B
W
W
CH1 5.00AB CH2 500mV
M20.0ms
40.0080ms
A CH2
510mV
W
W
CH3 10.0V B
CH3 10.0V B
T
W
T
W
Figure 27. Entering Hiccup Mode
(VSW1 is the Voltage of the SW1 Pin, and IL is Inductor Current)
Figure 30. Exiting Hiccup Mode
V
/V
EN1 EN2
V
EN1
2
3
V
VOUT1
V
PVOUT2
V
PVOUT1
3
1
4
I
LOAD1
4
2
1
I
LOAD2
V
SW1
CH1 1.00A
CH3 2.00V
CH2 1.00V
CH4 1.00V
M1.00ms
A CH3
2.04V
B
CH1 1A
CH3 1V
CH2 2V
CH4 10V B
M400µs
A CH2
1.56V
W
T
3.00400ms
B
W
W
Figure 31. Adaptive Mode Startup, VPVOUT2 = 3.3 V, ILOAD2 = 1 A
(VEN2 is the EN2 voltage.)
Figure 28. Buck Startup, VPVOUT1 = 3.3V, ILOAD1 = 3 A
(VEN1 is the EN1 voltage.)
I
LOAD1
V
PVIN1
0.42V/µs
0.11V/µs
2.3A/µs
3.1A/µs
4
2
V
PVOUT1
V
PVOUT1
4
2
10V OFFSET
CH2 500mV
CH4 1A
M200µs
A CH4
1.46A
CH2 500mV B CH4 20.0mVΩ B M80µs
A CH2
12.4V
W
W
T
493.480µs
T
25.50%
Figure 32. Buck Load Transient, VPVIN1 = 12 V, VPVOUT1 = 1.2 V, ILOAD1 = 0.5 A to 3 A,
fSW = 0.6 MHz, L = 2.2 μH, RC = 3.48 kΩ, CC = 2 nF, CCP = 22 pF, CPVOUT1 = 44 μF
Figure 29. Buck Line Transient, VPVIN1 = 12 V to 13 V, VPVOUT1 = 1.2 V, ILOAD1 = 1A,
fSW = 0.6 MHz, L = 2.2 μH, RC = 3.48 kΩ, CC = 2 nF, CCP = 22 pF, CPVOUT1 = 44 μF
Rev. A | Page 13 of 31
ADP5003
Data Sheet
2.3A/µs
3A/µs
I
LOAD2
0.18V/µs
V
0.07V/µs
PVIN2
4
2
1
2
3V OFFSET
V
PVOUT2
V
PVOUT2
CH2 20.0mV
CH4 1.00A
M8.00µs
A CH4
1.34A
B
CH1 500mV CH2 1.00mV
M80.0µs
A CH1
3.81V
W
T
18.4800µs
T
200.960µs
Figure 33. LDO Line Transient, VPVIN2 = 3.6 V to 4.1 V, VPVOUT2 = 3.3 V,
ILOAD2 = 1 A
Figure 36. LDO Load Transient, VPVIN2 = 3.6 V, VPVOUT2 = 3.3 V,
ILOAD2 = 0.5 A to 3 A
0.45V/µs
0.14V/µs
V
PVIN1
1.2A/µs
1.3A/µs
I
LOAD2
3
4
V
PVOUT2
V
PVOUT2
4
2
10V OFFSET
CH2 500mV B CH4 1.00mV Ω B
M80µs
25.90%
A CH2
12.5V
W
W
CH3 500mA
CH4 10.0mVΩ B M80µs
A CH2
1.52V
W
T
T
24.70%
Figure 34. Adaptive Mode Line Transient, VPVIN1 = 11 V to 13 V, VPVOUT2 = 3.3 V,
Figure 37. Adaptive Mode Load Transient, VPVIN1 = 12 V, VPVOUT2 = 3.3 V,
LOAD2 = 1 A to 1.5 A, fSW = 1.5 MHz, L = 2.2 μH, RC = 3.48 kΩ, CC = 22 nF,
CCP = 22 pF, CPVOUT1 = 64 μF
I
LOAD2 = 1 A, fSW = 1.5 MHz, L = 2.2 μH, RC = 3.48 kΩ, CC = 22 nF, CCP = 22 pF,
CPVOUT1 = 64 μF
I
I
PVIN1
3
4
V
PVOUT2
CH3 1.00 A
CH4 20.0mV Ω B
M8.00µs
A CH3
920mA
T
24.7%
W
Figure 35. Adaptive Mode Load Transient, VPVIN1 = 12 V, VPVOUT2 = 3.3 V,
LOAD2 = 0.5 A to 3 A, fSW = 1.5 MHz, L = 2.2 μH, RC = 3.48 kΩ, CC = 22 nF,
CCP = 22 pF, CPVOUT1 = 64 μF
I
Rev. A | Page 14 of 31
Data Sheet
ADP5003
THEORY OF OPERATION
Active Pull Down
POWER MANAGEMENT UNIT
Both regulators have active pull-down resistors discharging the
respective output capacitors when the regulators are disabled.
The pull-down resistors are connected between VOUT1 to
AGND1 and PVOUT2 to AGND2. Active pull-down resistors
are disabled when the regulators are turned on.
The ADP5003 is a micropower management unit combining a
step-down (buck) dc-to-dc converter and an ultralow noise low
dropout linear (LDO)regulator. The high switching frequency
and 5 mm × 5 mm, 32-lead LFCSP package allow a compact
power management solution.
When the enable pins are asserted low, or a TSD or UVLO
event occurs, the active pull-down resistors enable to quickly
discharge the output capacitors. The pull-down resistors remain
engaged until the enable pins are asserted high, the fault event is
no longer present, or the VREG supply voltage falls to less than
the voltage required (approximately 1 V) to guarantee that the
pull-down resistor remains enabled.
Adaptive Headroom Control
The ADP5003 features a scheme to control the LDO headroom
voltage to ensure optimal operating efficiency while maintaining a
consistent power supply rejection ratio (PSRR) across the full
range of the LDO load current.
The scheme works by varying the headroom voltage across the
LDO NFET with respect to the LDO load current. Lower and
upper limits prevent the headroom from approaching zero volts
at light loads and from increasing more than necessary at high
loads.
Soft Start (SS)
Both regulators have an internal soft start function that ramps
the output voltage in a controlled manner on startup, thereby
limiting the inrush current. The soft start function reduces the
risk of noise spikes and voltage drops on the upstream supplies.
Precision Enable/Shutdown
The ADP5003 has individual enable pins (EN1 and EN2) to
control the regulators.
Power-Good
The ADP5003 has a dedicated power-good, open-drain, output
(PWRGD). PWRGD indicates whether one or more regulators
are outside the voltage limits specified by the power-good lower
limit (PWRGDF) and the power-good upper limit (PWRGDF +
PWRGDFH). When either one or both of the regulator outputs
are outside the power-good limits, the PWRGD output pulls low.
PWRGD will continue to pull low, provided the VREG supply
voltage remains above approximately 1 V.
The precision enable function allows a precise turn on point for
the regulators to allow the possibility of external sequencing. A
voltage level higher than VTH_H applied to the EN1 or EN2 pin
activates a regulator, whereas a level below VTH_L turns off a
regulator. The buck is controlled by EN1, and the LDO is
controlled by the EN2 pin. When both EN1 and EN2 fall below
V
TH_S, the ADP5003 enters shutdown mode.
Undervoltage Lockout (UVLO)
When in adaptive mode, PWRGD only monitors the LDO
output, and when in standalone mode, PWRGD only monitors
the regulator/regulators that are enabled.
To protect against the input voltage being too low, UVLO
circuitry is integrated into the system. If the input voltage on
PVINSYS drops to less than the UVLOPVINSYSFALL threshold, all
channels shut down.
BUCK REGULATOR
Control Scheme
The device is enabled again when the voltage on PVINSYS rises
to more than the UVLOPVINSYSRISE threshold, provided the enable
pins remain active.
The buck regulator operates with a fixed frequency, emulated
peak current mode, pulse-width modulation (PWM) control
architecture, where the duty cycle of the integrated switches is
adjusted and regulates the output voltage. At the start of each
oscillator cycle, the positive channel field effect transistor (PFET)
switch is turned on, sending a positive voltage across the inductor.
Current in the inductor increases until the emulated current
sense signal crosses the peak inductor current threshold, which
turns off the PFET switch and turns on the NFET synchronous
rectifier. Turning on the NFET synchronous rectifier creates a
negative voltage across the inductor, which causes the inductor
current to decrease. The synchronous rectifier stays on for the
remainder of the cycle. By adjusting the peak inductor current
threshold, the buck regulator can regulate the output voltage.
Thermal Shutdown (TSD)
In the event that the junction temperature rises above TSD, the
thermal shutdown circuit turns off both regulators. Extreme
junction temperatures can be the result of high current operation,
poor circuit board design, or a high ambient temperature. A
hysteresis value of TSD-HYS is included so that when thermal
shutdown occurs, the regulators do not return to operation until
the on-chip temperature drops below TSD − TSD-HYS. When
emerging from thermal shutdown, both regulators restart with
soft start control.
Rev. A | Page 15 of 31
ADP5003
Data Sheet
The emulated inductor current scheme senses the current in the
inductor during the off phase of the cycle, when the NFET is
conducting, and uses this inductor current to generate the
emulated current sense signal during the on time of the cycle.
This scheme allows the low duty cycles necessary for high input
voltage, VIN, to output voltage, VOUT, conversion ratios.
External Oscillator Synchronization
The SYNC pin is dedicated for oscillator synchronization and
allows the ADP5003 to lock to an external clock.
When an applied external clock signal is present at the SYNC pin,
the buck regulator operates in sync with this signal.
When alternating between external clocks and the internal
oscillator, the presence of an external frequency causes a
multiplexer to switch between the internal oscillator and the
external SYNC frequency. The output of this multiplexer acts as
the frequency reference to an internal phase-locked loop (PLL),
which ensures that changing between the two modes of operation
results in a smooth transition between the different frequencies.
Oscillator Frequency Control
The ADP5003 buck regulator oscillator frequency is controlled
by using the RT pin or the SYNC pin. To define the buck
regulator internal switching frequency, connect the RT pin via a
resistor to AGND1. Figure 38 shows the relationship of the buck
oscillator frequency and the RT resistor value.
3.0
Buck Startup
2.5
2.0
1.5
1.0
0.5
0
The buck regulator turns on with a controlled soft start ramp to
limit inrush current. The reference of the buck is ramped
during tSSBUCK, which is typically 2 ms (see Figure 39).
tSSBUCK
V
EN1
2
V
PVOUT1
4
1
3
10k
100k
1M
I
LOAD1
RT RESISTOR (Ω)
Figure 38. Buck Oscillator Frequency vs. RT Resistor (RRT
)
V
SW1
To determine the oscillator frequency (fSW), use the following
equation:
B
B
CH1 1.00A B
CH3 5.00V
CH2 5.0V
CH4 1.0V
4.00µs
1.60ms
A CH2
1.20V
W
W
W
W
B
T
f
SW = (1.78 × 1011)/RRT
(1)
Figure 39. Buck Startup
An upper limit prevents out of range frequencies when the RT
pin is shorted to ground or connected with a resistor value less
than 70 kΩ.
Rev. A | Page 16 of 31
Data Sheet
ADP5003
Current-Limit and Short-Circuit Protection
LDO REGULATOR
The buck regulator includes current-limit protection circuitry
to limit the amount of forward current through the field effect
transistor (FET) switches. When the valley inductor current
exceeds the overcurrent limit threshold for a number of clock
cycles during an overload or short-circuit condition, the
regulator enters hiccup mode. The regulator stops switching
and then restarts with a new soft start cycle after the hiccup
time, tHICCUP, and repeats until the over-current condition is
removed. If the buck regulator output voltage falls below 50%
of the nominal output voltage, the regulator immediately enters
hiccup mode. When the valley inductor current falls below the
negative current-limit threshold, the NFET turns off and the
PFET remains off allowing the inductor current to be discharged
via the PFET body diode. The PFET turns on again with the
next clock edge after the inductor current no longer exceeds
the negative current-limit threshold.
The ADP5003 contains a single low noise, low dropout (LDO)
linear regulator that uses an NFET pass device to provide high
PSRR with low headroom voltage and an output current up to 3 A.
The LDO regulator can operate with an input voltage of 0.65 V
to 5 V while providing excellent line and load transient response
using 10 µF ceramic input and output capacitors.
LDO Startup
The LDO regulator turns on with a controlled soft start ramp to
limit inrush current. This soft start ramp is dictated by tSSLDO
,
which is typically 400 µs.
4.0
0.1A
3.5
1A
3A
3.5
3.0
2.5
2.0
1.5
1.0
0.5
0
V
EN2
2.5
1.5
0.5
–0.5
–1.5
–2.5
–3.5
–4.5
2
3.5A
3
–0.4 –0.2
0
0.2
0.4
0.6
0.8
1.0
1.2
1.4 1.6
TIME (ms)
tHICCUP
Figure 41. LDO Startup
1
Current Limit
The LDO operates in current limit when the output load exceeds
LIMIT2. When in current limit operation, the output voltage
I
reduces to maintain a constant output current.
Differential Remote Sensing
V
VOUT1
The LDO can sense at the point of load by using VFB2P and
VFB2N as shown in Figure 42. Differential remote sensing
compensates for both the source drop and the return drop to
provide a more precise supply scheme at the point of load.
2
3.5A
I
L
3
1
PVOUT2
LOW NOISE
PVOUT2
PVOUT2
LDO ACTIVE
FILTER
3A
–
+
V
SW1
VFB2P
VFB2N
+
LOAD
–
CH1 10.0V
CH3 2.0A
CH2 2.00V
20.0ms
A CH2
1.08V
B
T
79.7600ms
W
Figure 40. Short-Circuit Response (Current Limit and Hiccup Mode)
AGND1
AGND2
–
+
Figure 42. Differential Remote Sensing
Rev. A | Page 17 of 31
ADP5003
Data Sheet
POWER-GOOD
OUTPUT VOLTAGE OF THE LDO REGULATOR
An external pull-up resistor is necessary to drive the PWRGD
output high (see Figure 43). Through the value of the pull-up
resistor is not critical, it is recommended to use a 10 kΩ to
300 kΩ resistor. The resistor must be pulled to a voltage level
no greater than 5.5 V.
The output voltage on the LDO regulator is adjustable through
an external resistor divider. The LDO adjustable output voltage
configuration is shown in Figure 45.
PVOUT2
PVIN2
REFOUT
VFB2P
VFB2N
V
PULLUP
LDO
R
TOP2
VSET2
R
PULLUP
PWRGD
GPIO
V
R
PWRGD
BOT2
Figure 45. LDO Adjustable Output Voltage Configuration
Figure 43. Power-Good Setup
To calculate the LDO output voltage, use the following
equation:
OUTPUT VOLTAGE OF THE BUCK REGULATOR
The output voltage on the buck regulator is adjustable through
an external resistor divider. When using adaptive mode, the
ADP5003 controls the buck output voltage.
RBOT 2
RTOP 2 RBOT 2
(3)
VPVOUT 2 VREFOUT ALDO
where:
LDO is the LDO gain.
The adjustable output voltage configuration is shown in Figure 44.
A
SW1
PVOUT1
PVIN1
REFOUT
R
R
BOT2 is the bottom divider resistor.
TOP2 is the top divider resistor.
VOUT1
BUCK
R
VOLTAGE CONVERSION LIMITATIONS
TOP1
VSET1
For a given input voltage and switching frequency, an upper
and lower limitation on the output voltage exists due to the
minimum on time and minimum off time. The minimum on
time limits the minimum output voltage for a given input
voltage and switching frequency.
R
BOT1
Figure 44. Buck Regulator Adjustable Output Voltage
If the minimum on time is exceeded, the ADP5003 may not
To calculate the buck output voltage, use the following equation:
switch at a fixed frequency because the device can switch at an
effective zero on time, resulting in unpredictable switching
frequencies and unwanted noise.
RBOT 1
TOP1 RBOT 1
(2)
VPVOUT 1 VREFOUT ABUCK
R
To calculate the minimum output voltage for a given input
voltage and fixed switching frequency, use the following
equation:
where:
VREFOUT is the REFOUT output voltage.
BUCK is the buck regulator gain.
A
R
R
BOT1 is the bottom divider resistor.
TOP1 is the top divider resistor.
V
OUT_MIN = VPVIN1 × tMIN_ON × fSW − (RPFET – RNFET) ×
OUT_MIN × tMIN_ON × fSW − (RNFET + RL) × IOUT_MIN (4)
I
where:
V
V
OUT_MIN is the minimum output voltage.
PVIN1 is the input voltage.
t
MIN_ON is the minimum on time.
f
SW is the switching frequency.
R
R
PFET is the high-side PFET on resistance.
NFET is the low-side NFET on resistance.
I
OUT_MIN is the minimum output current.
RL is the resistance of the output inductor.
Rev. A | Page 18 of 31
Data Sheet
ADP5003
The minimum off time limits the maximum duty cycle which
in turn limits the maximum output voltage for a given input
voltage and switching frequency. Calculate the maximum output
voltage for a given input voltage and switching frequency by
using the following equation:
Use the following equation to calculate the worst case capacitance,
accounting for capacitor variation over temperature, component
tolerance, and voltage:
C
EFFECTIVE = CNOMINAL × (1 − TEMPCO) × (1 − DCBIASCO) ×
(1 − Tolerance) (6)
V
OUT_MAX = VPVIN1 × (1 − tMIN_OFF × fSW) − (RPFET – RNFET) × IOUT_MAX
×
where:
C
(1 − tMIN_OFF × fSW) − (RNFET + RL) × IOUT_MAX
(5)
EFFECTIVE is the effective capacitance at the operating voltage.
NOMINAL is the nominal data sheet capacitance.
TEMPCO is the worst case capacitor temperature coefficient.
DCBIASCO is the dc bias derating at the output voltage.
Tolerance is the worst case component tolerance.
where:
OUT_MAX is the maximum output voltage.
OUT_MAX is the maximum output current.
MIN_OFF is the minimum off time.
C
V
I
t
As shown in Equation 4 and Equation 5, reducing the switching
frequency eases the minimum on time and minimum off time
limitations.
To guarantee the performance of the device, it is imperative to
evaluate the dc bias effects, temperature, and tolerances on the
behavior of the capacitors for each application.
Capacitors with lower effective series resistance (ESR) and
effective series inductance (ESL) are preferred to minimize
output voltage ripple.
COMPONENT SELECTION
Output Capacitors
Higher output capacitor values reduce the output voltage ripple
and improve the load transient response.
Use the following equation to calculate the minimum
capacitance needed for a specific output voltage ripple:
Ceramic capacitors are manufactured with a variety of dielectrics,
each with a different behavior over temperature and applied
voltage. Capacitors must have a dielectric adequate to ensure
the minimum capacitance over the necessary temperature range
and dc bias conditions. X5R or X7R dielectrics with a voltage
rating of 25 V are recommended for best performance. Y5V
and Z5U dielectrics are not recommended for use with any dc-
to-dc converter because of their poor temperature and dc bias
characteristics.
ΔIL
(7)
COUT_MIN
≅
8× fSW ×(VRIPPLE
—
ΔIL ×RESR )
where:
ΔIL is the current ripple.
SW is the switching frequency.
f
V
R
RIPPLE is the allowed peak-to-peak voltage ripple.
ESR is the effective series resistance of the capacitor.
The minimum capacitance needed for stability considering
temperature and dc bias effects is 22 µF.
The minimum capacitance recommended for the LDO is 10 µF.
Table 8. Recommended Output Capacitors
Vendor
Wurth
Part No.
Value (µF)
Type
X7R
X7R
X5R
X5R
X7R
X7R
X7R
Voltage Rating (V)
Case
0805
1210
1210
1210
0805
1210
1210
885 012 207 026
885 012 209 006
885 012 109 012
885 012 109 004
GRM21BR71A106KE51
GRM32ER71C226KEA8
GRM32ER71A476KE15
10
22
47
100
10
22
47
10
10
25
6.3
10
16
10
Murata
Rev. A | Page 19 of 31
ADP5003
Data Sheet
To calculate the inductor value, L, use the following equation:
Input Capacitor
The input current to the buck converter steps from zero to a
positive value that is dependent on inductor value, switching
frequency, and load current (typically between 1 Aand 4 A) and
then drops quickly to zero again every switching cycle. Because
these current pulses occur at relatively high frequencies (0.3 MHz
to 2.5 MHz), the input bypass capacitor provides most of the
high frequency current while the input power source supplies
only the average current. Higher value input capacitors reduce
the input voltage ripple and improve transient response.
L = ((VPVIN1 − VPVOUT1) × D)/(ΔIL × fSW
where:
)
(8)
V
PVIN1 is the input voltage.
VPVOUT1 is the output voltage.
D is the duty cycle (D = VVOUT1/VPVIN1).
ΔIL is the inductor ripple current.
fSW is the switching frequency.
The minimum dc current rating of the inductor must be greater
than the inductor peak current. Use the following equation to
calculate the inductor peak current:
To minimize supply noise, it is recommended to place a low
ESR capacitor as close as possible to the relevant supply pin.
I
PEAK = ILOAD1 + (ΔIL/2)
where:
LOAD1 is the output current.
ΔIL is the inductor ripple current.
(9)
Inductor
The high switching frequency of the ADP5003 buck allows the
selection of small chip inductors. A small inductor leads to larger
inductor current ripple that provides improved transient response
but degrades efficiency. The sizing of the inductor is a trade-off
between efficiency and transient response. As a guideline, the
inductor peak-to-peak current ripple is typically set to 1/3 of
the maximum load current for optimal transient response and
efficiency.
I
Inductor conduction losses are minimized by using larger sized
inductors that have smaller dc resistance; this in turn improves
efficiency at the cost of solution size. Due to the high switching
frequency of the ADP5003, shielded ferrite core material is
recommended for its low core losses and low electromagnetic
interference (EMI).
Table 9. Recommended Inductors
Vendor
Part No.
Value (µH) Saturation Current, ISAT (A)
RMS Current, IRMS (A)
DC Resistance (mΩ)
Size (mm)
4 × 4
4 × 4
4 × 4
4 × 4
5 × 5
5 × 5
5 × 5
5 × 5
5 × 5
5 × 5
6 × 6
6 × 6
6 × 6
6 × 6
6 × 6
6 × 6
6 × 6
6 × 6
6 × 6
4 × 4
4 × 4
4 × 4
4 × 4
4 × 4
Coilcraft XAL4020-102
XAL4020-122
XAL4020-152
XAL4020-222
XAL5030-102
XAL5030-122
XAL5030-222
XAL5030-332
XAL5050-562
XAL5050-682
XEL6030-102
XEL6030-152
XEL6030-222
XEL6030-332
XEL6060-472
XAL6060-562
XEL6060-682
XEL6060-822
XAL6060-103
1
8.7
7.9
7.1
5.6
14
6.7
6.6
5.2
4
8.7
7.9
7.2
5.9
5.3
4.7
12
10
7
13.25
17.75
21.45
35.2
8.5
1.2
1.5
2.2
1
1.2
2.2
3.3
5.6
6.8
1
12.5
9.2
8.7
6.3
6
11.4
13.2
21.2
23.45
26.75
6.32
9.57
12.7
19.92
13.65
14.46
20.82
22.71
27
18
1.5
2.2
3.3
4.7
5.6
6.8
8.2
10
1
1.2
1.5
1.8
2.2
15
13
10.5
11.4
9.9
7.9
7.6
7.6
9.6
8.8
8.5
8
6
9
7.5
7.3
7
5
Wurth
744 383 570 10
744 383 570 12
744 383 570 15
744 383 570 18
744 383 570 22
7.4
7
6.2
5.8
5.2
11.6
13.4
17.1
18
7
22
Rev. A | Page 20 of 31
Data Sheet
ADP5003
CCP = (RESR × CPVOUT1)/RC
(12)
COMPENSATION COMPONENTS DESIGN
For the peak current mode control architecture, the power stage
can be simplified as a voltage controlled current source that
supplies current to the output capacitor and load resistor. The
simplified loop is composed of one dominant pole and a zero
contributed by the output capacitor ESR.
JUNCTION TEMPERATURE
In cases where the ambient temperature (TA) is known, the
thermal resistance parameter (θJA) can estimate the junction
temperature rise (TJ). TJ is calculated with TA and the power
dissipation (PD) using the following formula:
The ADP5003 uses a transconductance amplifier as the error
amplifier to compensate the system. Figure 46 shows the
simplified peak current mode control, small signal circuit.
TJ = TA + (PD × θJA)
(13)
The typical θJA value for the 32-lead, 5 mm × 5 mm LFCSP is
46.91°C/W. An important factor to consider is that θJA is based
on a 4-layer, 4 inches × 3 inches, 2.5 ounces copper PCB, as per
the JEDEC standard, and applications may use different sizes
and layers. It is important to maximize the copper used to
remove the heat from the device. Copper exposed to air
dissipates heat better than copper used in the inner layers.
Connect the exposed pad to the ground plane with several vias.
V
V
V
REFOUT
PVOUT1
PVOUT1
R
TOP1
C
–
gm
+
V
PVOUT1
ESR
COMP1
+
–
A
VI
V
A
BUCK
SET1
R
R
C
C
CP
R
R
BOT1
C
C
If the case temperature can be measured, the junction
temperature is calculated by
Figure 46. Simplified Peak Current Mode Control, Small Signal Circuit
TJ = TC + (PD × θJC)
where:
TC is the case temperature.
JC is the junction to case thermal resistance provided in Table 6.
(14)
The compensation components, RC and CC, contribute a zero,
and the optional CCP and RC contribute an optional pole.
The following procedure shows how to select the compensation
components (RC, CC, and CCP) for ceramic output capacitor
applications:
θ
To achieve reliable operation of the buck converter and LDO
regulator, the estimated die junction temperature of the
ADP5003 must be less than 125°C. Reliability and mean time
between failures (MTBF) is highly affected by increasing the
junction temperature. Additional information about product
reliability can be found in the Analog Devices, Inc., Reliability
Handbook at www.analog.com/reliability_handbook.
1. Determine the cross frequency (fC). Generally, fC is
between fSW/12 and fSW/6.
2. Use the following equation to calculate RC:
2 × π ×CPVOUT1 × ABUCK
(10)
RC =
gm × AVI
The total power dissipation in the ADP5003 simplifies to
where:
PD = PDBUCK + PDLDO
where:
(15)
C
A
PVOUT1 is the output capacitance.
VI = 7 A /V.
P
P
DBUCK = (VPVIN1 × IPVIN1) − (VPVOUT1 × ILOAD1).
DLDO = ((VPVIN2 − VPVOUT2) × ILOAD2) + (VPVIN2 × IGND).
3. Place the compensation zero at the domain pole (fP).
Determine CC as follows:
CC = ((R + RESR) × CPVOUT1)/RC
(11)
where:
R
ESR is the equivalent series resistance of the output
capacitor.
CP is optional. It can cancel the zero caused by the ESR of
the output capacitor. Determine CCP as follows:
4.
C
Rev. A | Page 21 of 31
ADP5003
Data Sheet
BUCK REGULATOR DESIGN EXAMPLE
This section provides an example of the step by step design
procedures and the external components required for the buck
regulator. Table 10 lists the design requirements for this
example.
SELECTING THE INDUCTOR FOR THE BUCK
REGULATOR
The peak-to-peak inductor ripple current, ΔIL, is set to 35% of
the maximum output current. Use Equation 8 to estimate the
value of the inductor:
Table 10. Example Design Requirements for the Buck Regulator
Parameter
Specification
VPVIN1 = 12 V
VPVOUT1 = 2.5 V
ILOAD1 = 3 A
ΔVOUT1_RIPPLE = 25 mV
5% at 20% to 80% load transient
L = ((VPVIN1 − VPVOUT1) × D)/(ΔIL × fSW
where:
)
Input Voltage
Output Voltage
Output Current
Output Ripple
Load Transient
V
PVIN1 = 12 V.
VPVOUT1 = 2.5 V.
D is the duty cycle (D = VPVOUT1/VPVIN1).
ΔIL = 35% × 3 A = 1.05 A.
f
SW = 600 kHz.
SETTING THE SWITCHING FREQUENCY FOR THE
BUCK REGULATOR
The first step is to determine the switching frequency for the
ADP5003 design. In general, higher switching frequencies
produce a smaller solution size due to the lower component
values required, whereas lower switching frequencies result in
higher conversion efficiency due to lower switching losses.
The resulting value for L is 3.14 µH. The selected standard
inductor value is 3.3 µH; therefore, ΔIL is 1 A.
To calculate the peak inductor current (IPEAK), use Equation 9:
IPEAK = ILOAD1 + (ΔIL/2)
The calculated peak current for the inductor is 3.5 A.
SELECTING THE OUTPUT CAPACITOR FOR THE
BUCK REGULATOR
The output capacitor must meet the output voltage ripple, load
transient requirements and stability requirements. To meet the
output voltage ripple requirement, use Equation 7 to calculate
the capacitance:
The switching frequency of the ADP5003 can be set from
0.3 MHz to 2.5 MHz by connecting a resistor from the RT pin
to ground. The selected resistor allows the user to make decisions
based on the trade-off between efficiency and solution size. (For
more information, see the Oscillator Frequency Control section.)
However, the highest supported switching frequency must be
assessed by checking the voltage conversion limitations enforced
by the minimum on time and the minimum off time (see the
Voltage Conversion Limitations section).
ΔIL
COUT_MIN
≅
8× fSW ×(VRIPPLE
—
ΔIL ×RESR )
The calculated capacitance, COUT_MIN, is 8.7 µF.
In this design example, a switching frequency of 600 kHz is
used to achieve an ideal combination of small solution size and
high conversion efficiency. To set the switching frequency to
600 kHz, use Equation 1 to calculate the resistor value, RRT. This
gives a standard resistor value of RT = 294 kΩ.
To meet the 5% overshoot and undershoot requirements, use
the following equations to calculate the capacitance:
KUV × ΔISTEP2 × L
(17)
(18)
COUT_UV
=
2×
(
VPVIN1 –VPVOUT1 × ΔVOUT _UV
)
KOV × ΔISTEP2 × L
SETTING THE OUTPUT VOLTAGE FOR THE BUCK
REGULATOR
Select a value for the top resistor (RTOP1) and then calculate the
bottom feedback (RBOT1) resistor by using the following
equation:
COUT_OV
=
2
2
V
PVOUT1 + ΔVOUT _OV
–VPVOUT1
where:
UV and KOV are factors (typically set to 2).
ΔISTEP is the load step.
K
ΔVOUT_UV is the allowable undershoot on the output voltage.
ΔVOUT_OV is the allowable overshoot on the output voltage.
R
BOT1 = (RTOP1 × VPVOUT1)/((VREFOUT × ABUCK) − VPVOUT1
) (16)
where:
For estimation purposes, use KOV = KUV = 2; therefore,
V
V
A
PVOUT1 is the buck output voltage.
REFOUT is 2 V.
BUCK is the buck regulator gain.
C
OUT_OV = 33.4 µF and COUT_UV = 9 µF.
It is recommended to use two 22 µF ceramic capacitors.
To set the output voltage to 2.5 V, RTOP1 is set to 100 kΩ, giving
an RBOT1 value of 100 kΩ.
Rev. A | Page 22 of 31
Data Sheet
ADP5003
Figure 47 shows the load transient waveform.
DESIGNING THE COMPENSATION NETWORK FOR
THE BUCK REGULATOR
0.02A/µs
0.015A/µs
For better load transient and stability performance, set the cross
frequency, fC, to fSW/10. In this example, fSW is set to 600 kHz;
therefore, fC is set to 60 kHz.
I
LOAD2
2
3
4
2 × π × 44 μF × 60 kHz ×2.5
RC =
= 9.87 kΩ
= 3.72 nF
600 μS × 7 A/V
V
VOUT1
(
)
0.833 Ω + 0.001 Ω × 44 μF
V
CC =
PVOUT2
7.18 kΩ
0.001 Ω × 44 μF
= = 4.46 pF
CCP
7.18 kΩ
B
CH2 1.00A
CH4 20.0mV
CH3 200mV
M200µs
A CH2
1.08A
W
B
T
432.000µs
W
Choose standard components: RC = 9.76 kΩ, CC = 4.7 nF,
CP = 4.7 pF.
Figure 47. 0.6 A to 2.4 A Load Transient for 2.5 V Output, fSW = 0.6 MHz,
L = 3.3 μH, RC = 9.76 kΩ, CC = 4.7 nF, CCP = 4.7 pF, CPVOUT1 = 44 μF
C
SELECTING THE INPUT CAPACITOR FOR THE BUCK
REGULATOR
For the input capacitor, select a ceramic capacitor with a
minimum capacitance of 10 µF. Place the input capacitor close
to the PVIN1 pin. In this example, one 10 µF, X5R, 25 V
ceramic capacitor is recommended.
Rev. A | Page 23 of 31
ADP5003
Data Sheet
ADAPTIVE HEADROOM CONTROL DESIGN EXAMPLE
This section provides an example of the step by step design
procedures and the external components required for the buck
regulator using adaptive headroom control. Table 11 lists the
design requirements for this example.
SELECTING THE INDUCTOR FOR THE BUCK
REGULATOR USING ADAPTIVE HEADROOM
CONTROL
The peak-to-peak inductor ripple current, ΔIL, is set to 35% of
the maximum output current. Use the Equation 8 to estimate
the value of the inductor:
Table 11. Example Design Requirements for the Buck
Regulator Using Adaptive Headroom Control
Parameter
Specification
L = ((VPVIN1 – VPVOUT1) × D)/(ΔIL × fSW)
Input Voltage
VPVIN1 = 12 V
VPVOUT2 = 1.3 V
ILOAD1 = ILOAD2 = 3 A
1ꢀꢀ ꢁV at 2ꢀ% to 8ꢀ% load transient
where:
Output Voltage
Output Current
Buck Load Transient
V
V
V
V
PVIN1 = 12 V.
PVOUT1 = VPVOUT2 + VHR = 1.7 V.
PVOUT2 = 1.3 V.
HR is the adaptive headroom voltage at steady state current. See
SETTING THE SWITCHING FREQUENCY FOR THE
BUCK REGULATOR USING ADAPTIVE HEADROOM
CONTROL
Similar to the buck design example, a switching frequency of
600 kHz is used to achieve a good combination of small solution
size and high conversion efficiency. To set the switching frequency
to 600 kHz, use Equation 1 to calculate the resistor value, RRT:
Table 4 and Figure 25 for the approximate values of VHR vs. load
current. For this example, use VHR equal to 0.4 V for steady state
load current of 3 A.
D is the duty cycle (D = VVOUT1/VPVIN1).
ΔIL = 35% × 3 A = 1.05 A.
f
SW = 600 kHz.
The resulting value for L is 2.32 μH. The selected standard
inductor value is 2.2 μH; therefore, ΔIL is 1.1 A.
R
RT (kΩ) = 1.78 × 1011/fSW (kHz)
Therefore, select standard resistor RT = 294 kΩ.
To calculate the peak inductor current (IPEAK), use Equation 9:
SETTING THE OUTPUT VOLTAGE FOR THE LDO
REGULATOR USING ADAPTIVE HEADROOM
CONTROL
Select a value for the top feedback resistor (RTOP2) and then
calculate the bottom resistor (RBOT2) by using the following
equation:
I
PEAK = ILOAD1 + (ΔIL/2)
The calculated peak current for the inductor is 3.55 A.
SELECTING THE OUTPUT CAPACITORS FOR THE
BUCK REGULATOR USING ADAPTIVE HEADROOM
CONTROL
To ensure that the LDO regulator does not track the buck
output, the undershoot voltage must be set to a value less than
the minimum adaptive headroom voltage. Use Equation 17 and
Equation 18 to calculate the capacitance.
R
BOT2 = (RTOP2 × VPVOUT2)/((VREFOUT × ALDO) – VPVOUT2
)
(19)
where:
V
V
A
PVOUT2 is the LDO output voltage.
REFOUT is 2 V.
LDO is the LDO regulator gain.
For estimation purposes, use KOV = KUV = 2; therefore,
COUT_OV = 40.7 μF and COUT_UV = 6.92 μF.
To set the output voltage to 1.3 V, RTOP2 is set to 100 kΩ giving
an RBOT2 value of 65 kΩ.
It is recommended to use a single 47 μF ceramic capacitor for the
output of the buck and a single 10 μF for the output of the LDO.
Rev. A | Page 24 of 31
Data Sheet
ADP5003
DESIGNING THE COMPENSATION NETWORK FOR
THE BUCK REGULATOR USING ADAPTIVE
HEADROOM CONTROL
V
PVOUT1
4
Due to the addition of the adaptive headroom scheme in the
feedback loop, a lower bandwidth is required. Set the crossover
frequency, fC, to fSW/60. In this example, fSW is set to 600 kHz;
therefore, fC is set to 10 kHz.
0.02A/µs
0.013A/µs
I
LOAD1
1
2 × π × 47 μF ×10 kHz ×2.5
RC =
CC =
= 1.76 kΩ
= 15.2 nF
600 μS × 7 A/V
(
)
0.433 Ω + 0.001 Ω × 47 μF
B
CH1 1.00AB CH4 100mV
200µs
T
A CH3
1.38A
W
W
1.76 kΩ
508µs
0.001 Ω × 47 μF
Figure 48. 0.6 A to 2.4 A Load Transient for 2.5 V Output, fSW = 600 kHz,
L = 2.2 μH, RC = 1.74 kΩ, CC = 22 nF, CCP = 22 pF, CPVOUT1 = 47μF
CCP
= = 26.7 pF
1.76 kΩ
SELECTING THE INPUT CAPACITOR FOR THE BUCK
REGULATOR USING ADAPTIVE HEADROOM
CONTROL
Choose standard components: RC = 1.74 kΩ, CC = 22 nF,
CP = 22 pF.
Figure 48 shows the load transient waveform.
C
For the input capacitor, select a ceramic capacitor with a
minimum value of 10 µF. Place the input capacitor close to the
PVIN1 pin. In this example, one 10 µF, X5R, 25 V ceramic
capacitor is recommended.
Rev. A | Page 25 of 31
ADP5003
Data Sheet
RECOMMENDED EXTERNAL COMPONENTS FOR THE BUCK REGULATOR
Table 12 lists the recommended external components for buck applications up to 3 A operation (±±5 tolerance at an ~605 step transient),
and Table 13 lists the recommended buck external components for adaptive headroom applications up to 3 A operation (VPVOUT2
100 mV at an ~605 step transient).
±
Table 12. Recommended External Components for Buck Applications up to 3 A Operation ( 5% Tolerance at an ~60% Step Transient)
fSW (kHz)
300
VIN (V)
12
12
12
12
12
12
12
5
5
5
5
5
VOUT (V)
1
L (μH)
3.3
4.7
4.7
5.6
6.8
8.2
10
COUT (μF)
210
204.7
147
110
69
RTOP1 (kΩ)
200
150
174
150
100
49.9
0
200
150
174
150
100
49.9
150
150
100
49.9
0
200
150
174
150
100
49.9
100
49.9
0
200
150
174
150
100
49.9
RBOT1 (kΩ)
49.9
47.5
75
84.5
100
97.6
open
49.9
47.5
75
84.5
100
97.6
84.5
84.5
100
97.6
Open
49.9
47.5
75
84.5
100
97.6
100
97.6
Open
49.9
47.5
75
RC (kΩ)
23.7
23.2
16.5
12.4
7.68
5.23
3.01
23.7
16.5
14.7
10.5
5.23
5.76
15.4
15.4
7.15
6.04
4.99
21
CC (nF)
3.3
3.3
4.7
4.7
6.8
10
CCP (pF)
10
10
10
10
10
10
10
10
10
10
10
10
10
1.2
1.5
1.8
2.5
3.3
5
47
26.7
210
147
132
94
47
51.7
69
69
32
26.7
22
94
147
49.2
47
23
24.2
22
22
22
69
47
15
1
3.3
3.3
4.7
4.7
4.7
4.7
2.2
3.3
3.3
4.7
5.6
1.5
1.8
1.8
2.2
2.2
2.2
2.2
3.3
3.3
1
3.3
3.3
4.7
4.7
6.8
10
1.2
1.5
1.8
2.5
3.3
1.5
1.8
2.5
3.3
5
5
600
12
12
12
12
12
5
5
5
5
5
2.2
2.2
3.3
4.7
6.8
1.5
1.5
2.2
2.2
3.3
4.7
2.2
3.3
4.7
1
4.7
4.7
4.7
4.7
4.7
4.7
4.7
4.7
4.7
4.7
4.7
2.2
2.2
2.2
2.2
2.2
2.2
2.2
2.2
2.2
1
1.2
1.5
1.8
2.5
3.3
2.5
3.3
5
33.2
11
10.5
5.11
5.49
8.25
8.25
8.25
25.5
17.4
12.1
8.66
8.25
8.25
5
1000
12
12
12
5
5
5
5
5
5
1
1.2
1.5
1.8
2.5
3.3
1
1
1.2
1.2
1.5
1.2
32
23
22
22
1.5
1.5
2.2
3.3
84.5
100
97.6
Rev. A | Page 26 of 31
Data Sheet
ADP5003
Table 13. Recommended Buck External Components for Adaptive Headroom Applications up to 3 A Operation (VPVOUT2 100 mV
at an ~60% Step Transient)
fSW (kHz)
600
VIN (V)
VOUT2 (V)
3.3
2.5
1.8
1.3
1.1
3.3
2.5
L (µH)
4.7
3.3
3.3
2.2
1.8
1.5
1.8
COUT1 (µF)
RC (kΩ)
1.74
1.65
2.15
1.74
1.74
1.65
1.21
1.21
1.65
1.65
CC (nF)
33
22
22
22
10
33
22
CCP (pF)
22
22
22
22
22
22
22
RTOP2 (kΩ)
Short
37.4
100
100
100
Short
37.4
100
100
RBOT2 (kΩ)
Open
118
121
64.9
49.9
Open
118
121
64.9
COUT2 (µF)
12
12
12
12
12
5
5
5
5
5
47
44
57
47
47
44
32
32
44
44
10
10
10
10
10
10
10
10
10
10
1.8
1.3
1.1
1.8
1.8
1.5
22
22
10
22
22
22
100
49.9
Rev. A | Page 27 of 31
ADP5003
Data Sheet
BUCK CONFIGURATIONS
80
70
INDEPENDENT
The buck and LDO regulators can operate independently of
each other (see Figure 50) to provide two voltage rails from a
single supply. In this way, the buck regulator can provide an
intermediate supply rail for the LDO regulator with a fixed
headroom voltage between the buck output voltage and the
LDO output voltage. The LDO regulator acts to filter the voltage
ripple and switching noise generated by the buck regulator for
noise sensitive supplies. Where additional filtering is required, a
second stage LC filter can be added between the buck output
and the LDO input. Because the regulators are independently
operated to provide a single voltage rail, the PSRR and efficiency
can be configured as required by the application by either
setting a lower headroom voltage for greater efficiency or a
higher headroom voltage for greater PSRR.
60
50
40
30
20
10
0
ADAPTIVE HEADROOM CONTROL
INDEPENDENT, 150mV HEADROOM
INDEPENDENT, 500mV HEADROOM
0
0.5
1.0
1.5
2.0
2.5
3.0
LOAD CURRENT (A)
Figure 49. Efficiency vs. Load Current for
Different Operating Modes
VPVIN1: 12V
PVIN1
EN1
CPVIN1
10µF
VOUT1
SW1
CC
4.7nF
RC
9.76kΩ
L1
3.3µH
COMP1
VSET1
BUCK
REGULATOR
3A
V
= 2.5V
PVOUT1
CPVOUT1
44µF
RBOT1
100kΩ
PGND1
RTOP1
100kΩ
CVREG
1µF
RRT
294kΩ
VREG
RT
VPVINSYS: 12V
PVINSYS
CPVINSYS
PWRGD
SYNC
SYSTEM
ANALOG DEVICES
RF TRANSCEIVER,
HIGH SPEED
ADC/DAC, CLOCK,
ASIC/PROCESSOR
10µF
REFOUT
CREFOUT
0.22µF
RTOP2
100kΩ
PVIN2
VSET2
CPVIN2
10µF
RBOT2
64.9kΩ
VBUF
LOW NOISE
LDO ACTIVE
FILTER
V
= 1.3V
PVOUT2
CPVOUT2
CVBUF
0.1µF
PVOUT2
3A
VREG_LDO
10µF
CVREG_LDO
1µF
VFB2P
VFB2N
EN2
AGND1
AGND2
Figure 50. Independent Configuration (Dual Output)
Rev. A | Page 28 of 31
Data Sheet
ADP5003
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
0.2V, 1A
LDO PSRR
= 12V, V
ADAPTIVE HEADROOM
0.28V, 1.5A
0.35V, 2A
0.4V, 2.5A
0.4V, 3A
V
= 0.9V
PVOUT2
PVIN1
The ADP5003 features a scheme to control the buck regulator
output voltage and thus the LDO headroom voltage to provide
better efficiency with the same noise performance of a standalone
LDO regulator. When the buck regulator uses the adaptive
headroom control configuration, the ADP5003 manages the
buck regulator output voltage vs. the LDO load current (see
Figure 25). The adaptive headroom control also optimizes the
LDO headroom when the remote sense feedback corrects any
output voltage drop due to additional filtering or high trace
impedance under high load conditions. The headroom profile
of the adaptive headroom control is set to deliver a consistent
PSRR across the load range while optimizing efficiency of the
overall system (see Figure 51). To enable adaptive headroom
control, connect VSET1 to VREG (see Figure 52).
1
10
100
1k
10k
100k
1M
10M
FREQUENCY (Hz)
Figure 51. LDO PSRR vs. Frequency
VPVIN1: 12V
PVIN1
PVIN1
CPVIN1
10µF
EN1
VOUT1
SW1
CC
2.2nF
RC
1.74kΩ
L1
2.2µH
V
PVOUT1
COMP1
VSET1
BUCK
REGULATOR
3A
(ADAPTIVE)
SW1
SW1
CPVOUT1
47µF
PGND1
PGND1
PGND1
CVREG
1µF
VREG
RRT
294kΩ
RT
VPVINSYS: 12V
PVINSYS
PWRGD
SYNC
SYSTEM
CPVINSYS
10µF
REFOUT
CREFOUT
0.22µF
RTOP2
100kΩ
PVIN2
PVIN2
PVIN2
VSET2
VBUF
CPVIN2
10µF
CVBUF
0.1µF
RBOT2
64.9kΩ
PVOUT2
PVOUT2
PVOUT2
LOW NOISE
LDO ACTIVE
FILTER
V
= 1.3V
VPOUT2
ANALOG DEVICES
RF TRANSCEIVER,
HIGH SPEED ADC/DAC,
CLOCK, ASIC/
CPVOUT2
10µF
3A
VREG_LDO
CVREG_LDO
1µF
EN2
PROCESSOR
VFB2P
VFB2N
AGND1
AGND2
Figure 52. Adaptive Headroom Configuration
Rev. A | Page 29 of 31
ADP5003
Data Sheet
LAYOUT CONSIDERATIONS
Layout is important for all switching regulators but is
particularly important for regulators with high switching
frequencies. To achieve high efficiency, proper regulation,
stability, and low noise, a well designed PCB layout is required.
Follow these guidelines when designing PCBs:
of load. Keep them as short as possible and away from
noise sources.
•
•
Place the frequency setting resistor close to the RT pin.
Keep AGND1 and PGND1 separate on the top layer of the
board. This separation avoids pollution of AGND1 with
switching noise. Do not connect PGND1 to the EPAD on
the top layer of the layout. Connect both AGND1 and
PGND1 to the board ground plane with vias. Ideally,
connect PGND1 to the plane at a point between the input
and output capacitors.
•
Keep high current loops as short and wide as possible.
•
Keep the input bypass capacitors close to the PVIN1,
PVIN2, and PVINSYS pins.
•
Keep the inductor and output capacitor close to SW1
and PGND1.
Connect the negative terminal of CVBUF to the VFB2N pin.
•
Route the VFB2P and VFB2N LDO sense traces side by
side connecting them each as close as possible to the point
13.2mm
L1
PVIN
C
PVINSYS
10µF
C
PVIN1
10µF
50V/X5R
1206
35V/X5R
0805
C
VREG
1µF
C
VOUT1
10V/X5R
0406
22µF
25V/X5R
1206
R
0201
RT
24
1
C
C
2
3
23
22
21
0402
R
C
4
5
0402
ADP5003
20
19
18
17
R
R
C
TOP1
BOT1 CP
6
7
8
0201
C
REFOUT
0.22µF
10V/X5R
0402
C
PVIN2
0201
10µF
50V/X5R
1206
R
R
TOP2
BOT2
C
1µF
PVOUT2
VREG_LDO
10V/X5R
0402
C
PVOUT2
10µF
25V/X5R
0805
C
0.1µF
VBUF
10V/X5R
0402
Figure 53. Example Outline Layout
Rev. A | Page 30 of 31
Data Sheet
ADP5003
OUTLINE DIMENSIONS
DETAIL A
(JEDEC 95)
5.10
5.00 SQ
4.90
0.30
0.25
0.18
PIN 1
INDICATOR
PIN 1
25
32
INDIC ATOR AREA OPTIONS
(SEE DETAIL A)
24
1
0.50
BSC
3.25
3.10 SQ
2.95
EXPOSED
PAD
17
8
9
16
0.50
0.40
0.30
0.20 MIN
BOTTOM VIEW
TOP VIEW
SIDE VIEW
0.80
0.75
0.70
FOR PROPER CONNECTION OF
THE EXPOSED PAD, REFER TO
THE PIN CONFIGURATION AND
FUNCTION DESCRIPTIONS
0.05 MAX
0.02 NOM
COPLANARITY
0.08
SECTION OF THIS DATA SHEET.
SEATING
PLANE
0.20 REF
COMPLIANT TO JEDEC STANDARDS MO-220-WHHD
Figure 54. 32-Lead Lead Frame Chip Scale Package [LFCSP]
5 mm × 5 mm Body and 0.75 mm Package Height
(CP-32-7)
Dimensions shown in millimeters
ORDERING GUIDE
Model1
ADP5003ACPZ-R7
ADP5003CP-EVALZ
Temperature Range
−40°C to +125°C
Package Description
32-Lead Lead Frame Chip Scale Package [LFCSP]
Evaluation Board
Package Option
CP-32-7
1 Z = RoHS Compliant Part.
©2017–2019 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
D15021-0-3/19(A)
Rev. A | Page 31 of 31
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