ADL5504ACBZ-P2 [ADI]
450 MHz to 6000 MHz TruPwr Detector; 450 MHz至6000 MHz的TruPwr检测器
| 型号： | ADL5504ACBZ-P2 |
| 厂家： | 
ADI |
| 描述： | 450 MHz to 6000 MHz TruPwr Detector |
| 文件： | 总24页 (文件大小：1470K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
450 MHz to 6000 MHz
TruPwr Detector
ADL5504
FEATURES
FUNCTIONAL BLOCK DIAGRAM
VPOS
True rms response detector
Excellent temperature stability
ADL5504
INTERNAL
FILTERING
ENBL
RFIN
1kΩ
0.2ꢀ dB rms detection accuracy vs. temperature
Over 3ꢀ dB input power dynamic range, inclusive of crest factor
RF bandwidths from 4ꢀ0 MHz to 6000 MHz
ꢀ00 Ω input impedance
FLTR
100Ω
RMS CORE
VRMS
BUFFER
Single-supply operation: 2.ꢀ V to 3.3 V
Low power: 1.8 mA at 3.0 V supply
RoHS compliant part
COMM
Figure 1.
APPLICATIONS
Power measurement of W-CDMA, CDMA2000, QPSK-/QAM-
based OFDM (LTE and WiMAX), and other complex
modulation waveforms
10
RF transmitter or receiver power measurement
1
0.1
0.01
–25
–20
–15
–10
–5
0
5
10
15
INPUT (dBm)
Figure 2. Output vs. Input Level, 3 V Supply, Frequency 1900 MHz
GENERAL DESCRIPTION
The ADL5504 is a TruPwr™ mean-responding (true rms) power
detector for use in high frequency receiver and transmitter signal
chains from 450 MHz to 6000 MHz. Requiring only a single
supply between 2.5 V and 3.3 V, the detector draws less than
1.8 mA. The input is internally ac-coupled and has a nominal
input impedance of 500 Ω. The rms output is a linear-responding
dc voltage with a conversion gain of 1.87 V/V rms at 900 MHz.
The on-chip modulation filter provides adequate averaging for
most waveforms. For more complex waveforms, an external
capacitor at the FLTR pin can be used for supplementary signal
demodulation. An on-chip, 100 Ω series resistance at the output,
combined with an external shunt capacitor, creates a low-pass filter
response that reduces the residual ripple in the dc output voltage.
The ADL5504 offers excellent temperature stability across a
30 dB range and near 0 dB measurement error across temperature
over the top portion of the dynamic range. In addition to its
temperature stability, the ADL5504 offers low process variations
that further reduce calibration complexity.
The ADL5504 is a highly accurate, easy to use means of
determining the rms of complex waveforms. It can be used for
power measurements of both simple and complex waveforms
but is particularly useful for measuring high crest factor (high
peak-to-rms ratio) signals, such as W-CDMA, CDMA2000,
WiMAX, WLAN, and LTE waveforms.
The power detector operates from −40°C to +85°C and is
available in a 6-ball, 0.8 mm × 1.2 mm, wafer level chip scale
package. It is fabricated on a high fT silicon BiCMOS process.
Rev. 0
Information furnished by Analog Devices is believed to be accurate and reliable. However, no
responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other
rights of third parties that may result from its use. Specifications subject to change without notice. No
license is granted by implication or otherwise under any patent or patent rights of Analog Devices.
Trademarks and registeredtrademarks arethe property of their respective owners.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781.329.4700
Fax: 781.461.3113
www.analog.com
©2009 Analog Devices, Inc. All rights reserved.
ADL5504
TABLE OF CONTENTS
Features .............................................................................................. 1
RF Input Interfacing................................................................... 14
Linearity....................................................................................... 15
Output Drive Capability and Buffering................................... 16
Applications....................................................................................... 1
Functional Block Diagram .............................................................. 1
General Description......................................................................... 1
Revision History ............................................................................... 2
Specifications..................................................................................... 3
Absolute Maximum Ratings............................................................ 6
ESD Caution.................................................................................. 6
Pin Configuration and Function Descriptions............................. 7
Typical Performance Characteristics ............................................. 8
Circuit Description......................................................................... 13
RMS Circuit Description and Filtering ................................... 13
Filtering........................................................................................ 13
Output Buffer.............................................................................. 13
Applications Information .............................................................. 14
Basic Connections...................................................................... 14
Selecting the Square-Domain Filter and Output Low-Pass
Filter ............................................................................................. 16
Power Consumption, Enable, and Power-On/Power-Off
Response Time............................................................................ 17
Device Calibration and Error Calculation.............................. 17
Calibration for Improved Accuracy......................................... 18
Drift over a Reduced Temperature Range .............................. 19
Device Handling......................................................................... 19
Evaluation Board........................................................................ 20
Outline Dimensions....................................................................... 22
Ordering Guide .......................................................................... 22
REVISION HISTORY
10/09—Revision 0: Initial Version
Rev. 0 | Page 2 of 24
ADL5504
SPECIFICATIONS
TA = 25°C, VS = 3.0 V, CFLTR = 10 nF, COUT = open, light condition ≤ 600 lux, 75 Ω input termination resistor, unless otherwise noted.
Table 1.
Parameter
Test Conditions
Input RFIN
Min
Typ
Max
Unit
FREQUENCY RANGE
RF INPUT (f = 450 MHz)
Input Impedance
RMS Conversion
450
6000
MHz
Input RFIN to output VRMS
No termination
520||1.00
Ω||pF
Dynamic Range1
Continuous wave (CW) input, −40°C < TA < +85°C
Delta from 25°C
0.25 dꢀ Error 2
25
16
35
39
dꢀ
dꢀ
dꢀ
dꢀ
dꢀm
dꢀm
V/V rms
V
0.25 dꢀ Error 3
1 dꢀ Error3
2 dꢀ Error3
Maximum Input Level
Minimum Input Level
Conversion Gain
Output Intercept4
Output Voltage, High Input Power
Output Voltage, Low Input Power
Temperature Sensitivity
0.25 dꢀ error3
1 dꢀ error3
VRMS = (gain × VIN) + intercept
15
−21
1.90
0.003
0.760
0.077
PIN = 5 dꢀm, 400 mV rms
PIN = −15 dꢀm, 40 mV rms
PIN = 0 dꢀm
25°C < TA < 85°C
0.0027
0.0024
dꢀ/°C
dꢀ/°C
−40°C < TA < +25°C
Input RFIN to output VRMS
No termination
RF INPUT (f = 900 MHz)
Input Impedance
RMS Conversion
370||0.80
Ω||pF
Dynamic Range1
CW input, −40°C < TA < +85°C
Delta from 25°C
0.25 dꢀ Error2
27
dꢀ
0.25 dꢀ Error3
17
dꢀ
1 dꢀ Error3
35
dꢀ
2 dꢀ Error3
39
dꢀ
Maximum Input Level
Minimum Input Level
Conversion Gain
0.25 dꢀ error3
1 dꢀ error3
VRMS = (gain × VIN) + intercept
15
−22
1.87
dꢀm
dꢀm
V/V rms
V
1.6
2.2
+0.1
Output Intercept4
Output Voltage, High Input Power
Output Voltage, Low Input Power
Temperature Sensitivity
−0.1 +0.004
0.746
PIN = 5 dꢀm, 400 mV rms
PIN = −15 dꢀm, 40 mV rms
PIN = 0 dꢀm
V
0.077
V
25°C < TA < 85°C
−40°C < TA < +25°C
0.0024
0.0018
dꢀ/°C
dꢀ/°C
Rev. 0 | Page 3 of 24
ADL5504
Parameter
Test Conditions
Min
Typ
Max
Unit
RF INPUT (f = 1900 MHz)
Input Impedance
RMS Conversion
Input RFIN to output VRMS
No termination
260||0.68
Ω||pF
Dynamic Range1
CW input, −40°C < TA < +85°C
Delta from 25°C
0.25 dꢀ Error2
20
15
35
40
dꢀ
dꢀ
dꢀ
dꢀ
dꢀm
dꢀm
V/V rms
V
V
V
0.25 dꢀ Error3
1 dꢀ Error3
2 dꢀ Error3
Maximum Input Level
Minimum Input Level
Conversion Gain
Output Intercept4
Output Voltage, High Input Power
Output Voltage, Low Input Power
Temperature Sensitivity
0.25 dꢀ error3
1 dꢀ error3
VRMS = (gain × VIN) + intercept
15
−22
1.82
0.001
0.719
0.072
PIN = 5 dꢀm, 400 mV rms
PIN = −15 dꢀm, 40 mV rms
PIN = 0 dꢀm
25°C < TA < 85°C
0.0016
0.0070
dꢀ/°C
dꢀ/°C
−40°C < TA < +25°C
Input RFIN to output VRMS
No termination
RF INPUT (f = 2600 MHz)
Input Impedance
RMS Conversion
240||0.61
Ω||pF
Dynamic Range1
CW input, −40°C < TA < +85°C
Delta from 25°C
0.25 dꢀ Error2
13
dꢀ
0.25 dꢀ Error3
10
dꢀ
1 dꢀ Error3
35
dꢀ
2 dꢀ Error3
40
dꢀ
Maximum Input Level
Minimum Input Level
Conversion Gain
0.25 dꢀ error3
1 dꢀ error3
VRMS = (gain × VIN) + intercept
15
dꢀm
dꢀm
V/V rms
V
V
V
−22
1.79
−0.003
0.702
0.069
Output Intercept4
Output Voltage, High Input Power
Output Voltage, Low Input Power
Temperature Sensitivity
PIN = 5 dꢀm, 400 mV rms
PIN = −15 dꢀm, 40 mV rms
PIN = 0 dꢀm
25°C < TA < 85°C
0.0031
0.0046
dꢀ/°C
dꢀ/°C
−40°C < TA < +25°C
Input RFIN to output VRMS
No termination
RF INPUT (f = 3500 MHz)
Input Impedance
RMS Conversion
200||0.50
Ω||pF
Dynamic Range1
CW input, −40°C < TA < +85°C
Delta from 25°C
0.25 dꢀ Error2
6
dꢀ
0.25 dꢀ Error3
5
dꢀ
1 dꢀ Error3
34
dꢀ
2 dꢀ Error3
40
dꢀ
Maximum Input Level
Minimum Input Level
Conversion Gain
0.25 dꢀ error3
1 dꢀ error3
VRMS = (gain × VIN) + intercept
13
dꢀm
dꢀm
V/V rms
V
V
V
−21
1.65
−0.006
0.639
0.060
Output Intercept4
Output Voltage, High Input Power
Output Voltage, Low Input Power
Temperature Sensitivity
PIN = 5 dꢀm, 400 mV rms
PIN = −15 dꢀm, 40 mV rms
PIN = 0 dꢀm
25°C < TA < 85°C
−40°C < TA < +25°C
0.0037
0.0074
dꢀ/°C
dꢀ/°C
Rev. 0 | Page 4 of 24
ADL5504
Parameter
Test Conditions
Min
Typ
Max
Unit
RF INPUT (f = 6000 MHz)
Input Impedance
Input RFIN to output VRMS
No termination
90||0.31
Ω||pF
RMS Conversion
Dynamic Range1
CW input, −40°C < TA < +85°C
1 dꢀ Error3
25
dꢀ
2 dꢀ Error3
34
dꢀ
Maximum Input Level
Minimum Input Level
Conversion Gain
0.25 dꢀ error3
1 dꢀ error3
VRMS = (gain × VIN) + intercept
12
dꢀm
dꢀm
V/V rms
V
V
V
−16
0.82
-0.005
0.314
0.027
Output Intercept4
Output Voltage, High Input Power
Output Voltage, Low Input Power
Temperature Sensitivity
PIN = 5 dꢀm, 400 mV rms
PIN = −15 dꢀm, 40 mV rms
PIN = 0 dꢀm
25°C < TA < 85°C
−40°C < TA < +25°C
Pin VRMS
0.0108
0.0120
dꢀ/°C
dꢀ/°C
VRMS OUTPUT
Output Offset
No signal at RFIN
VS = 3.0 V, RLOAD ≥ 10 kΩ
10
2.5
3
100
mV
V
mA
μs
Maximum Output Voltage
Available Output Current
Pulse Response Time
10 dꢀ step, 10% to 90% of settling level, no filter
capacitor
3
ENAꢀLE INTERFACE
Pin ENꢀL
Logic Level to Enable Power, High Condition
Input Current when High
Logic Level to Disable Power, Low Condition
Power-Up Response Time5
2.5 V ≤ VS ≤ 3.3 V, −40°C < TA < +85°C
2.5 V at ENꢀL, –40°C < TA < +85°C
2.5 V ≤ VS ≤ 3.3 V, −40°C < TA < +85°C
CFLTR = open, 0 dꢀm at RFIN
CFLTR = 10 nF, 0 dꢀm at RFIN
1.8
VPOS
0.1
+0.5
V
μA
V
μs
μs
0.05
−0.5
1
8
POWER SUPPLIES
Operating Range
Quiescent Current6
Disable Current7
−40°C < TA < +85°C
No signal at RFIN, ENꢀL high input condition
ENꢀL input low condition
2.5
3.3
1
V
mA
μA
1.8
0.1
1 The available output swing and, therefore, the dynamic range are altered by the supply voltage; see Figure 8.
2 Error referred to delta from 25°C response; see Figure 13 to Figure 15 and Figure 19 to Figure 21.
3 Error referred to best-fit line at 25°C; see Figure 10 to Figure 12 and Figure 16 to Figure 18.
4 Calculated using linear regression.
5 The response time is measured from 10% to 90% of settling level; see Figure 31 to Figure 33.
6 Supply current is input level-dependent; see Figure 27.
7 Guaranteed but not tested; limits are specified at six sigma levels.
Rev. 0 | Page 5 of 24
ADL5504
ABSOLUTE MAXIMUM RATINGS
Table 2.
Stresses above those listed under Absolute Maximum Ratings
may cause permanent damage to the device. This is a stress
rating only; functional operation of the device at these or any
other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute
maximum rating conditions for extended periods may affect
device reliability.
Parameter
Rating
Supply Voltage, VS
3.5 V
VRMS, ENꢀL
0 V to VS
RFIN
1.25 V rms
15 dꢀm
150 mW
260°C/W
125°C
−40°C to +85°C
−65°C to +150°C
Equivalent Power, Referred to 50 Ω
Internal Power Dissipation
θJA (WLCSP)
Maximum Junction Temperature
Operating Temperature Range
Storage Temperature Range
ESD CAUTION
Rev. 0 | Page 6 of 24
ADL5504
PIN CONFIGURATION AND FUNCTION DESCRIPTIONS
FLTR
VPOS
RFIN
1
2
3
6
5
4
ENBL
VRMS
COMM
ADL5504
TOP VIEW
(BALL SIDE DOWN)
Not to Scale
Figure 3. Pin Configuration
Table 3. Pin Function Descriptions
Pin No. Mnemonic Description
1
2
3
FLTR
VPOS
RFIN
Modulation Filter. Connect an external capacitor to this pin to lower the corner frequency of the modulation filter.
Supply Voltage. The operational range is 2.5 V to 3.3 V.
Signal Input. This pin is internally ac-coupled after internal termination resistance. The nominal input impedance
is 500 Ω.
4
5
COMM
VRMS
Device Ground.
RMS Output. This pin is a rail-to-rail voltage output with limited current drive capability. The output has an internal
100 Ω series resistance. High resistive loads and low capacitance loads are recommended to preserve output swing
and allow fast response.
6
ENꢀL
Enable. Connect this pin to VS for normal operation. Connect this pin to ground for disable mode.
Rev. 0 | Page 7 of 24
ADL5504
TYPICAL PERFORMANCE CHARACTERISTICS
TA = 25°C, VS = 3.0 V, CFLTR = 10 nF, COUT = open, light condition ≤ 600 lux, 75 Ω input termination resistor; colors: black = +25°C,
blue = −40°C, red = +85°C; unless otherwise noted.
3
10
2
1
1
0
0.1
0.01
–1
–2
–3
450
450
900
900
1900
2600
3500
5000
6000
1900
2600
3500
5000
6000
–25
–20
–15
–10
–5
0
5
10
15
–25
–20
–15
–10
–5
0
5
10
15
INPUT (dBm)
INPUT (dBm)
Figure 4. Output vs. Input Level, 450 MHz, 900 MHz, 1900 MHz, 2600 MHz,
3500 MHz, 5000 MHz, 6000 MHz Frequencies, 3.0 V Supply
Figure 7. Linearity Error vs. Input Level, 450 MHz, 900 MHz, 1900 MHz,
2600 MHz, 3500 MHz, 5000 MHz, 6000 MHz Frequencies, 3.0 V Supply
2.0
10
450
900
1.8
1900
2600
1.6
1.4
1.2
1.0
0.8
0.6
0.4
0.2
0
3500
5000
6000
1
0.1
2.5V
2.7V
3.0V
3.3V
0.01
–25
0
0.1
0.2
0.3
0.4
0.5
0.6
0.7
0.8
0.9
1.0
–20
–15
–10
–5
0
5
10
15
INPUT (dBm)
INPUT (V rms)
Figure 5. Outputvs. InputLevel(Linear Scale), 450 MHz, 900 MHz, 1900 MHz,
2600 MHz, 3500 MHz, 5000 MHz, 6000 MHz Frequencies, 3.0VSupply
Figure 8. Output vs. Input Level, 900 MHz Frequency,
2.5 V, 2.7 V, 3.0 V, and 3.3 V Supplies
2.5
2.0
1.5
1.0
100
700
600
500
400
300
200
100
0
1.4
1.2
1.0
0.8
0.6
0.4
0.2
0
80
60
SHUNT CAPACITANCE
SHUNT RESISTANCE
40
0.5
0
20
0
0
1k
2k
3k
4k
5k
6k
0.5
1.0
1.5
2.0
2.5
3.0
FREQUENCY (MHz)
FREQUENCY (GHz)
Figure 6. Conversion Gain and Intercept vs. Frequency, 3.0 V Supply
at −40°C, +25°C, and +85°C
Figure 9. Input Impedance vs. Frequency, 3.0 V Supply,
at −40°C, +25°C, and +85°C
Rev. 0 | Page 8 of 24
ADL5504
3
2
3
2
1
1
0
0
–1
–2
–3
–1
–2
–3
–25
–20
–15
–10
–5
0
5
10
15
–25
–20
–15
–10
–5
0
5
10
15
15
15
INPUT (dBm)
INPUT (dBm)
Figure 10. Output Temperature Drift from +25°C Linear Reference
for 50 Devices at −40°C, +25°C, and +85°C, 450 MHz Frequency
Figure 13. Output Delta from +25°C Output Voltage for
50 Devices at −40°C and +85°C, 450 MHz Frequency
3
3
2
2
1
1
0
0
–1
–2
–3
–1
–2
–3
–25
–20
–15
–10
–5
0
5
10
15
–25
–20
–15
–10
–5
0
5
10
INPUT (dBm)
INPUT (dBm)
Figure 11. Output Temperature Drift from +25°C Linear Reference
for 50 Devices at −40°C, +25°C, and +85°C, 900 MHz Frequency
Figure 14. Output Delta from +25°C Output Voltage for
50 Devices at −40°C and +85°C, 900 MHz Frequency
3
3
2
2
1
1
0
0
–1
–2
–3
–1
–2
–3
–25
–20
–15
–10
–5
0
5
10
15
–25
–20
–15
–10
–5
0
5
10
INPUT (dBm)
INPUT (dBm)
Figure 12. Output Temperature Drift from +25°C Linear Reference
for 50 Devices at −40°C, +25°C, and +85°C, 1900 MHz Frequency
Figure 15. Output Delta from +25°C Output Voltage for
50 Devices at −40°C and +85°C, 1900 MHz Frequency
Rev. 0 | Page 9 of 24
ADL5504
3
3
2
2
1
1
0
0
–1
–2
–1
–2
–3
–3
–25
–20
–15
–10
–5
0
5
10
15
–25
–20
–15
–10
–5
0
5
10
15
15
15
INPUT (dBm)
INPUT (dBm)
Figure 16. Output Temperature Drift from +25°C Linear Reference
for 50 Devices at −40°C, +25°C, and +85°C, 2600 MHz Frequency
Figure 19. Output Delta from +25°C Output Voltage for
50 Devices at −40°C and +85°C, 2600 MHz Frequency
3
3
2
2
1
1
0
0
–1
–2
–3
–1
–2
–3
–25
–20
–15
–10
–5
0
5
10
15
–25
–20
–15
–10
–5
0
5
10
INPUT (dBm)
INPUT (dBm)
Figure 17. Output Temperature Drift from +25°C Linear Reference
for 50 Devices at −40°C, +25°C, and +85°C, 3500 MHz Frequency
Figure 20. Output Delta from +25°C Output Voltage for
50 Devices at −40°C and +85°C, 3500 MHz Frequency
3
3
2
2
1
1
0
0
–1
–2
–3
–1
–2
–3
–25
–20
–15
–10
–5
0
5
10
15
–25
–20
–15
–10
–5
0
5
10
INPUT (dBm)
INPUT (dBm)
Figure 18. Output Temperature Drift from +25°C Linear Reference
for 50 Devices at −40°C, +25°C, and +85°C, 6000 MHz Frequency
Figure 21. Output Delta from +25°C Output Voltage for
50 Devices at −40°C and +85°C, 6000 MHz Frequency
Rev. 0 | Page 10 of 24
ADL5504
3
2
3
2
CW
CW
dB, 15kSPS) + DPDCHꢀ
dB, 15kSPS) + DPDCHꢀ
PICH, 4.7dB
12.2kbps, DPCCH (–5.46
(0dB, 60kSPS), 3.4dB CF
PICH + FCH (9.6kbps), 4.8dB CF
PICH + FCH (9.6kbps) + DCCH, 6.3dB CF
PICH + FCH (9.6kbps) + SCH (153.6kbps), 6.7dB
144kbps, DPCCH (–11.48
(0dB, 480kSPS), 3.3dB CF
, 15kSPS) + DPDCH1 + 2ꢀ
768kbps, DPCCH (–11.48dB
(0dB, 960kSPS), 5.8dB CF
PICH + FCH (9.6kbps) + DCCH +SCH (153.6kbps), 7.6dB CF
1
1
0
0
–1
–2
–3
–1
–2
–3
DPCCH (–6.02dB, 15kSPS) + DPDCH (–4.08dB, 60kSPS) +
HS-DPCCH (0dB, 15kSPS), 4.91dB CFDPCCH (–6.02dB,
15kSPS) + DPDCH (–11.48dB, 60kSPS) + HS-DPCCH (0dB,
15kSPS), 5.34dB CF
DPCCH (–6.02dB, 15kSPS) + HS-DPCCH (0dB, 15kSPS),
5.44dB CF
–25
–20
–15
–10
–5
0
5
10
15
–25
–20
–15
–10
INPUT (dBm)
–5
0
5
10
15
INPUT (dBm)
Figure 22. Error from CW Linear Reference vs. Input with Various
Figure 25. Error from CW Linear Reference vs. Input with Various
W-CDMA Reverse Link Waveforms at 900 MHz, CFLTR = 10 nF, COUT = Open
CDMA2000 Reverse Link Waveforms at 1900 MHz, CFLTR = 12 nF, COUT = Open
3
3
CW
CW
16QAM RB1
16QAM RB10
TEST MODEL 1 WITH 16 DPCH, 1 CARRIER
TEST MODEL 1 WITH 32 DPCH, 1 CARRIER
16QAM RB100
QPSK RB1
QPSK RB10
QPSK RB100
2
2
1
TEST MODEL 1 WITH 64 DPCH, 1 CARRIER
TEST MODEL 1 WITH 64 DPCH, 2 CARRIERS
TEST MODEL 1 WITH 64 DPCH, 3 CARRIERS
TEST MODEL 1 WITH 64 DPCH, 4 CARRIERS
1
0
0
–1
–2
–3
–1
–2
–3
–25
–20
–15
–10
–5
0
5
10
15
–25
–20
–15
–10
–5
0
5
10
15
INPUT (dBm)
INPUT (dBm)
Figure 23. Error from CW Linear Reference vs. Input with Various
W-CDMA Forward Link Waveforms at 2200 MHz, CFLTR = 10 nF, COUT = Open
Figure 26. Error from CW Linear Reference vs. Input with Various
LTE Reverse Link Waveforms at 2600 MHz, CFLTR = 12 nF, COUT = Open
3
15
14
13
12
11
10
9
CW
BPSK, 11dB CF
QPSK, 11dB CF
2
16QAM, 12dB CF
64QAM, 11dB CF
1
8
0
–1
–2
–3
7
2.5V
6
5
4
3
2
1
0
–25
–20
–15
–10
–5
0
5
10
15
0
1
.0
0.1
0.2
0.3
0.4
0.5
0.6
0.7
0.8
0.9
INPUT (dBm)
INPUT (V rms)
Figure 24. Error from CW Linear Reference vs. Input with Various
802.16 OFDM Waveforms at 3500 MHz, 10 MHz Signal BW, and
256 Subcarriers for All Modulated Signals, CFLTR = 10 nF, COUT = Open
Figure 27. Supply Current vs. Input Level, 2.5 V, 3.0 V, and 3.3 V Supplies,
900 MHz Frequency, at −40°C, +25°C, and +85°C
Rev. 0 | Page 11 of 24
ADL5504
PULSED RFIN
ENBL
400mV rms RF INPUT
250mV rms
400mV rms RF INPUT
250mV rms
160mV rms
160mV rms
70mV rms
70mV rms
4µs/DIV
2µs/DIV
Figure 28. Output Response to Various RF Input Pulse Levels, 3.0 V Supply,
900 MHz Frequency, CFLTR = Open, COUT = Open, ROUT = Open
Figure 31. Output Response to Enable Gating at Various RF Input Levels,
3.0 V Supply, 900 MHz Frequency, CFLTR = Open, COUT = Open, ROUT = Open
ENBL
PULSED RFIN
400mV rms RF INPUT
400mV rms RF INPUT
250mV rms
250mV rms
10µs/DIV
4µs/DIV
Figure 29. Output Response to Various RF Input Pulse Levels, 3.0 V Supply,
900 MHz Frequency, CFLTR = 10 nF, COUT = Open, ROUT = Open
Figure 32. Output Response to Enable Gating at Various RF Input Levels,
3.0 V Supply, 900 MHz Frequency, CFLTR = 10 nF, COUT = Open, ROUT = Open
ENBL
PULSED RFIN
400mV rms RF INPUT
400mV rms RF INPUT
10µs/DIV
10µs/DIV
Figure 33. Output Response to Enable Gating at Various RF Input Levels,
3.0 V Supply, 900 MHz Frequency, CFLTR =Open, COUT = 10 nF, ROUT = 1 kΩ
Figure 30. Output Response to Various RF Input Pulse Levels, 3.0 V Supply,
900 MHz Frequency, CFLTR =Open, COUT = 10 nF, ROUT = 1 kΩ
Rev. 0 | Page 12 of 24
ADL5504
CIRCUIT DESCRIPTION
The ADL5504 employs two-stage detection. The critical aspect
of this technical approach is the concept of first stripping the
carrier to reveal the envelope and then performing the required
analog computation of rms.
For improved accuracy with more complex RF waveforms
(with modulation components extending down into the
kilohertz region), more filtering is necessary to supplement
the on-chip, low-pass filter. For this reason, the FLTR pin is
provided; a capacitor attached between this pin and VPOS
can extend the averaging time to very low frequencies (see
the Selecting the Square-Domain Filter and Output Low-Pass
Filter section). Any external capacitor acts on a 1 kΩ resistor to
yield a new corner frequency for the rms filter (see Figure 1).
RMS CIRCUIT DESCRIPTION AND FILTERING
The rms processing is executed using a proprietary translinear
technique. This method is a mathematically accurate rms
computing approach and allows achieving unprecedented rms
accuracies for complex modulation signals irrespective of the
crest factor of the input signal. An integrating filter capacitor
performs the square-domain averaging. The VRMS output can
be expressed as
Adequate filtering ensures the accuracy of the rms measurement;
however, some ripple or ac residual can still be present on the
dc output. To reduce this ripple, an external shunt capacitor can
be used at the output to form a low-pass filter with the on-chip,
100 ꢀ resistance (see the Selecting the Square-Domain Filter
and Output Low-Pass Filter section).
T2
VI2N ×dt
∫
T1
VRMS = A ×
T2 −T1
OUTPUT BUFFER
Note that A is a scaling parameter that is determined by the
on-chip resistor ratio, and there are no other scaling parameters
involved in this computation, which means that the rms output
is inherently free from any sources of error due to temperature,
supply, and process variations.
A buffer takes the internal rms signal and amplifies it accor-
dingly before it is output on the VRMS pin. The output stage
of the rms buffer is a common source PMOS with a resistive
load to provide a rail-to-rail output. The buffer has a 100 Ω
on-chip series resistance on the output, allowing for easy low-
pass filtering.
FILTERING
An important aspect of rms-dc conversion is the need for
averaging (the function is root-mean-square). The on-chip
averaging in the square domain has a corner frequency of
approximately 40 kHz and is sufficient for common modulation
signals, such as CDMA-, CDMA2000-, WCDMA-, and QPSK-/
QAM-based OFDM (for example, LTE, WLAN, and WiMAX).
Rev. 0 | Page 13 of 24
ADL5504
APPLICATIONS INFORMATION
BASIC CONNECTIONS
Resistive Tap RF Input
Figure 36 shows a technique for coupling the input signal into
the ADL5504 that can be applicable when the input signal is
much larger than the input range of the ADL5504. A series
resistor combines with the input impedance of the ADL5504
to attenuate the input signal. Because this series resistor forms
a divider with the frequency-dependent input impedance, the
apparent gain changes greatly with frequency. However, this
method has the advantage of very little power being tapped
off in RF power transmission applications. If the resistor is
large compared with the impedance of the transmission line,
the VSWR of the system is relatively unaffected.
Figure 34 shows the basic connections for the ADL5504. The
device is powered by a single supply between 2.5 V and 3.3 V,
with a quiescent current of 1.8 mA. The VPOS pin is decoupled
using 100 pF and 0.1 μF capacitors.
Placing a single 75 ꢀ resistor at the RF input provides a
broadband match of 50 Ω. More precise resistive or reactive
matches can be applied for narrow frequency band use (see
the RF Input Interfacing section).
The rms averaging can be augmented by placing additional
capacitance at CFLTR. The ac residual can be reduced further by
increasing the output capacitance, COUT. The combination of
the internal 100 Ω output resistance and COUT produces a low-
pass filter to reduce output ripple of the VRMS output (see the
Selecting the Square-Domain Filter and Output Low-Pass Filter
section for more details).
RF TRANSMISSION LINE
RFIN
R
SERIES
+V = 2.5V TO 3.3V
S
ADL5504
0.1µF
100pF
Figure 36. Attenuating the Input Signal
C
FLTR
1
2
3
6
5
4
FLTR
ENBL
VRMS
The resistive tap or series resistance, RSERIES, can be expressed as
ADL5504
R
SERIES = RIN (1 − 10ATTN/20)/(10ATTN/20
where:
IN is the input resistance of RFIN.
ATTN is the desired attenuation factor in decibels.
)
(1)
VPOS
RFIN
VRMS
R
C
OUT
OUT
COMM
RFIN
R
R10
75ꢀ
Figure 34. Basic Connections for ADL5504
For example, if a power amplifier with a maximum output power
of 28 dBm is matched to the ADL5504 input at 5 dBm, then a
−23 dB attenuation factor is required. At 900 MHz, the input
resistance, RIN, is 370 Ω.
RF INPUT INTERFACING
The input impedance of the ADL5504 decreases with increasing
frequency in both its resistive and capacitive components (see
Figure 9). The resistive component varies from 370 ꢀ at 900 MHz
to about 240 ꢀ at 2600 MHz.
R
SERIES = (370 Ω)(1 − 10−23/20)/(10−23/20) = 4870 Ω
(2)
Thus, for an attenuation of −23 dB, a series resistance of
approximately 4.87 kΩ is needed.
A number of options exist for input matching. For operation
at multiple frequencies, a 75 ꢀ shunt to ground, as shown in
Figure 35, provides the best overall match. For use at a single
frequency, a resistive or a reactive match can be used. By plotting
the input impedance on a Smith chart, the best value for a
resistive match can be calculated. (Both input impedance and
input capacitance can vary by up to 20ꢁ around their nominal
values.) Where VSWR is critical, the match can be improved
with a series inductor placed before the shunt component.
RF TRANSMISSION LINE
DIRECTIONAL
COUPLER
50ꢀ
ATTN
RFIN
75ꢀ
ADL5504
Figure 35. Input Interfacing to Directional Coupler
Rev. 0 | Page 14 of 24
ADL5504
Multiple RF Inputs
Output Swing
Figure 37 shows a technique for combining multiple RF input
signals to the ADL5504. Some applications can share a single
detector for multiple bands. Three 16.5 Ω resistors in a T network
combine the three 50 Ω terminations (including the ADL5504
with the shunt 75 Ω matching component). The broadband
resistive combiner ensures that each port of the T network sees
a 50 Ω termination. Because there are only 6 dB of isolation
from one port of the combiner to the other ports, only one
band should be active at a time.
At 900 MHz, the VRMS output voltage is nominally 1.87× the
input rms voltage (a conversion gain of 1.87 V/V rms). The output
voltage swings from near ground to 2.5 V on a 3.0 V supply.
Figure 8 shows the output swings of the ADL5504 to a CW input
for various supply voltages. Only at the lowest supply voltage
(2.5 V) is there a reduction in the dynamic range as the input
headroom decreases.
Output Offset
The ADL5504 has a 1 dB error detection range of about 30 dB,
as shown in Figure 10 to Figure 12 and Figure 16 to Figure 18.
The error is referred to the best-fit line defined in the linear
region of the output response (see the Device Calibration and
Error Calculation section for more details). Below an input
power of −18 dBm, the response is no longer linear and begins
to lose accuracy. In addition, depending on the supply voltage,
saturation may limit the detection accuracy above 12 dBm.
Calibration points should be chosen in the linear region,
avoiding the nonlinear ranges at the high and low extremes.
BAND 1
DIRECTIONAL
COUPLER
50ꢀ
16.5ꢀ
16.5ꢀ
BAND 2
RFIN
DIRECTIONAL
COUPLER
50ꢀ
75ꢀ
16.5ꢀ
ADL5504
Figure 37. Combining Multiple RF Input Signals
Figure 38 shows a distribution of the output response vs. the
input for multiple devices. The ADL5504 loses accuracy at low
input powers as the output response begins to fan out. As the
input power is reduced, the spread of the output response
increases along with the error.
LINEARITY
Because the ADL5504 is a linear responding device, plots of output
voltage vs. input voltage result in a straight line (see Figure 4
and Figure 5) and the dynamic range in decibels (dB) is not
clearly visible. It is more useful to plot the error on a logarith-
mic scale, as shown in Figure 7. The deviation of the plot from
the ideal straight line characteristic is caused by input stage
clipping at the high end and by signal offsets at the low end.
However, offsets at the low end can be either positive or neg-
ative; therefore, the linearity error vs. input level plots (see
Figure 7) can also trend upwards at the low end. Figure 10 to
Figure 12 and Figure 16 to Figure 18 show error distributions
for a large population of devices at specific frequencies over
temperature.
10
1
0.1
0.01
0.001
0.0001
It is also apparent in Figure 7 that the error at the lower portion
of the dynamic range tends to shift up as frequency is increased.
This is due to the calibration points chosen, −14 dBm and +8 dBm
(see the Device Calibration and Error Calculation section).
–25
–20
–15
–10
–5
0
5
10
15
INPUT (dBm)
Figure 38. Output vs. Input Level Distribution of 50 Devices,
900 MHz Frequency, 3.0 V Supply
The absolute value cell has an input impedance that varies with
frequency. The result is a decrease in the actual voltage across the
squaring cell as the frequency increases, reducing the conversion
gain. The dynamic range is near constant over frequency, but
with a decrease in conversion gain as frequency is increased.
Although some devices follow the ideal linear response at very
low input powers, not all devices continue the ideal linear regres-
sion to a near 0 V y-intercept. Some devices exhibit output
responses that rapidly decrease and some flatten out.
With no RF signal applied, the ADL5504 has a typical output
offset of 10 mV (with a maximum of 100 mV) on VRMS.
Rev. 0 | Page 15 of 24
ADL5504
100
90
80
70
60
50
40
30
20
10
0
OUTPUT DRIVE CAPABILITY AND BUFFERING
The ADL5504 is capable of sourcing a VRMS output current of
approximately 3 mA. The output current is sourced through the
on-chip, 100 Ω series resistor; therefore, any load resistor forms
a voltage divider with this on-chip resistance. It is recommended
that the ADL5504 VRMS output drive high resistance loads to
preserve output swing. If an application requires driving a low
resistance load (as well as in cases where increasing the nominal
conversion gain is desired), a buffering circuit is necessary.
C
OUT
C
FLTR
SELECTING THE SQUARE-DOMAIN FILTER AND
OUTPUT LOW-PASS FILTER
1
10
100
1000
The internal filter capacitor of the ADL5504 provides averaging
in the square domain but leaves some residual ac on the output.
Signals with high peak-to-average ratios, such as W-CDMA or
CDMA2000, can produce ac residual levels on the ADL5504
VRMS dc output. To reduce the effects of these low frequency
components in the waveforms, some additional filtering is
required.
CAPACITANCE (nF)
Figure 39. AC Residual vs. CFLTR and COUT
W-CDMA Reverse Link (5.8 dB CF) Waveform
,
400
350
300
250
200
150
100
50
C
OUT
The square-domain filter capacitance of the ADL5504 can be
augmented by connecting a capacitor between Pin 1 (FLTR) and
Pin 2 (VPOS). In addition, the VRMS output of the ADL5504 can
be filtered directly by placing a capacitor between VRMS (Pin 5)
and ground. The combination of the on-chip, 100 Ω output
series resistance and the external shunt capacitor forms a low-
pass filter to reduce the residual ac.
C
FLTR
Figure 39 and Figure 40 show the effects on the residual ripple
vs. the output and square-domain filter capacitor values at two
communication standards with high peak-to-average ratios.
Note that there is a trade-off between ac residual and response
time. Large filter capacitances increase the turn-on and pulse
response times (see Figure 28 to Figure 33). Figure 41 shows the
effect of the two filtering options, the output filter and the
square-domain filter capacitor, on the pulse response time of
the ADL5504. For more information on the effects of the filter
capacitances on the response, see the Power Consumption,
Enable, and Power-On/Power-Off Response Time section.
0
1
10
100
1000
CAPACITANCE (nF)
Figure 40. AC Residual vs. CFLTR and COUT
W-CDMA Forward Link (11.7 dB CF) Waveform
,
1000
250
225
200
175
150
125
100
75
900
800
700
600
500
400
300
200
100
0
50
C
FLTR
25
C
OUT
0
1000
1
10
100
CAPACITANCE (nF)
Figure 41. CFLTR and COUT Response Time vs. Capacitance
Rev. 0 | Page 16 of 24
ADL5504
POWER CONSUMPTION, ENABLE, AND POWER-
ON/POWER-OFF RESPONSE TIME
PULSED RFIN
The quiescent current consumption of the ADL5504 varies
linearly with the size of the input signal from approximately
1.8 mA for no signal up to 9 mA at an input level of 0.7 V rms
(10 dBm, referred to 50 Ω). There is little variation in supply
current across power supply voltage or temperature, as shown in
Figure 27.
400mV rms RF INPUT
250mV rms
160mV rms
70mV rms
The ADL5504 can be disabled either by pulling the ENBL (Pin 6)
to COMM (Pin 4) or by removing the power supply to the device.
Disabling the device via the ENBL function reduces the leakage
current to less than 1 μA. When the device is disabled, the output
impedance increases to approximately 5.5 kΩ on VRMS.
1ms/DIV
Figure 43. Output Response to Various RF Input Pulse Levels,
3 V Supply, 900 MHz Frequency, Square-Domain Filter Open,
COUT = 0.1 μF with Parallel 1 kΩ
The turn-on time and pulse response is strongly influenced
by the sizes of the square-domain filter and the output shunt
capacitor. Figure 42 shows a plot of the output response to an
RF pulse on the RFIN pin, with a 0.1 μF output filter capacitor and
a no square-domain filter capacitor. The falling edge is particularly
dependent on the output shunt capacitance, as shown in Figure 42.
The square-domain filter improves the rms accuracy for high
crest factors (see the Selecting the Square-Domain Filter and
Output Low-Pass Filter section), but it can hinder the response
time. For optimum response time and low ac residual, both the
square-domain filter and the output filter should be used. The
square-domain filter at FLTR can be reduced to improve response
time, and the remaining ac residual can be decreased by using
the output filter, which has a smaller time constant.
PULSED RFIN
DEVICE CALIBRATION AND ERROR CALCULATION
400mV rms RF INPUT
Because slope and intercept vary from device to device, board-
level calibration must be performed to achieve high accuracy.
In general, calibration is performed by applying two input power
levels to the ADL5504 and measuring the corresponding output
voltages. The calibration points are generally chosen to be within
the linear operating range of the device. The best-fit line is
characterized by calculating the conversion gain (or slope) and
intercept using the following equations:
250mV rms
160mV rms
70mV rms
1ms/DIV
Figure 42. Output Response to Various RF Input Pulse Levels, 3 V Supply,
900 MHz Frequency, Square-Domain Filter Open, COUT = 0.1 μF
Gain = (VVRMS2 − VVRMS1)/(VIN2 − VIN1
Intercept = VVRMS1 − (Gain × VIN1
where:
)
(3)
(4)
)
To improve the falling edge of the enable and pulse responses, a
resistor can be placed in parallel with the output shunt capacitor.
The added resistance helps to discharge the output filter capacitor.
Although this method reduces the power-off time, the added
load resistor also attenuates the output (see the Output Drive
Capability and Buffering section).
V
INx is the rms input voltage to RFIN.
V
VRMSx is the voltage output at VRMS.
Once gain and intercept are calculated, an equation can be
written that allows calculation of an (unknown) input power
based on the measured output voltage.
V
IN = (VVRMS − Intercept)/Gain
(5)
For an ideal (known) input power, the law conformance error of
the measured data can be calculated as
ERROR (dB) = 20 × log [(VVRMS, MEASURED − Intercept)/
(Gain × VIN, IDEAL)]
(6)
Rev. 0 | Page 17 of 24
ADL5504
Figure 44 shows a plot of the error at 25°C, the temperature
at which the ADL5504 is calibrated. Note that the error is not 0;
this is because the ADL5504 does not perfectly follow the ideal
linear equation, even within its operating region. The error at
the calibration points is, however, equal to 0 by definition.
This plot is a useful tool for estimating temperature drift at a
particular power level with respect to the (nonideal) response
at ambient temperature. The linearity and dynamic range tend
to be improved artificially with this type of plot because the
ADL5504 does not perfectly follow the ideal linear equation
(especially outside of its linear operating range). Achieving
this level of accuracy in an end application requires calibration
at multiple points in the operating range of the device.
Figure 44 also shows error plots for the output voltage at −40°C
and +85°C. These error plots are calculated using the gain and
intercept at 25°C. This is consistent with calibration in a mass
production environment where calibration at temperature is not
practical.
In some applications, very high accuracy is required at just one
power level or over a reduced input range. For example, in a
wireless transmitter, the accuracy of the high power amplifier
(HPA) is most critical at or close to full power. The ADL5504
offers a tight error distribution in the high input power range,
as shown in Figure 45. The high accuracy range, beginning
around 2 dBm at 1900 MHz, offers 12 dB of 0.15 dB detection
error over temperature. Multiple point calibration at ambient
temperature in the reduced range offers precise power
measurement with near 0 dB error from −40°C to +85°C.
3
3
2
1
+85°C
+25°C
–40°C
0
–1
–2
–3
2
1
–25
–20
–15
–10
–5
0
5
10
15
+85°C
INPUT (dBm)
0
Figure 44. Error from Linear Reference vs. Input at −40°C, +25°C, and
+85°C vs. +25°C Linear Reference, 1900 MHz Frequency, 3.0 V Supply
+25°C
–40°C
–1
–2
–3
CALIBRATION FOR IMPROVED ACCURACY
Another way of presenting the error function of the ADL5504
is shown in Figure 45. In this case, the decibel (dB) error at hot
and cold temperatures is calculated with respect to the transfer
function at ambient temperature. This is a key difference in
comparison to Figure 44, in which the error was calculated
with respect to the ideal linear transfer function at ambient
temperature. When this alternative technique is used, the
error at ambient temperature becomes equal to 0 by definition
(see Figure 45).
–25
–20
–15
–10
–5
0
5
10
15
INPUT (dBm)
Figure 45. Error from +25°C Output Voltage at −40°C, +25°C, and +85°C After
Ambient Normalization, 1900 MHz Frequency, 3.0 V Supply
Note that the high accuracy range center varies over frequency
(see Figure 13 to Figure 15 and Figure 19 to Figure 21).
Rev. 0 | Page 18 of 24
ADL5504
DEVICE HANDLING
DRIFT OVER A REDUCED TEMPERATURE RANGE
The wafer level chip scale package consists of solder bumps
connected to the active side of the die. The part is Pb-free and
RoHS compliant with 95.5ꢁ tin, 4.0ꢁ silver, and 0.5ꢁ copper
solder bump composition. The WLCSP can be mounted on
printed circuit boards using standard surface-mount assembly
techniques; however, caution should be taken to avoid damaging
the die. See the AN-617 Application Note, MicroCSP Wafer
Level Chip Scale Package, for additional information. WLCSP
devices are bumped die; therefore, the exposed die may be
sensitive to light, which can influence specified limits. Lighting
in excess of 600 lux can degrade performance.
Figure 46 shows the error over temperature for a 1900 MHz
input signal. The error due to drift over temperature consis-
tently remains within 0.20 dB and only begins to exceed this
limit when the ambient temperature rises above +55°C and
drops below −30°C. For all frequencies using a reduced temper-
ature range, higher measurement accuracy is achievable.
1.00
–40°C
–30°C
–20°C
–10°C
0°C
+15°C
+25°C
+35°C
+45°C
+55°C
+65°C
+75°C
+85°C
0.75
0.50
0.25
0
+5°C
–0.25
–0.50
–0.75
–1.00
–25
–20
–15
–10
–5
0
5
10
15
INPUT (dBm)
Figure 46. Typical Drift at 1900 MHz for Various Temperatures
Rev. 0 | Page 19 of 24
ADL5504
Land Pattern and Soldering Information
EVALUATION BOARD
Pad diameters of 0.28 mm are recommended with a solder paste
mask opening of 0.38 mm. For the RF input trace, a trace width
of 0.30 mm is used, which corresponds to a 50 ꢀ characteristic
impedance for the dielectric material being used (FR4). All traces
going to the pads are tapered down to 0.15 mm. For the RFIN
line, the length of the tapered section is 0.20 mm.
Figure 47 shows the schematic of the ADL5504 evaluation board.
The board is powered by a single supply in the 2.5 V to 3.3 V
range. The power supply is decoupled by 100 pF and 0.1 μF
capacitors. The device must be enabled by switching SW1A
to the position labeled on.
The RF input has a broadband match of 50 Ω using a single
75 ꢀ resistor at R7A. More precise matching at spot frequencies
is possible (see the RF Input Interfacing section).
Table 4 details the various configuration options of the evaluation
board. Figure 48 shows the layout of the evaluation board.
C7A
SW1A
(OPEN)
VPOSA
R4A
VPOSA
(P1 – B8)
R1A
0ꢀ
R9A
R8A
R10A
(OPEN)
P2
(OPEN)
(OPEN)
(OPEN)
(P1 – B6)
VPOSA
ENA
1
2
3
6
5
4
FLTR
ENBL
VRMS
COMM
C3A
10nF
R3A
ADL5504
0
ꢀ
VRMSA
VPOS
RFIN
R2A
(OPEN)
C4A
(OPEN)
R5A
(OPEN)
C9A
(OPEN)
C2A
0.1µF
C1A
100pF
(P1 – B4)
(P1 – A1,B1)
RFINA
C8A
(OPEN)
VPOSA
R7A
75ꢀ
R
6A
EN)
(OP
C5
(OPEN)
C6
(OPEN)
(P1 – B12)
Figure 47. Evaluation Board Schematic
Figure 48. Layout of Evaluation Board, Component Side
Rev. 0 | Page 20 of 24
ADL5504
Table 4. Evaluation Board Configuration Options
Component
Description
Default Condition
VPOSA, GNDA
Ground and supply vector pins.
Not applicable
C1A, C2A, C7A, C8A, Power supply decoupling. Nominal supply decoupling of 0.01 μF and 100 pF.
C9A, C5, C6
C1A = 100 pF (Size 0402)
C2A = 0.1 μF (Size 0402)
C7A = C8A = open (Size 0805)
C9A = open (Size 0402)
C5 = C6 = open (Size 0402)
C3A
Filter capacitor. The internal rms averaging capacitor can be augmented by placing
additional capacitance in C3A.
RF input interface. The 75 Ω resistor at R7A combines with the ADL5504 internal
input impedance to give a broadband input impedance of around 50 Ω.
C3A = 10 nF (Size 0402)
R7A = 75 Ω (Size 0402)
R7A
C4A, R2A, R3A
Output filtering. The combination of the internal 100 Ω output resistance and C4A
produce a low-pass filter to reduce output ripple of the VRMS output. The output
can be scaled down using the resistor divider pads, R2A and R3A.
R3A = 0 Ω (Size 0402)
R2A = open (Size 0402)
C4A= open (Size 0402)
SW1A, R4A, R10A, P2 Device enable. When the SW1A is set to the on position, the ENꢀL pin is connected to the R4A = 0 Ω (Size 0402)
supply and the ADL5504 is in enable mode. In the opposite switch position, the ENꢀL pin R10A = open (Size 0402)
is grounded (through the 0 Ω resistor) putting the device in power-down mode.
SW1A = on position
P2 = not installed
P1, R1A, R5A, R6A,
R8A, R9A
Alternate interface. The end connector, P1, allows access to various ADL5504 signals. P1 = not installed
These signal paths are only used during factory test and characterization.
R1A = R5A = open (Size 0402)
R6A = R9A = open (Size 0402)
R8A = open (Size 0805)
Rev. 0 | Page 21 of 24
ADL5504
OUTLINE DIMENSIONS
0.660
0.600
0.540
0.830
0.790
0.750
0.430
0.400
0.370
SEATING
PLANE
2
1
A
B
0.280
0.260
0.240
BALL A1
IDENTIFIER
1.230
1.190
1.150
0.80
REF
0.40
REF
C
TOP VIEW
(BALL SIDE DOWN)
COPLANARITY
0.05
0.40 REF
0.230
0.200
0.170
BOTTOM VIEW
(BALL SIDE UP)
Figure 49. 6-Ball Wafer Level Chip Scale Package [WLCSP]
(CB-6-8)
Dimensions shown in millimeters
ORDERING GUIDE
Model
Temperature Range Package Description
Package Option
Branding Ordering Quantity
ADL5504ACꢀZ-P71 –40°C to +85°C
ADL5504ACꢀZ-P21 –40°C to +85°C
ADL5504-EVALZ1
6-ꢀall WLCSP, 7”Pocket Tape and Reel Cꢀ-6-8
6-ꢀall WLCSP, 7”Pocket Tape and Reel Cꢀ-6-8
Evaluation ꢀoard
3P
3P
3,000
250
1 Z = RoHS Compliant Part.
Rev. 0 | Page 22 of 24
ADL5504
NOTES
Rev. 0 | Page 23 of 24
ADL5504
NOTES
©2009 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
D08437-0-10/09(0)
Rev. 0 | Page 24 of 24
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