AD5725 [ADI]
Quad 12-Bit Serial Input Unipolar/Bipolar Voltage Output DAC; 四通道12位串行输入,单极性/双极性电压输出DAC型号: | AD5725 |
厂家: | ADI |
描述: | Quad 12-Bit Serial Input Unipolar/Bipolar Voltage Output DAC |
文件: | 总20页 (文件大小:518K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
Quad, 12-Bit, Serial Input,
Unipolar/Bipolar, Voltage Output DAC
AD5726
Bipolar outputs are configured by connecting both VREFP and
VREFN to nonzero voltages. This method of setting output voltage
ranges has advantages over the bipolar offsetting methods
because it is not dependent on internal and external resistors
with different temperature coefficients.
FEATURES
+5 V to 15 V operation
Unipolar or bipolar operation
1 ꢀSB maximum INꢀ error, 1 ꢀSB maximum DNꢀ error
Guaranteed monotonic over temperature
Double-buffered inputs
Simultaneous updating via ꢀDAC
Asynchronous CꢀR to zero scale/midscale
Operating temperature range: −40°C to +125°C
iCMOS® process technology1
The AD5726 uses a serial interface that operates at clock rates up to
30 MHz and is compatible with DꢀP and microcontroller interface
standards. Double buffering allows simultaneous updating of all
CLR
DACs. The asynchronous
function clears all DAC registers
to a user-selectable, zero-scale or midscale output.
The AD5726 is available in 16-lead ꢀꢀOP and 16-lead ꢀOIC
packages. It can be operated from a wide variety of supply and
reference voltages with supplies ranging from single +5 V to
15 V, and references ranging from +2.5 V to 10 V. Power
dissipation is less than 240 mW with 15 V supplies and only
30 mW with a +5 V supply. Operation is specified over the
temperature range of −40°C to +125°C.
APPꢀICATIONS
Industrial automation
Closed-loop servo control, process control
Automotive test and measurement
Programmable logic controllers
GENERAꢀ DESCRIPTION
The AD5726 is a quad, 12-bit, serial input, voltage output
digital-to analog converter that offers guaranteed monotonicity
and integral nonlinearity (INL) of 1 LꢀB maximum.
Table 1. Related Devices
Part No.
Description
AD5725
Quad, 12-bit, parallel input,
Output voltage swing is set by two reference inputs, VREFP and
unipolar/bipolar, voltage output DAC.
AD5724R/AD5734R/ Complete, quad, 12-/14-/16-bit, serial
VREFN. The DAC offers a unipolar positive output range when
the VREFN input is set to 0 V and the VREFP input is set to a positive
voltage. A similar configuration with VREFP at 0 V and VREFN at a
negative voltage provides a unipolar negative output range.
AD5754R
input, unipolar/bipolar voltage output
DAC with internal reference.
AD5722R/AD5732R/ Complete, dual, 12-/14-/16-bit, serial
AD5752R
input, unipolar/bipolar voltage output
DAC with internal reference.
FUNCTIONAꢀ BꢀOCK DIAGRAM
AV
AV
V
REFP
SS
DD
12
12
12
12
12
12
12
12
12
INPUT
REG A
DAC
DAC A
DAC B
DAC C
DAC D
V
V
V
V
OUTA
OUTB
OUTC
OUTD
I/O
REG A
SDIN
SCLK
CS
REGISTER
AND
CONTROL
LOGIC
INPUT
REG B
DAC
REG B
INPUT
REG C
DAC
REG C
INPUT
REG D
DAC
REG D
AD5726
V
GND
CLR CLRSEL LDAC
REFN
Figure 1.
1 For analog systems designers within industrial/instrumentation equipment OEMs who need high performance ICs at higher-voltage levels, iCMOS is a technology
platform that enables the development of analog ICs capable of 30 V and operating at 15 V supplies while allowing dramatic reductions in power consumption and
package size, and increased ac and dc performance.
Rev. 0
Information furnished by Analog Devices is believed to be accurate and reliable. However, no
responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
rights of third parties that may result from its use. Specifications subject to change without notice. No
Tel: 781.329.4700
Fax: 781.461.3113
www.analog.com
©2007 Analog Devices, Inc. All rights reserved.
license is granted by implication or otherwise under any patent or patent rights of Analog Devices.
Trademarks and registeredtrademarks arethe property of their respective owners.
AD5726
TABLE OF CONTENTS
Features .............................................................................................. 1
Theory of Operation ...................................................................... 13
DAC Architecture....................................................................... 13
Output Amplifiers...................................................................... 13
Reference Inputs......................................................................... 13
ꢀerial Interface............................................................................ 14
Applications..................................................................................... 15
Power-Up ꢀequence ................................................................... 15
Reference Configuration ........................................................... 15
Power ꢀupply Bypassing and Grounding................................ 16
Galvanically Isolated Interface ................................................. 16
Microprocessor Interfacing....................................................... 17
Outline Dimensions....................................................................... 18
Ordering Guide .......................................................................... 18
Applications....................................................................................... 1
General Description......................................................................... 1
Functional Block Diagram .............................................................. 1
Revision History ............................................................................... 2
ꢀpecifications..................................................................................... 3
AC Performance Characteristics................................................ 5
Timing Characteristics ................................................................ 6
Absolute Maximum Ratings............................................................ 7
Thermal Resistance ...................................................................... 7
EꢀD Caution.................................................................................. 7
Pin Configuration and Function Descriptions............................. 8
Typical Performance Characteristics ............................................. 9
Terminology .................................................................................... 12
REVISION HISTORY
4/07—Revision 0: Initial Version
Rev. 0 | Page 2 of 20
AD5726
SPECIFICATIONS
AVDD = +5 V 5%, AVꢀꢀ = 0 V/−5 V 5%, VREFP = +2.5 V, VREFN = 0 V/−2.5 V, RLOAD = 2 kΩ.
All specifications TMIN to TMAX, unless otherwise noted.1
Table 2.
Parameter
Value
Unit
Test Conditions/Comments
ACCURACY
Resolution
Relative Accuracy (INL)
12
1
1
1
1
6
6
12
12
10
10
Bits
LSB max
LSB max
LSB max
LSB typ
LSB max
LSB max
LSB max
LSB max
ppm FSR/°C typ
ppm FSR/°C typ
Y grade, AVSS = −5 V, outputs unloaded
Y grade, AVSS = 0 V2
Guaranteed monotonic
Differential Nonlinearity (DNL)
Linearity Matching
Zero-Scale Error
Full-Scale Error
Zero-Scale Error
Full-Scale Error
AVSS = −5 V
AVSS = −5 V
AVSS = 0 V2
AVSS = 0 V2
AVSS = −5 V
AVSS = −5 V
Zero-Scale TC3
Full-Scale TC3
REFERENCE INPUT
VREFP
Reference Input Range4
VREFN + 2.5
AVDD − 2.5
0.75
V min
V max
mA max
Input Current
VREFN
Reference Input Range4
Typically 0.25 mA
AVSS = 0 V
AVSS
V min
0 V
V min
VREFP − 2.5
−1.0
160
V max
mA max
kHz typ
Input Current
Large Signal Bandwidth3
OUTPUT CHARACTERISTICS3
Output Current
Typically −0.6 mA, AVSS = −5 V
−3 dB, VREFP = 0 V to 10 V p-p
1.25
mA max
AVSS = −5 V
DIGITAL INPUTS
VIH, Input High Voltage
VIL, Input Low Voltage
Input Current3
Input Capacitance3
POWER SUPPLY CHARACTERISTICS
Power Supply Sensitivity3
AIDD
2.4
0.8
10
5
V min
V max
μA max
pF typ
0.002
1.5
1.5
%/% max
Typically 0.0004
mA/channel max
mA/channel max
mW max
Outputs unloaded, typically 0.75 mA, VIL = DGND, VIH = 5 V
Outputs unloaded, typically 0.75 mA, VIL = DGND, VIH = 5 V
Outputs unloaded, typically 15 mW, AVSS = 0 V
AISS
Power Dissipation
30
1 All supplies can be varied 5% and operation is guaranteed. Device is tested with AVDD = 4.75 V.
2 For single-supply operation (VREFN = 0 V, AVSS = 0 V), due to internal offset errors, INL and DNL are measured beginning at code 0x005.
3 Guaranteed by design and characterization, not production tested.
4 Operation is guaranteed over this reference range, but linearity is neither tested nor guaranteed.
Rev. 0 | Page 3 of 20
AD5726
AVDD = +15 V 5%, AVꢀꢀ = −15 V 5%, VREFP = +10 V, VREFN = −10 V, RLOAD = 2 kΩ. All specifications TMIN to TMAX, unless otherwise noted.1
Table 3.
Parameter
Value
Unit
Test Conditions/Comments
ACCURACY
Resolution
12
0.5
1
1
3
3
4
4
Bits
LSB max
LSB max
LSB max
LSB max
LSB max
ppm FSR/°C typ
ppm FSR/°C typ
Relative Accuracy (INL)
Differential Nonlinearity (DNL)
Linearity Matching
Zero-Scale Error
Full-Scale Error
Zero-Scale TC2
Y grade
Guaranteed monotonic
Full-Scale TC2
REFERENCE INPUT
VREFP
Reference Input Range3
VREFN + 2.5
AVDD − 2.5
2
V min
V max
mA max
Input Current
VREFN
Reference Input Range3
Code 0x000, Code 0x555, typically 1 mA
−10 V
VREFP − 2.5
−3.5
V min
V max
mA min
kHz typ
Input Current2
Large Signal Bandwidth2
OUTPUT CHARACTERISTICS2
Output Current
Code 0x000, Code 0x555, typically −2 mA
−3 dB, VREFP = 0 V to 2.5 V p-p
450
5
mA max
DIGITAL INPUTS
VIH, Input High Voltage
VIL, Input Low Voltage
Input Current2
Input Capacitance2
POWER SUPPLY CHARACTERISTICS
Power Supply Sensitivity2
AIDD
2.4
0.8
10
5
V min
V max
μA max
pF typ
0.002
2
2
%/% max
Typically 0.0004
Outputs unloaded, typically 1.25 mA, VIL = DGND, VIH = 5 V
Outputs unloaded, typically 1.25 mA, VIL = DGND, VIH = 5 V
mA/channel max
mA/channel max
mW max
AISS
Power Dissipation
240
1 All supplies can be varied 5% and operation is guaranteed.
2 Guaranteed by design and characterization, not production tested.
3 Operation is guaranteed over this reference range, but linearity is neither tested nor guaranteed.
Rev. 0 | Page 4 of 20
AD5726
AC PERFORMANCE CHARACTERISTICS
AVDD = +5 V 5%/+15 V 5%, AVꢀꢀ = −5 V 5%/0 V/−15 V 5%, GND = 0 V, VREFP = +2.5 V/+10 V, VREFN = −2.5 V/0 V/−10 V,
LOAD = 2 kΩ. All specifications TMIN to TMAX, unless otherwise noted.1
R
Table 4.
Parameter
A Grade
B Grade
Unit
Test Conditions/Comments
DYNAMIC PERFORMANCE
Output Voltage Settling Time (tS)
13
9
2.3
2
100
0.25
90
30
13
9
2.3
2
100
0.25
90
30
μs typ
μs typ
V/μs typ
V/μs typ
dB
nV-sec
kHz
nV-sec
To 0.01%, 10 V voltage swing
To 0.01%, 2.5 V voltage swing, AVDD = 5 V
10% to 90%, 10 V voltage swing
10% to 90%, 2.5 V voltage swing
Slew Rate
Analog Crosstalk
Digital Feedthrough
Large Signal Bandwidth
Glitch Impulse
3 dB, VREFP = 5 V +10 Vp-p, VREFN = −10 V.
Code transition = 0x7FF to 0x800 and vice versa
1 Guaranteed by design and characterization, not production tested.
Rev. 0 | Page 5 of 20
AD5726
TIMING CHARACTERISTICS
AVDD = +15 V/+5 V, AVꢀꢀ = −15 V/−5 V/0 V, GND = 0 V; VREFP = +10 V/+2.5 V; VREFN = −10 V/−2.5 V/0 V, VL = 5 V, RLOAD = 2 kΩ,
CL = 200 pF. All specifications TMIN to TMAX, unless otherwise noted.1, 2
Table 5.
Parameter
ꢀimit at TMIN, TMAX
Unit
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
Description
tDS
tDH
tCH
tCL
tCSS
tCSH
tLD1
tLD2
5
5
Data setup time.
Data hold time.
Clock pulse width high.
Clock pulse width low.
Select time.
Deselect delay.
Load disable time.
Load delay.
13
13
13
13
20
20
20
20
tLDW
tCLRW
Load pulse width.
Clear pulse width.
1 Guaranteed by design and characterization, not production tested.
2 All input control signals are specified with tr = tf = 5 ns (10% to 90% of 5 V) and timed from a voltage level of 1.6 V.
tCSH
CS
tCSS
SDIN
A1
A0
X
X
D11
D10
D9
D8
D4
D3
D2
D1
D0
SCLK
tLD1
tLD2
LDAC
Figure 2. Data Load Sequence
tDS
tDH
SDIN
SCLK
CS
tCH
tCSH
tCL
CLRSEL
tCLRW
tLD2
tLDW
CLR
LDAC
tS
tS
±1LSB
V
OUT
V
±1LSB
OUT
Figure 4. Clear Timing
Figure 3. Data Load Timing
Rev. 0 | Page 6 of 20
AD5726
ABSOLUTE MAXIMUM RATINGS
THERMAꢀ RESISTANCE
TA = 25°C unless otherwise noted.
Transient currents up to 100 mA do not cause ꢀCR latch-up.
θJA is specified for the worst-case conditions, that is, a device
soldered in a circuit board for surface-mount packages.
Table 6.
Table 7. Thermal Resistance
Parameter
Rating
AVSS to GND
AVDD to GND
AVSS to AVDD
AVSS to VREFN
Current into Any Pin
Digital Input Voltage to GND
Digital Output Voltage to GND
Operating Temperature Range
Industrial
Storage Temperature Range
Junction Temperature (TJ max)
Lead Temperature
Soldering
+0.3 V to −17 V
−0.3 V to +17 V
−0.3 V to +34 V
−0.3 V to +AVSS − 2 V
15 mA
Package Type
16-Lead SSOP
16-Lead SOIC
θJA
θJC
Unit
°C/W
°C/W
151
124.9
28
42.9
ESD CAUTION
−0.3 V to +7 V
−0.3 V to +7 V
−40°C to +85°C
−65°C to +150°C
105°C
JEDEC industry standard
J-STD-020
ꢀtresses above those listed under Absolute Maximum Ratings
may cause permanent damage to the device. This is a stress
rating only; functional operation of the device at these or any
other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute
maximum rating conditions for extended periods may affect
device reliability.
Rev. 0 | Page 7 of 20
AD5726
PIN CONFIGURATION AND FUNCTION DESCRIPTIONS
AV
1
2
3
4
5
6
7
8
16 CLRSEL
15 CLR
14 LDAC
13 NC
DD
V
OUTD
OUTC
V
AD5726
TOP VIEW
(Not to Scale)
V
REFN
V
V
12 CS
REFP
11 SCLK
10 SDIN
OUTB
OUTA
V
AV
9
GND
SS
NC = NO CONNECT
Figure 5. Pin Configuration
Table 8. Pin Function Descriptions
Pin No.
Mnemonic
Description
1
2
3
4
AVDD
VOUTD
VOUTC
VREFN
Positive Analog Supply Pin. Voltage ranges from 5 V to 15 V
Buffered Analog Output Voltage of DAC D.
Buffered Analog Output Voltage of DAC C.
Negative DAC Reference Input. The voltage applied to this pin defines the zero-scale output.
Allowable range is AVSS to VREFP − 2.5 V.
5
VREFP
Positive DAC Reference Input. The voltage applied to this pin defines the full-scale output voltage.
Allowable range is AVDD − 2.5 V to VREFN + 2.5 V.
6
7
8
9
10
11
12
VOUTB
VOUTA
AVSS
GND
SDIN
SCLK
CS
Buffered Analog Output Voltage of DAC B.
Buffered Analog Output Voltage of DAC A.
Negative Analog Supply Pin. Voltage ranges from 0 V to −15 V.
Ground Reference Pin.
Serial Data Input. Data must be valid on the rising edge of SCLK. This input is ignored when CS is high.
Serial Clock Input. Data is clocked into the input register on the rising edge of SCLK.
Active Low Chip Select Pin. This pin must be active for data to be clocked in. This pin is logically OR’ed with
the SCLK input and disables the serial data input when high.
13
14
NC
LDAC
No Internal Connection.
Active Low, Asynchronous Load DAC Input. The data currently contained in the serial input register is
transferred out to the DAC data registers on the falling edge of LDAC, independent of CS. Input data must
remain stable while LDAC is low.
15
16
CLR
Active Low Input. Sets input register and DAC registers to zero-scale (0x000) or midscale (0x800),
depending on the state of CLRSEL. The data in the serial input register is unaffected by this control.
Determines the action of CLR. If high, a clear command sets the internal DAC registers to midscale (0x800).
If low, the registers are set to zero (0x000).
CLRSEL
Rev. 0 | Page 8 of 20
AD5726
TYPICAL PERFORMANCE CHARACTERISTICS
0.4
0.05
0
0.3
+85°C
+25°C
0.2
–40°C
–0.05
–0.10
–0.15
–0.20
–0.25
0.1
0
–0.1
–0.2
AV
= +15V
AV
= 5V
DD
AV = –15V
DD
AV = 0V
SS
SS
–0.3
–0.4
V
V
= +10V
= –10V
V
T
= 0V
REFP
REFN
REFN
= 25°C
A
0
500
1000 1500 2000 2500 3000 3500
DAC (Code)
4000
1.0
1.2
1.4
1.6
1.8
2.0
2.2
2.4
2.6
2.8
3.0
V
(V)
REFP
Figure 6. INL Error vs. DAC Code, VSUPPLY
=
15 V, VREFP/VREFN = 10 V
Figure 9. DNL Error vs. VREFP, VSUPPLY = +5 V, VREFN = 0 V
0.20
0.15
0.10
0.05
0
1.0
0.8
AV
= +15V
+85°C
+25°C
–40°C
DD
AV = –15V
SS
V
= –10V
REFN
= 25°C
A
T
0.6
0.4
0.2
0
–0.2
–0.4
–0.6
–0.8
–1.0
–0.05
–0.10
AV
= +15V
DD
AV = –15V
SS
–0.15
–0.20
V
V
= +10V
= –10V
REFP
REFN
0
500
1000 1500 2000 2500 3000 3500
DAC (Code)
4000
6
7
8
9
10
11
12
V
(V)
REFP
Figure 7. DNL Error vs. DAC Code, VSUPPLY
= 15 V, VREFP/VREFN = 10 V
Figure 10. INL Error vs. VREFP, VSUPPLY
=
15 V, VREFN = −10 V
1.0
0.5
0.4
AV
= +15V
AV
AV = 0V
= 5V
DD
AV = –15V
DD
SS
0.8
0.6
SS
V
T
= –10V
V
T
= 0V
= 25°C
REFN
= 25°C
REFN
A
A
0.3
0.4
0.2
0.2
0.1
0
0
–0.2
–0.4
–0.6
–0.8
–1.0
–0.1
–0.2
–0.3
–0.4
6
7
8
9
10
11
12
1.0
1.2
1.4
1.6
1.8
2.0
2.2
2.4
2.6
2.8
3.0
V
(V)
V
(V)
REFP
REFP
Figure 8. DNL Error vs. VREFP, VSUPPLY
= 15 V, VREFN = −10 V
Figure 11. INL Error vs. VREFP, VSUPPLY = +5 V, VREFN = 0 V
Rev. 0 | Page 9 of 20
AD5726
0
0.3
0.2
AV
= +15V
DD
AV = –15V
SS
V
V
= +10V
= –10V
–0.1
–0.2
–0.3
–0.4
–0.5
–0.6
–0.7
DAC A
DAC B
DAC C
DAC D
REFP
REFN
2kΩ LOAD
0.1
DAC D
0
–0.1
–0.2
–0.3
–0.4
AV
= 5V
DAC C
DD
AV = 0V
DAC B
SS
V
V
= 2.5V
= 0V
= 25°C
REFP
REFN
DAC A
20
T
A
–40
–20
0
40
60
80
0
500
1000 1500 2000 2500 3000 3500 4000
DAC (Code)
TEMPERATURE (°C)
Figure 12. Full-Scale Error vs. Temperature
Figure 15. Channel-to-Channel Matching, VSUPPLY = +5 V, VREFP = 2.5 V, VREFN = 0 V
0.3
0.2
16
14
12
10
8
AV
= +15V
DD
AV = –15V
SS
V
V
= +10V
= –10V
REFP
REFN
2kΩ LOAD
0.1
0
DAC A
6
–0.1
–0.2
–0.3
DAC D
4
2
0
AV
= +15V
DD
AV = –15V
DAC C
SS
V
= –10V
REFN
DIGITAL INPUTS HIGH
DAC B
T
= 25°C
A
–40
–20
0
20
40
60
80
–7
–5
–3
–1
1
3
5
7
9
11
13
TEMPERATURE (°C)
V
(V)
REFP
Figure 13. Zero-Scale Error vs. Temperature
Figure 16. AIDD vs. VREFP, All DACs Loaded with Full-Scale Code
0.3
0.2
1.7995
1.5995
1.3995
1.1995
0.9995
0.7995
0.5995
0.3995
0.1995
–0.0005
AV
= +15V
V
= +10V
V
= –10V
T = 25°C
A
DD
REFP
REFN
AV = –15V
SS
DAC A
DAC B
DAC C
DAC D
0.1
0
–0.1
–0.2
–0.3
AV
= +15V
DD
AV = –15V
SS
V
V
= +10V
= –10V
= 25°C
REFP
REFN
T
A
0
500
1000 1500 2000 2500 3000 3500 4000
DAC (Code)
0
500
1000 1500 2000 2500 3000 3500 4000
DAC (Code)
Figure 14. Channel-to-Channel Matching, VSUPPLY
=
15 V, VREFP/VREFN
=
10 V
Figure 17. IVREFP vs. DAC Code
Rev. 0 | Page 10 of 20
AD5726
2
0
25
20
15
10
5
AV
= 15V
DD
AV = 0V
SS
V
V
= 10V
= 0V
= 25°C
REFP
REFN
–2
T
A
DATA = 0x800
–4
–6
–8
–10
–12
–14
–16
AV
= +15V
0
DD
AV = –15V
SS
V
V
= 0V ± 100mV
= –10V
REFP
–5
–10
REFN
FULL-SCALE CODE LOADED
= 25°C
T
A
10
100
1k
10k
100k
1M
10M
0
1
2
3
4
5
6
7
8
9
10
FREQUENCY (Hz)
V
(V)
OUT
Figure 18. Small Signal Response, VSUPPLY
= 15 V, VREFN = −10 V
Figure 20. Output Current vs. Output Voltage, VSUPPLY
=
15 V, VREFP/VREFN = 10 V
8
12
AV
= +15V
DD
AV = –15V
I
DD
SS
6
V
V
= +10V
= –10V
REFP
REFN
10
8
AV
= +15V
DD
AV = –15V
T = 25°C
A
4
2
SS
0
6
–2
–4
–6
–8
4
I
SS
2
0
0.01
–35
–15
5
25
45
65
85
0.1
1
10
100
TEMPERATURE (°C)
LOAD RESISTANCE (kꢀ)
Figure 21. Output Swing vs. Load Resistance, VSUPPLY
= 15 V, VREFP/VREFN = 10 V
Figure 19. Power Supply Currents vs. Temperature,
VSUPPLY 15 V, VREFP/VREFN 10 V
=
=
Rev. 0 | Page 11 of 20
AD5726
TERMINOLOGY
Zero-Scale Error TC
Relative Accuracy or Integral Nonlinearity (INL)
This is a measure of the change in zero-scale error with a
change in temperature. Zero-scale error TC is expressed in
ppm FꢀR/°C.
For the DAC, relative accuracy or integral nonlinearity (INL) is
a measure of the maximum deviation, in LꢀBs, from a straight
line passing through the endpoints of the DAC transfer
function. A typical INL vs. code plot can be seen in Figure 6.
Output Voltage Settling Time
Output voltage settling time is the amount of time it takes for the
output to settle to a specified level for a full-scale input change.
Differential Nonlinearity (DNL)
Differential nonlinearity (DNL) is the difference between the
measured change and the ideal 1 LꢀB change between any two
adjacent codes. A specified differential nonlinearity of 1 LꢀB
maximum ensures monotonicity. This DAC is guaranteed
monotonic by design. A typical DNL vs. code plot can be seen
in Figure 7.
Slew Rate
The slew rate of a device is a limitation in the rate of change of
the output voltage. The output slewing speed of a voltage-
output DAC converter is usually limited by the slew rate of the
amplifier used at its output. ꢀlew rate is measured from 10% to
90% of the output signal and is given in V/μs.
Monotonicity
A DAC is monotonic if the output either increases or remains
constant for increasing digital input code. The AD5726 is
monotonic over its full operating temperature range
Digital Feedthrough
Digital feedthrough is a measure of the impulse injected into
the analog output of the DAC from the digital inputs of the
DAC, but is measured when the DAC output is not updated. It
is specified in nV-sec and measured with a full-scale code
change on the data bus.
Full-Scale Error
Full-scale error is a measure of the output error when full-scale
code is loaded to the DAC register. Ideally, the output should be
VREFP − 1 LꢀB. Full-scale error is expressed in LꢀBs. A plot of
Power Supply Sensitivity
full-scale error vs. temperature can be seen in Figure 12.
Power supply sensitivity indicates how the output of the DAC is
affected by changes in the power supply voltage.
Zero-Scale Error
Zero-scale error is the error in the DAC output voltage when
0x0000 (straight binary coding) is loaded to the DAC register.
Ideally, the output voltage should be VREFN. A plot of zero-scale
error vs. temperature can be seen in Figure 13.
Analog Crosstalk
This is the dc change in the output level of one DAC in response
to a change in the output of another DAC. It is measured with a
full-scale output change on one DAC while monitoring another
DAC. It is expressed in dB.
Rev. 0 | Page 12 of 20
AD5726
THEORY OF OPERATION
The AD5726 is a quad, 12-bit, serial input, unipolar/bipolar
voltage output DAC. It operates from single-supply voltages of
+5 V to +15 V or dual supply voltages of 5 V to 15 V. The
four outputs are buffered and capable of driving a 2 kΩ load.
Data is written to the AD5726 in a 16-bit word format via a
3-wire serial interface.
symmetric bipolar waveforms, which require an accurate, low
drift bipolar reference. The AD588 provides both voltages and
needs no external components. Additionally, the part is
trimmed in production for 12-bit accuracy over the full
temperature range without user calibration.
AV
DD
DAC ARCHITECTURE
2.5V MIN
V
VREFP
Each of the four DACs is a voltage switched, high impedance
(50 kΩ), R-2R ladder configuration. Each 2R resistor is driven by a
pair of switches that connect the resistor to either VREFP or VREFN
0xFFF
.
OUTPUT AMPꢀIFIERS
2.5V MIN
The AD5726 features buffered analog voltage outputs capable of
sourcing and sinking up to 5 mA when operating from 15 V
supplies, eliminating the need for external buffer amplifiers in
most applications while maintaining specified accuracy over the
rated operating conditions. The output amplifiers are short-
circuit protected. The designer should verify that the output
load meets the capabilities of the device, in terms of both output
current and load capacitance. The AD5726 is stable with
capacitive loads up to 2 nF typically. However, any capacitance
load increases the settling time and should be minimized if
speed is a concern.
1 LSB
0x000
–10V MIN
V
VREFN
0V MIN
AV
SS
Figure 22. Output Voltage Range Programming
When driving the reference input, it is important to note that
REFP both sinks and sources current, and that the input currents
of both are code dependent. Many voltage reference products
have limited current sinking capabilities and must be buffered
with an amplifier to drive VREFP to maintain overall system
accuracy. The input VREFN, however, has no such requirement.
The output stage includes a P-channel MOꢀFET to pull the
output voltage down to the negative supply. This is very
important in single-supply systems where VREFN usually has the
same potential as the negative supply. With no load, the zero-
scale output voltage in these applications are less than 500 μV
typically, or less than 1 LꢀB when VREFP = 2.5 V. However, when
sinking current, this voltage does increase because of the finite
impedance of the output stage. The effective value of the pull-
down resistor in the output stage is typically 320 Ω. With a
100 kΩ resistor connected to 5 V, the resulting zero-scale output
voltage is 16 mV. Thus, the best single-supply operation is
obtained with the output load connected to ground, so the
output stage does not have to sink current.
V
For a single 5 V supply, VREFP is limited to 2.5 V at the most, and
must always be at least 2.5 V less than the positive supply to
ensure linearity of the device. For these applications, the AD780
is an excellent low drift 2.5 V reference. It works well with the
AD5726 in a single 5 V system, as shown in Figure 26.
It is recommended that the reference inputs be bypassed with
0.2 μF capacitors when operating with 10 V references. This
limits the reference bandwidth.
Like all amplifiers, the AD5726 output buffers do generate
voltage noise, 5 nV/rtHz typically. This is easily reduced by
adding a simple RC low-pass filter on each output.
VREFP Input Requirements
The AD5726 uses a DAC switch driver circuit that compensates
for different supply, reference voltage, and digital code inputs.
This ensures that all DAC ladder switches are always biased
equally, ensuring excellent linearity under all conditions. Thus,
as indicated in the specifications, the VREFP input of the AD5726
requires both sourcing and sinking current capability from the
reference voltage source. Many positive voltage references are
intended as current sources only and offer little sinking capability.
The user should consider references such as the AD584, AD586,
AD587, AD588, AD780, and REF43 for such an application.
REFERENCE INPUTS
The two reference inputs of the AD5726 allow a great deal of
flexibility in circuit design. The user must take care, however, to
observe the minimum voltage input levels on VREFP and VREFN to
maintain the accuracy shown in the data sheet. These input
voltages can be set anywhere across a wide range within the
supplies, but must be a minimum of 2.5 V apart in any case (see
Figure 22). A wide output voltage range can be obtained with
5 V references that can be provided by the AD588 as shown in
Figure 24. Many applications utilize the DACs to synthesize
Rev. 0 | Page 13 of 20
AD5726
LOAD DAC (
)
LDAC
SERIAꢀ INTERFACE
The AD5726 is controlled over a versatile 3-wire serial interface
that operates at clock rates up to 30 MHz and is compatible with
ꢀPI, QꢀPI™, MICROWIRE™, and DꢀP standards.
LDAC
When asserted, the
pin is an asynchronous, active low,
digital input that transfers the contents of the input register to
the internal data bus, updating the addressed DAC output. New
LDAC
data must not be programmed to the AD5726 while the
pin is low.
Input Shift Register
The input shift register is 16 bits wide. Data is loaded into the
device MꢀB first as a 16-bit word under the control of a serial
clock input ꢀCLK. The input register consists of two address
bits, two don’t care bits, and 12 data bits as shown in Table 11.
The timing diagram for this operation is shown in Figure 2.
and CLRSEL
CLR
CLR
The
control allows the user to perform an asynchronous
CLR
clear function. Asserting
loads all four DAC registers,
forcing the DAC outputs to either zero-scale (0x000) or
Cꢀ
When
is low, the data presented to the input ꢀDIN is shifted
midscale (0x800), depending on the state of CLRꢀEL as shown
MꢀB first into the internal shift register on the rising edge of
ꢀCLK. Once all 16 bits of the serial data-word have been input,
the load control LDAC is strobed, and the word is latched onto
the internal data bus. The two address bits are decoded and used to
route the 12-bit data-word to the appropriate DAC data register.
CLR
Cꢀ CLR
of . When
clear value until
registers with either the data held in the input register prior to
the clear or with new data loaded through the serial interface.
in Table 9. The
function is asynchronous and independent
returns high, the DAC outputs remain at the
LDAC
is strobed, reloading the individual DAC
Operation of and SCLK
CS
CLR
Table 9.
CꢀR
/CLRSEL Truth Table
Cꢀ
The
and ꢀCLK pins are internally fed to the same logical OR
CꢀRSEꢀ
DAC Registers
gate and, therefore, require careful attention during a load cycle
to avoid clocking in false data bits. As shown in the timing
diagram in Figure 2, ꢀCLK must be halted high, or
brought high, during the last high portion of ꢀCLK following
the rising edge that clocked in the last data bit. Otherwise, an
0
0
1
1
0
1
0
1
Zero-Scale (0x000)
Midscale (0x800)
No Change
Cꢀ
must be
No Change
Cꢀ
additional rising edge is generated by
rising while ꢀCLK is
to act as the clock and allowing a false data bit
Table 10. DAC Address Word Decode Table
Cꢀ
low, causing
A1
A0
DAC Addressed
into the input shift register. The same must also be considered
for the beginning of the data load sequence.
0
0
0
1
DAC A
DAC B
1
1
0
1
DAC C
DAC D
Coding
The AD5726 uses binary coding. The output voltage can be
calculated from the following equation:
(
VREFP −VREFN × D
)
VOUT = VREFN
+
4096
where D is the digital code in decimal.
Table 11. Input Register Format
DB0
DB1
DB2
DB3
DB4
DB5
DB6
DB7
DB8
DB9
DB10 DB11 DB12 DB13 DB14 DB15
D5 D4 D3 D2 D1 D0
A1
A0
X
X
D11
D10
D9
D8
D7
D6
Rev. 0 | Page 14 of 20
AD5726
APPLICATIONS
Figure 24 (symmetrical bipolar operation) shows the AD5726
configured for 10 V operation. ꢀee the AD688 datasheet for a
full explanation of the reference operation.
POWER-UP SEQUENCE
To prevent CMOꢀ latch-up conditions, powering AVDD, AVꢀꢀ,
and GND prior to any reference voltages is recommended. The
ideal power-up sequence is GND, AVꢀꢀ, AVDD, VREFP, VREFN, and
the digital inputs. Noncompliance with the power-up sequence
over an extended period can elevate the reference currents and
eventually damage the device. On the other hand, if the non-
compliant power-up sequence condition is as short as a few
milliseconds, the device can resume normal operation without
damage once AVDD/AVꢀꢀ are powered up.
Adjustments may not be necessary for many applications
because the AD688 is a very high accuracy reference. However,
if additional adjustments are required, adjust the AD5726 full-
scale first. Begin by loading the digital full-scale code (0xFFF).
Then, modify the gain adjust potentiometer to attain a DAC
output voltage of 9.9976 V. Next, alter the balance adjust to set
the midscale output voltage to 0.000 V.
The 0.2 μF bypass capacitors shown at their reference inputs in
Figure 24 should be used whenever 10 V references are used.
Applications with single references or references to 5 V may
not require the 0.2 μF bypassing. The 6.2 Ω resistor in series
with the output of the reference amplifier keeps the amplifier
from oscillating with the capacitive load. This has been found to
be large enough to stabilize this circuit. Larger resistor values
are acceptable if the drop across the resistor does not exceed a VBE.
Assuming a minimum VBE of 0.6 V and a maximum current of
2.75 mA, the resistor should be under 200 Ω for the loading of a
single AD5726.
REFERENCE CONFIGURATION
Output voltage ranges can be configured as either unipolar or
bipolar, and within these choices, a wide variety of options
exists. The unipolar configuration can be either a positive (as
shown in Figure 23) or a negative voltage output. The bipolar
configuration can be either symmetrical (as shown in Figure 24)
or nonsymmetrical.
+15V
+15V
+
V
REFP
AV
INPUT
DD
OP1177
Using two separate references is not recommended. Having two
references may cause different drifts with time and temperature,
whereas with a single reference, most drifts track.
OUTPUT
TRIM
0.2µF
AD5726
ADR01
0.1µF║10µF
10kꢀ
V
REFN
Unipolar positive full-scale operation can usually be set by a
reference with the correct output voltage. This is preferable to
using a reference and dividing down to the required value. For a
10 V full-scale output, the circuit can be configured as shown in
Figure 25. In this configuration, the full-scale value is first set by
adjusting the 10 kΩ resistor for a full-scale output of 9.9976 V.
AV
SS
+10V OPERATION
–15V
Figure 23. Unipolar +10 V Operation
+15V
+15V
U1
39kꢀ
V
V
OUT
+15V
IN
+15V
ADR01
TEMP TRIM
6
4
AV
DD
3
1
AV
DD
V
REFP
6.2ꢀ
V
BALANCE
REFP
+15V
12
5
GND
100kꢀ
0.2µF
AD5726
0.1µF║10µF
AD688 FOR ±10V
AD588 FOR ±5V
AD5726
U2
V+
OP1177
V–
0.1µF║10µF
14
15
V
GAIN
100kꢀ
REFN
6.2ꢀ
AV
SS
0.2µF
V
REFN
AV
0.2µF
SS
8
13
7
–15V
–15V
0V TO –10V OPERATION
1µF
–15V
±5 OR ±10V OPERATION
Figure 25. Unipolar −10 V Operation
Figure 25 shows the AD5726 configured for −10 V to 0 V opera-
tion. An ADR01 and OP1177 are configured to produce a −10 V
output that is connected directly to VREFP for the reference voltage.
Figure 24. Symmetrical Bipolar Operation
Rev. 0 | Page 15 of 20
AD5726
Single +5 V Supply Operation
The ground path (circuit board trace) should be as wide as
possible to reduce any effects of parasitic inductance and ohmic
drops. A ground plane is recommended if possible. The noise
immunity of the on-board digital circuitry, typically in the
hundreds of millivolts, is well able to reject the common-mode
noise typically seen between system analog and digital grounds.
Finally, the analog and digital ground should be connected to
each other at a single point in the system to provide a common
reference. This is preferably done at the power supply
For operation with a 5 V supply, the reference voltage should be
set between 1.0 V and 2.5 V for optimum linearity. Figure 26
shows an AD780 used to supply a 2.5 V reference voltage. The
headroom of the reference and DAC are both sufficient to support
a 5 V supply with 5 V tolerance. AVDD and VL should be
connected to the same supply. ꢀeparate bypassing to each pin
should be used.
5V
Good grounding practice is essential to maintain analog perform-
ance in the surrounding analog support circuitry as well. With
two reference inputs and four analog outputs capable of moderate
bandwidth and output current, there is a significant potential
for ground loops. Again, a ground plane is recommended as
the most effective solution to minimize errors due to noise and
ground offsets.
10µF
0.01µF
INPUT
AV
DD
V
OUTPUT
TRIM
REFP
0.2µF
AD780
0.1µF║10µF
10kꢀ
AD5726
GND
V
REFN
The AD5726 should have ample supply bypassing located as
close to the package as possible. Recommended capacitor values
are 10 μF in parallel with 0.1 μF. The 0.1 μF capacitor should
have low effective series resistance (EꢀR) and effective series
inductance (EꢀI), such as the common ceramic types, which
provide a low impedance path to ground at high frequencies to
handle transient currents due to internal logic switching.
AV
SS
0V TO 2.5V OPERATION
SINGLE 5V SUPPLY
Figure 26. 5 V Single-Supply Operation
POWER SUPPꢀY BYPASSING AND GROUNDING
In any circuit where accuracy is important, careful consideration
to the power supply and ground return layout helps to ensure
the rated performance. The AD5726 has a single ground pin
that is internally connected to the digital section as the logic
reference level. The user’s first instinct may be to connect this
pin to the digital ground; however, in large systems, the digital
ground is often noisy because of the switching currents of other
digital circuitry. Any noise introduced at the ground pin could
couple into the analog output. Thus, to avoid error-causing
digital noise in the sensitive analog circuitry, the ground pin
should be connected to the system analog ground.
GAꢀVANICAꢀꢀY ISOꢀATED INTERFACE
In many process control applications, it is necessary to provide
an isolation barrier between the controller and the unit being
controlled to protect and isolate the controlling circuitry from any
hazardous common-mode voltages that may occur. Isocouplers
provide voltage isolation in excess of 2.5 kV. The serial loading
structure of the AD5726 makes it ideal for isolated interfaces
because the number of interface lines is kept to a minimum.
Figure 27 shows a 4-channel isolated interface connected to the
AD5726 using an ADuM1400.
MICROCONTROLLER
ADuM1400*
V
V
V
V
V
V
IA
OA
OB
OC
OD
TO SCLK
TO SDIN
TO CS
SERIAL CLOCK OUT
SERIAL DATA OUT
ENCODE
ENCODE
ENCODE
ENCODE
DECODE
DECODE
DECODE
DECODE
IB
V
IC
ID
SYNC OUT
V
TO LDAC
CONTROL OUT
*ADDITIONAL PINS OMITTED FOR CLARITY.
Figure 27. Isolated Interface
Rev. 0 | Page 16 of 20
AD5726
The 8xC51 transmits data in 8-bit bytes with only eight falling
clock edges occurring in the transmit cycle. Because the DAC
MICROPROCESSOR INTERFACING
Microprocessor interfacing to the AD5726 is via a serial bus
that uses standard protocol compatible with microcontrollers
and DꢀP processors. The communications channel is a 3-wire
interface (minimum) consisting of a clock signal, a data signal,
and a synchronization signal. The AD5726 requires a 16-bit
data-word with data valid on the falling edge of ꢀCLK.
Cꢀ
expects a 16-bit word,
(P3.3) must be left low after the first
eight bits are transferred. After the second byte has been
transferred, the P3.3 line is taken high. The DAC can be
LDAC
updated using
via P3.4 of the 8xC51
8xC51*
RxD
AD5726*
SDIN
For all the interfaces, the DAC output update can be done
automatically when all the data is clocked in, or it can be done
TxD
P3.3
P3.4
SCLK
CS
LDAC
under the control of
.
LDAC
MC68HC11 Interface
*ADDITIONAL PINS OMITTED FOR CLARITY.
Figure 28 shows an example of a serial interface between the
AD5726 and the MC68HC11 microcontroller. The serial
peripheral interface (ꢀPI) on the MC68HC11 is configured for
master mode (MꢀTR = 1); clock polarity bit (CPOL = 0), and
the clock phase bit (CPHA = 1). The ꢀPI is configured by writing
to the ꢀPI control register (ꢀPCR); see the 68HC11 User Manual.
ꢀCK of the MC68HC11 drives the ꢀCLK of the AD5726, the
MOꢀI output drives the serial data line (ꢀDIN) of the AD5726.
Figure 29. 8xC51 to AD5726 Interface
PIC16C6x/7x Interface
The PIC16C6x/7x synchronous serial port (ꢀꢀP) is configured as
an ꢀPI master with the clock polarity bit set to 0. This is done by
writing to the synchronous serial port control register (ꢀꢀPCON).
ꢀee the PIC16/17 Microcontroller User Manual. In this example,
Cꢀ
I/O port RA1 is being used to pulse
and enable the serial
Cꢀ
The
is driven from one of the port lines, in this case PC7.
port of the AD5726. This microcontroller transfers only eight
bits of data during each serial transfer operation; therefore, two
consecutive write operations are needed. Figure 30 shows the
connection diagram.
Cꢀ
When data is being transmitted to the AD5726, the
line
(PC7) is taken low and data is transmitted MꢀB first. Data
appearing on the MOꢀI output is valid on the falling edge of
ꢀCK. Eight falling clock edges occur in the transmit cycle; thus,
to load the required 16-bit word, PC7 is not brought high until
the second 8-bit word has been transferred to the DACs input
shift register.
PIC16C6x/7x*
AD5726*
SDO/RC5
SCLK/RC3
RA1
SDIN
SCLK
CS
MC68HC11*
MOSI
AD5726*
SDIN
*ADDITIONAL PINS OMITTED FOR CLARITY.
Figure 30. PIC16C6x/7x to AD5726 Interface
SCK
PC7
SCLK
CS
Blackfin® DSP interface
Figure 31 shows how the AD5726 can be interfaced to the
Analog Devices Blackfin DꢀP. The Blackfin has an integrated
ꢀPI port that can be connected directly to the ꢀPI pins of the
AD5726. It also has programmable I/O pins that can be used to
*ADDITIONAL PINS OMITTED FOR CLARITY.
Figure 28. MC68HC11 to AD5726 Interface
8xC51 Interface
LDAC
set the state of a digital input such as the
pin.
The AD5726 requires a clock synchronized to the serial data.
For this reason, the 8xC51 must be operated in Mode 0. In this
mode, serial data is transferred through RxD, and a shift clock
is output on TxD.
ADSP-BF531
AD5726*
SPISELx
SCK
CS
SCLK
SDIN
LDAC
P3.3 and P3.4 are bit-programmable pins on the serial port and
MOSI
PF10
Cꢀ
LDAC
are used to drive
and , respectively. The 8Cx51 provides
the LꢀB of its ꢀBUF register as the first bit in the data stream. The
user must ensure that the data in the ꢀBUF register is arranged
correctly because the DAC expects MꢀB first. When data is to
be transmitted to the DAC, P3.3 is taken low. Data on RxD is
clocked out of the microcontroller on the rising edge of TxD
and is valid on the falling edge. As a result, no glue logic is
required between this DAC and the microcontroller interface.
*ADDITIONAL PINS OMITTED FOR CLARITY.
Figure 31. Blackfin DSP to AD5726 Interface
Rev. 0 | Page 17 of 20
AD5726
OUTLINE DIMENSIONS
6.50
6.20
5.90
9
8
16
5.60
5.30
5.00
8.20
7.80
7.40
1
0.25
0.09
1.85
1.75
1.65
2.00 MAX
8°
4°
0°
0.95
0.75
0.55
0.38
0.22
0.05 MIN
SEATING
PLANE
COPLANARITY
0.10
0.65 BSC
COMPLIANT TO JEDEC STANDARDS MO-150-AC
Figure 32. 16-Lead Shrink Small Outline Package [SSOP]
(RS-16)
Dimensions shown in millimeters
10.50 (0.4134)
10.10 (0.3976)
16
9
8
7.60 (0.2992)
7.40 (0.2913)
1
10.65 (0.4193)
10.00 (0.3937)
0.75 (0.0295)
0.25 (0.
0098)
1.27 (0.0500)
BSC
45°
2.65 (0.1043)
2.35 (0.0925)
0.30 (0.0118)
0.10 (0.0039)
8°
0°
COPLANARITY
0.10
SEATING
PLANE
0.51 (0.0201)
0.31 (0.0122)
1.27 (0.0500)
0.40 (0.0157)
0.33 (0.0130)
0.20 (0.0079)
COMPLIANT TO JEDEC STANDARDS MS-013-AA
CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS
(IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR
REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN.
Figure 33. 16-Lead Standard Small Outline Package [SOIC_W]
Wide Body
(RW-16)
Dimensions shown in millimeters and (inches)
ORDERING GUIDE
Model
AD5726YRSZ-500RL71
AD5726YRSZ-REEL1
AD5726YRWZ-REEL1
AD5726YRWZ-REEL71
Temperature Range
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
Package Description
16-Lead SSOP
16-Lead SSOP
16-Lead SOIC_W
16-Lead SOIC_W
Package Option
RS-16
RS-16
RW-16
RW-16
1 Z = RoHS Compliant Part.
Rev. 0 | Page 18 of 20
AD5726
NOTES
Rev. 0 | Page 19 of 20
AD5726
NOTES
©2007 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
D06469-0-4/07(0)
Rev. 0 | Page 20 of 20
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