ACT4455YH-T_技术文档

ACT4455

Rev 2, 21-Nov-12

36V/5A Step Down DC/DC Converter

FEATURES

APPLICATIONS

• Automotive Industry

• Dual-Output Car Charger

• LCD-TV

• 7.5V to 36V Input Voltage

• 40V Input Voltage Surge

• Up to 5A Output Current

• Up to 12V Output Voltage

GENERAL DESCRIPTION

• Dual Outputs with Independent Over Current

ACT4455 is a wide input voltage step-down DC/DC

converter with high-side MOSFET integrated. It

provides up to 5A continuous output current at

200kHz switching frequency. The converter can be

configured as single output or dual outputs with

independent over current protection. The converter

achieves high efficiency and excellent load and line

regulation. The converter enters into hiccup and

sleeping mode and the converter power

consumption is nearly zero when output is

overloaded or shorted to ground. Other protection

features includes cycle-by-cycle current limit, under

voltage protection and thermal shutdown. The

device is available in SOP8-EP package.

Protection

• 7.5% Accurate Over Current Protection (OCP)

• Integrated 45mΩ High Side Power FET

• 90% Efficiency at Heavy Load

• Internal 3ms Soft Startup

• Low Standby Input Current

• Sleeping Mode at OCP, OTP and SCP

• Zero Input and Output Currents at Over Current

and Short Circuit Protection

• Auto Recovery into Full Load after Faults

• Output Cord Voltage Drop Compensation

• Stable with Low ESR Ceramic Output Capacitors

• Internal Cycle-by-Cycle Current Control

• Programmable Over Current Setting

• SOP-8EP Package

Efficiency vs. Load current

100

V_IN= 12V

90

80

V_IN= 24V

V_IN= 32V

70

60

50

0

1000

2000

3000

4000

5000

Efficiency (%)

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ACT4455

Rev 2, 21-Nov-12

ORDERING INFORMATION

PART NUMBER OPERATION TEMPERATURE RANGE

PACKAGE

PINS

PACKING

ACT4455YH-T

-40°C to 85°C

SOP-8EP

8

TAPE & REEL

PIN CONFIGURATION

PIN DESCRIPTIONS

NAME

DESCRIPTION

The output current of V_OUT1is sensed by this pin. When the voltage on this pin reaches

116mV for 750µs, the IC shuts down for 2.5 seconds before initiating a restartup.

1

CS1

2

3

SW

Switch Output. Connect this pin to the switching end of the external inductor.

High Side Bias. This pin acts as the positive rail for the high-side switch’s gate driver.

Connect a 22nF-100nF capacitor between HSB and SW pins.

HSB

4

5

6

GND

COMP

FB

Ground.

Compensation Node. COMP is used to compensate the voltage regulation loop.

Feedback Input. FB senses the output voltage to regulate that voltage. Drive FB with a

resistive voltage divider from the output voltage. The feedback threshold is 0.808V.

See Setting the Output Voltage.

7

8

IN

Input Supply. Bypass this pin to GND with a 10µF or greater low ESR capacitor.

The output current of V_OUT2is sensed by this pin. When the voltage on this pin reaches

116mV for 750µs, the IC shuts down for 2.5 seconds and then restarts.

CS2

Exposed Pad Exposed Pad. Connect this pad to thick copper plane via copper vias.

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ACT4455

Rev 2, 21-Nov-12

ABSOLUTE MAXIMUM RATINGS^c

PARAMETER

IN to GND

VALUE

UNIT

-0.3 to 44

V

SW to GND

-0.3 to V_IN+ 0.3

_SW- 0.3 to V_SW+ 7

-0.3 to + 6

50

V

HSB to GND

V

FB, CS1, CS2, COMP to GND

Junction to Ambient Thermal Resistance

Operating Junction Temperature

Storage Junction Temperature

Lead Temperature (Soldering 10 sec.)

V

°C/W

°C

-40 to 150

-55 to 150

300

c: Do not exceed these limits to prevent damage to the device. Exposure to absolute maximum rating conditions for long periods may

affect device reliability.

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ACT4455

Rev 2, 21-Nov-12

ELECTRICAL CHARACTERISTICS

(V_IN= 12V, T_A= 25°C, unless otherwise specified.)

PARAMETER

SYMBOL

V_FB

TEST CONDITIONS

MIN

TYP

MAX UNIT

Feedback Voltage

7.5V ≤ V_IN≤ 40V

798

808

4000

650

41

818

mV

V/V

µA/V

V

Error Amplifier Voltage Gain

Error Amplifier Transconductance

Over Voltage Protection Threshold

Max E/A Source Current

A_EA

G_EA

∆I_COMP= ± 10µA

V_OVP

I_SRCMAX

I_SINKMAX

R_DS(ON)1

R_DS(ON)2

D_MAX

V_FB= 0.5V

V_FB= 1.0V

At 25°C

120

38

µA

mΩ

Ω

Max E/A Sink Current

High-Side Switch ON-Resistance

Low-Side Switch ON-Resistance

Maximum Duty Cycle

5

80

%

Switching Frequency

F_SW

180

200

6.5

220

kHz

A

Upper Switch Current Limit

I_LIM

Duty Cycle = 65%

COMP to Current Limit

Transconductance

G_COMP

T_{ON_MIN}

V_{IN_Rise}

5

250

7

A/V

ns

V

Minimum on Time

Input Under Voltage Lockout Thresh-

old

V_INRising

V_INFalling

6.75

7.25

Input Under Voltage Lockout Hystere-

sis

V_{IN_Falling}

650

mV

Internal Soft Startup Time

CS1 reference voltage

T_SS

V_CS1

3.0

116

0.65

ms

mV

V

113

119

CS2 reference voltage

V_CS2

Frequency Foldback Threshold

V_{FB_Foldback}

V

5A

_IN= 12V, R_FB1=200k, I_OUT

=

Cord Compensation

Thermal Shutdown

0.35

150

V

°C

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ACT4455

Rev 2, 21-Nov-12

FUNCTIONAL BLOCK DIAGRAM

FUNCTIONAL DESCRIPTION

FB is lower than the reference voltage, COMP

tends to go higher to increase current to the output.

Operation

As seen in Functional Block Diagram, the ACT4455

is a current mode controlled regulator. The EA

output voltage (COMP voltage) is proportional to

the peak inductor current.

Over Current and Short Circuit

Protection

CS pins are connected to the high side of current

sensing resistors to prevent output over current.

With independent CS1 and CS2 pins, two output

currents are detected. If the voltage at either CS

pins exceeds 116mV for more than 750µs. The

converter shuts down and goes into sleeping mode.

A new soft startup is triggered after 2.5s. If the fault

condition is un-cleared, the converter shuts down

again until over current condition is cleared. With

this long-waiting-time hiccup mode, the power

consumption at over loading or outputs short is

reduced to nearly zero.

A switching cycle starts when the rising edge of the

Oscillator clock output causes the High-Side Power

Switch to turn on and the Low-Side Power Switch to

turn off. With the SW side of the inductor now

connected to IN, the inductor current ramps up to

store energy. The inductor current level is

measured by the Current Sense Amplifier and

added to the Oscillator ramp signal. If the resulting

summation is higher than the COMP voltage, the

output of the PWM Comparator goes high. When

this happens or when Oscillator clock output goes

low, the High-Side Power Switch turns off and the

inductor freewheels through the schottky diode

causing the inductor current to decrease and

magnetic energy to be transferred to output. This

state continues until the cycle starts again. The

High-Side Power Switch is driven by logic using

HSB as the positive rail. This pin is charged to V_SW

+ 5V when the Low-Side Power Switch turns on.

The Comp voltage is the integration of the error

between FB input and internal 0.808V reference. If

Thermal Shutdown

The ACT4455 shuts down when its junction

temperature exceeds 150°C. The converter triggers

a soft-start when the temperature has dropped by

10°C. The soft-restart avoids output over voltage at

thermal hiccup.

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ACT4455

Rev 2, 21-Nov-12

APPLICATIONS INFORMATION

With a selected inductor value the peak-to-peak

inductor current is estimated as:

Output Voltage Setting

_

Figure 1:

(

)

V_OUT× V_INV_OUT

I_LPK_{_}

=

(4)

(5)

PK

Output Voltage Setting

L×V_IN×f_SW

The peak inductor current is estimated as:

1

I_LPK= I_LOADMAX

+

I_LPK

^_PK

2

The selected inductor should not saturate at I_LPK.

The maximum output current is calculated as:

1

_

I_OUTMAX= I_LIM

I_LPK

^_PK

(6)

2

I_LIMis the internal current limit, which is typically

6.5A, as shown in Electrical Characteristics Table.

Figure 1 shows the connections for setting the

output voltage. Select the proper ratio of the two

feedback resistors R_FB1and R_FB2based on the

output voltage. Typically, use R_FB2≈ 10kΩ and

determine R_FB1from the following equation:

Input Capacitor

The input capacitor needs to be carefully selected

to maintain sufficiently low ripple at the supply input

of the converter. A low ESR capacitor is highly

recommended. Since large current flows in and out

of this capacitor during switching, its ESR also

affects efficiency.

V_OUT

⎛

⎜

⎞

⎟

R_{FB 1}= R_{FB 2}

− 1

(1)

0.808 V

⎝

⎠

Over Current Protection Setting

The output over current threshold is calculated by:

The input capacitance needs to be higher than

10µF. The best choice is the ceramic type,

however, low ESR tantalum or electrolytic types

may also be used provided that the RMS ripple

current rating is higher than 50% of the output

current. The input capacitor should be placed close

to the IN and G pins of the IC, with the shortest

traces possible. In the case of tantalum or

electrolytic types, they can be further away if a

small parallel 0.1µF ceramic capacitor is placed

right next to the IC.

I_OCP1= I_OCP2= 116mV / R_SENSE

(2)

It is recommended that 1% or 0.5% high-accuracy

current sensing resistor is selected to achieve high-

accuracy over current protection. Two over current

protection thresholds can be different based on

different current sensing resistance.

Inductor Selection

The inductor maintains a continuous current to the

output load. This inductor current has a ripple that is

dependent on the inductance value:

Output Capacitor

The output capacitor also needs to have low ESR to

keep low output voltage ripple. The output ripple

voltage is:

Higher inductance reduces the peak-to-peak ripple

current. The trade off for high inductance value is

the increase in inductor core size and series

resistance, and the reduction in current handling

capability. In general, select an inductance value L

based on ripple current requirement:

V_IN

+

V_RIPPLE= I_OUTMAXK_RIPPLER_ESR

(7)

28 × f_SW²LC_OUT

Where I_OUTMAXis the maximum output current,

K_RIPPLEis the ripple factor, R_ESRis the ESR of the

output capacitor, f_SWis the switching frequency, L is

the inductor value, and C_OUTis the output

capacitance. In the case of ceramic output

capacitors, R_ESRis very small and does not

_

(

)

V

_OUT× V V_OUT

IN

(3)

L =

V_INf_SWI_LOADMAXK_RIPPLE

where V_INis the input voltage, V_OUTis the output

voltage, f_SWis the switching frequency, I_LOADMAXis

the maximum load current, and K_RIPPLEis the ripple

contribute to the ripple. Therefore,

a

lower

capacitance value can be used for ceramic type. In

the case of tantalum or electrolytic capacitors, the

ripple is dominated by R_ESRmultiplied by the ripple

factor. Typically, choose K_RIPPLE

correspond to the peak-to-peak ripple current being

30% of the maximum load current.

=

30% to

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ACT4455

Rev 2, 21-Nov-12

APPLICATIONS INFORMATION CONT’D

current. In that case, the output capacitor is chosen

to have sufficiently low ESR.

For ceramic output capacitor, typically choose a

capacitance of about 22µF. For tantalum or

electrolytic capacitors, choose a capacitor with less

than 50mꢀ ESR.

Rectifier Diode

Use a Schottky diode as the rectifier to conduct

current when the High-Side Power Switch is off.

The Schottky diode must have current rating higher

than the maximum output current and a reverse

voltage rating higher than the maximum input

voltage.

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ACT4455

Rev 2, 21-Nov-12

STABILITY COMPENSATION

If R_COMPis limited to 15kꢀ, then the actual cross

over frequency is 6.36 / (V_OUTC_OUT). Therefore:

Figure 2:

Stability Compensation

C_COMP=6.67×10⁻⁶V_OUTC_OUT

(F)

(15)

STEP 3. If the output capacitor’s ESR is high

enough to cause a zero at lower than 4 times the

cross over frequency, an additional compensation

capacitor C_COMP2is required. The condition for using

c

C_COMP2is:

c: C_COMP2is needed only for high ESR output capacitor

−6

⎛

⎞

1.1×10

C_OUT

⎜

⎟

R_ESRCOUT≥ Min

,0.012 ×V_OUT

The feedback loop of the IC is stabilized by the

components at the COMP pin, as shown in Figure

2. The DC loop gain of the system is determined by

the following equation:

(Ω)

(16)

⎝

⎠

And the proper value for C_COMP2is:

0.808 V

C_OUTR_ESRCOUT

A_VDC

=

A_VEAG_COMP

C_COMP2

=

(8)

(17)

I_OUT

R_COMP

Though C_COMP2is unnecessary when the output

capacitor has sufficiently low ESR, a small value

The dominant pole P1 is due to C_COMP

:

G_EA

C_COMP2such as 100pF may improve stability against

f_P1

=

(9)

2πA_VEAC_COMP

PCB layout parasitic effects.

The second pole P2 is the output pole:

Table 1 shows some calculated results based on

the compensation method above.

I_OUT

f_{P 2}

=

(10)

2πV_OUTC_OUT

Table 1:

The first zero Z1 is due to R_COMPand C_COMP

:

Typical Compensation for Different Output

Voltages and Output Capacitors

1

f_Z1

=

(11)

2πR_COMPC_COMP1

c

V_OUT

2.5V

3.3V

5V

C_OUT

R_COMPC_COMPC_COMP2

And finally, the third pole is due to R_COMPand

47μF SP CAP

5.6kꢀ

7.5kꢀ

11kꢀ

5.6nF

4.7nF

3.3nF

4.7nF

None

C_COMP2(if C_COMP2is used):

1

None

f_P3

=

(12)

2πR_COMPC_COMP2

2.5V 680μF/6.3V/30mꢀ 15kꢀ

3.3V 680μF/6.3V/30mꢀ 15kꢀ

220pF

The following steps should be used to compensate

the IC:

5V

680μF/6.3V/30mꢀ 15kꢀ

STEP 1. Set the cross over frequency at 1/10 of the

c: C_COMP2is needed for high ESR output capacitor.

switching frequency via R_COMP

:

2πV_OUTC_OUTf_SW

10G_EAG_COMP× 0.808V

Output Cable Resistance Compensation

R_COMP

=

To compensate for resistive voltage drop across the

charger's output cable, the ACT4455 integrates a

simple, user-programmable cable voltage drop

compensation using the impedance at the FB pin.

Use the curve in Figure 3 to choose the proper

feedback resistance values for cable compensation.

= 0.48 ×10 ⁸V_OUTC_OUT

(13)

(Ω)

STEP 2. Set the zero f_Z1at 1/4 of the cross over

frequency. If R_COMPis less than 15kꢀ, the equation

for C_COMPis:

R_FB1is the high side resistor of voltage divider.

3.18 × 10 ⁻⁵

C_COMP

=

(F)

(14)

R_COMP

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ACT4455

Rev 2, 21-Nov-12

STABILITY COMPENSATION CONT’D

In the case of high R_FB1used, the frequency

single point for best noise immunity. Connect

exposed pad to power ground copper area with

copper and vias.

compensation

needs

to

be

adjusted

correspondingly. As show in Figure 4, adding a

capacitor in paralled with R_FB1or increasing the

compensation capacitance at COMP pin helps the

system stability.

4) Use copper plane for power GND for best heat

dissipation and noise immunity.

5) Place feedback resistor close to FB pin.

Figure 3:

6) Use short trace connecting HSB-C_HSB-SW loop

Cable Compensation at Various Resistor Divider

Values

7) SW pad is noisy node switching from V_INto

GND. It should be isolated away from the rest

of circuit for good EMI and low noise operation.

Delta Output Voltage vs. Output Current

0.6

0.5

v

0.4

0.3

0.2

0.1

0

1000

2000

3000

4000

5000

Output Current (mA)

Figure 4:

Frequency Compensation for High R_FB1

PC Board Layout Guidance

When laying out the printed circuit board, the

following checklist should be used to ensure proper

operation of the IC.

1) Arrange the power components to reduce the

AC loop size consisting of C_IN, IN pin, SW pin

and the schottky diode.

2) Place input decoupling ceramic capacitor C_INas

close to IN pin as possible. C_INis connected

power GND with vias or short and wide path.

3) Return FB, COMP and ISET to signal GND pin,

and connect the signal GND to power GND at a

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ACT4455

Rev 2, 21-Nov-12

Figure 5:

Typical Application Circuit for 5V/4.2A Dual-output Car Charger

Table 2:

BOM List for 5V/4.2A Dual-output Car Charger

ITEM REFERENCE

DESCRIPTION

MANUFACTURER

QTY

1

2

U1

C1

IC ACT4455YH, SOP-8EP

Active-Semi

Koshin

Capacitor, Electrolytic, 150µF/50V, 8×8mm

Capacitor, Electrolytic, 680µF/10V, 8×11.5mm

Capacitor, Ceramic, 10µF/50V, 1206, SMD

Capacitor, Ceramic, 4.7nF/25V, 0603, SMD

Capacitor, Ceramic, 220pF/25V, 0603, SMD (Optional)

Capacitor, Ceramic, 2.2nF/25V, 0603, SMD

Capacitor, Ceramic, 1000pF/25V, 0603, SMD (Optional)

Capacitor, Ceramic, 100pF/25V, 0603, SMD (Optional)

Capacitor, Ceramic, 2200pF/25V, 0805, SMD

Capacitor, Ceramic, 2.2µF/16V, 0603, SMD

Inductor, 18µH, 5A, 20%, DIP

1

3

C2

Koshin

1

4

C3

Murata, TDK

Electronic-Magnetics

Vishay

1

5

C4

1

6

C5

1

7

C6

1

8

C7

1

9

C8

1

10

11

12

13

14

15

16

17

18

C9

1

C10

L1

1

D1

Diode, Schottky, 45V/10A, V10L45

1

R1, R2

R3

Chip Resistor, 50mꢀ, 1206, 1%

Murata, TDK

2

Chip Resistor, 9.7kꢀ, 0603, 1%

1

R4

Chip Resistor, 51kꢀ, 0603, 1%

1

R5

Chip Resistor, 15kꢀ, 0603, 5%

1

R6

Chip Resistor, 5.1ꢀ, 1206, 5%

1

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ACT4455

Rev 2, 21-Nov-12

TYPICAL PERFORMANCE CHARACTERISTICS

(Circuit of Figure 7, R_CS1= R_CS2= 50mꢀ, L = 18µH, C_IN= 150µF, C_OUT= 680µF, T_A= 25°C, unless otherwise specified.)

Efficiency vs. Load current

Switching Frequency vs. Input Voltage

100

90

80

70

60

50

250

200

150

100

50

V_IN= 12V

V_IN= 24V

V_IN= 32V

0

5

10

15

20

25

30

35

40

0

1000

2000

3000

4000

5000

Input Voltage (V)

Efficiency (%)

Maximum Peak Current vs. Duty Cycle

Switching Frequency vs. Feedback Voltage

250

9

8.5

8

200

150

100

50

7.5

7

6.5

6

0

0.2

0.4

0.6

0.8

1

0.15

0.25

0.35

0.45

0.55

0.65

0.75 0.85

Feedback Voltage (mV)

Duty cycle

Input Current vs. Input Voltage at No Load

Standby Current vs. Input Voltage

14

940

920

900

880

860

840

820

800

12

10

8

6

4

2

0

5

10

15

20

25

30

35

40

5

10

15

20

25

30

35

40

Input Voltage (V)

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ACT4455

Rev 2, 21-Nov-12

TYPICAL PERFORMANCE CHARACTERISTICS CONT’D

(Circuit of Figure 7, R_CS1= R_CS2= 50mꢀ, L = 18µH, C_IN= 150µF, C_OUT= 680µF, T_A= 25°C, unless otherwise specified.)

Input Current at Output Short Output

Vcs vs. Temperature

1.2

0.18

1

0.17

0.8

0.16

0.6

V_CS1

0.15

0.4

0.14

V_CS2

0.2

0.13

0

-25

0

25

50

75

100

125

150

5

10

15

20

25

30

35

40

Temperature (°C)

Input Voltage (V)

SW vs. Output Ripples

Start Up

V_IN= 12V

V_OUT= 5V

R_LORD= 1.5ꢀ

V_IN= 12V

I_OUT= 0A

I_OUT= 1A

I_ISET= 2A

V_IN= 12V

CH1

CH2

CH1

CH2

CH1: Ripper, 50mV/div

CH2: SW, 10V/div

TIME: 2µs/div

CH1: V_OUT, 2V/div

CH2: V_IN, 5V/div

TIME: 1ms/div

SW vs. Output Ripples

Load Step Waveforms

V_IN= 12V

I_OUT= 4.2A

V_IN= 12V

_OUT1= 0.08-2.1A

I

I_OUT2= 0A

CH1

CH2

CH1: Ripper, 50mV/div

CH2: SW, 10V/div

TIME: 2µs/div

CH1: V_OUTRipple, 200mV/div

CH2: I_OUT, 2A/div

TIME: 400µs/div

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ACT4455

Rev 2, 21-Nov-12

TYPICAL PERFORMANCE CHARACTERISTICS CONT’D

(Circuit of Figure 7, R_CS1= R_CS2= 50mꢀ, L = 18µH, C_IN= 150µF, C_OUT= 680µF, T_A= 25°C, unless otherwise specified.)

Load Step Waveforms

Short Circuit

V_IN= 12V

I_OUT1= 0-2.1A

I_OUT2= 2.1A

CH1

V_IN= 12V

I_OUT1= 2.1A

I_OUT2= 0A

CH1

CH2

CH3

CH1: V_OUTRipper, 200mV/div

CH2: I_OUT, 2A/div

CH1: V_OUT, 5V/div

CH2: IL, 2A/div

TIME: 400µs/div

CH3: SW, 10V/div

TIME: 400µs/div

Short Circuit

Short Circuit Recovery

V_IN= 12V

I_OUT1= 2.1A

I_OUT2= 0A

CH1

V_IN= 12V

I_OUT1= 2.1A

I_OUT2= 2.1A

CH1

CH2

CH3

CH2

CH3

CH1: V_OUT, 5V/div

CH2: IL, 2A/div

CH3: SW, 10V/div

TIME: 400µs/div

CH1: V_OUT, 2V/div

CH2: IL, 2A/div

CH3: SW, 10V/div

TIME: 1ms/div

Hiccup Mode

Short Circuit Recovery

V_IN= 12V

I_OUT1= 2.1A

I_OUT2= 2.1A

I_OUT1= 2.1A

I_OUT2= 2.1A

CH1

CH2

CH1

CH2

CH1: V_OUT, 2V/div

CH2: IL, 2A/div

CH3: SW, 10V/div

TIME: 1ms/div

CH1: V_OUT, 5V/div

CH2: SW, 5V/div

TIME: 1s/div

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ACT4455

Rev 2, 21-Nov-12

TYPICAL PERFORMANCE CHARACTERISTICS CONT’D

(Circuit of Figure 7, R_CS1= R_CS2= 50mꢀ, L = 18µH, C_IN= 150µF, C_OUT= 680µF, T_A= 25°C, unless otherwise specified.)

Input Surge

V_IN= 8V-40V

I_OUT1= 2.1A

I_OUT2= 0 A

V_IN= 8V-40V

I_OUT1= 2.1A

I_OUT2= 2.1A

V_IN= 24V

_OUT= 5V

I_ISET= 2.1A

V

CH1

CH2

CH1: V_IN, 10V/div

CH2: V_OUTRipper, 200mV/div

TIME: 10ms/div

CH1: V_IN, 10V/div

CH2: V_OUTRipper, 200mV/div

TIME: 10ms/div

Innovative Power^TM

- 14 -

www.active-semi.com

ACT4455

Rev 2, 21-Nov-12

PACKAGE OUTLINE

SOP-8EP PACKAGE OUTLINE AND DIMENSIONS

DIMENSION IN

MILLIMETERS

DIMENSION IN

INCHES

SYMBOL

MIN

MAX

1.700

0.100

1.550

0.510

0.250

5.100

3.402

4.000

6.200

2.513

MIN

MAX

A

A1

A2

b

1.350

0.000

1.350

0.330

0.170

4.700

3.202

3.800

5.800

2.313

0.053 0.067

0.000 0.004

0.053 0.061

0.013 0.020

0.007 0.010

0.185 0.200

0.126 0.134

0.150 0.157

0.228 0.244

0.091 0.099

0.050 TYP

c

D

D1

E

E1

E2

e

1.270 TYP

0.400

0°

1.270

8°

0.016 0.050

L

0°

8°

θ

Active-Semi, Inc. reserves the right to modify the circuitry or specifications without notice. Users should evaluate each

product to make sure that it is suitable for their applications. Active-Semi products are not intended or authorized for use

as critical components in life-support devices or systems. Active-Semi, Inc. does not assume any liability arising out of

the use of any product or circuit described in this datasheet, nor does it convey any patent license.

Active-Semi and its logo are trademarks of Active-Semi, Inc. For more information on this and other products, contact

sales@active-semi.com or visit http://www.active-semi.com.

is a registered trademark of Active-Semi.

Innovative Power^TM

- 15 -

www.active-semi.com


型号：	ACT4455YH-T
厂家：	ACTIVE-SEMI, INC
描述：	36V/5A Step Down DC/DC Converter 36V / 5A降压型DC / DC转换步骤
文件：	总15页 (文件大小：674K)
中文：	中文翻译
下载：	下载PDF数据表文档文件

ACT4455YH-T [ACTIVE-SEMI]

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