AD8137YRZ-REEL7 [AAVID]
Low Cost, Low Power, Differential ADC Driver; 低成本，低功耗差分ADC驱动器
| 型号： | AD8137YRZ-REEL7 |
| 厂家： | 
AAVID THERMALLOY, LLC |
| 描述： | Low Cost, Low Power, Differential ADC Driver |
| 文件： | 总32页 (文件大小：588K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
Low Cost, Low Power,
Differential ADC Driver
AD8137
Data Sheet
FEATURES
FUNCTIONAL BLOCK DIAGRAM
Fully differential
AD8137
–IN
1
2
8
7
6
5
+IN
PD
Extremely low power with power-down feature
2.6 mA quiescent supply current @ 5 V
450 µA in power-down mode @ 5 V
High speed
V
OCM
V
V
3
4
S–
S+
+OUT
–OUT
110 MHz large signal 3 dB bandwidth @ G = 1
450 V/µs slew rate
Figure 1.
12-bit SFDR performance @ 500 kHz
Fast settling time: 100 ns to 0.02%
Low input offset voltage: 2.6 mV max
Low input offset current: 0.45 µA max
Differential input and output
Differential-to-differential or single-ended-to-differential
operation
Rail-to-rail output
Adjustable output common-mode voltage
Externally adjustable gain
Wide supply voltage range: 2.7 V to 12 V
Available in small SOIC package
Qualified for automotive applications
3
2
G = 1
1
0
–1
G = 2
G = 5
–2
–3
–4
–5
–6
–7
–8
–9
G = 10
–10
–11
–12
R
V
= 1kΩ
O, dm
G
= 0.1V p-p
0.1
1
10
FREQUENCY (MHz)
100
1000
APPLICATIONS
ADC drivers
Figure 2. Small Signal Response for Various Gains
Automotive vision and safety systems
Automotive infotainment systems
Portable instrumentation
Battery-powered applications
Single-ended-to-differential converters
Differential active filters
Video amplifiers
Level shifters
GENERAL DESCRIPTON
The AD8137 is a low cost differential driver with a rail-to-rail
output that is ideal for driving ADCs in systems that are sensitive
to power and cost. The AD8137 is easy to apply, and its internal
common-mode feedback architecture allows its output common-
mode voltage to be controlled by the voltage applied to one pin.
The internal feedback loop also provides inherently balanced
outputs as well as suppression of even-order harmonic distortion
products. Fully differential and single-ended-to-differential gain
configurations are easily realized by the AD8137. External
closed-loop gain of the amplifier. The power-down feature is
beneficial in critical low power applications.
The AD8137 is manufactured on Analog Devices, Inc.,
proprietary second-generation XFCB process, enabling it to
achieve high levels of performance with very low power
consumption.
The AD8137 is available in the small 8-lead SOIC package and
3 mm × 3 mm LFCSP package. It is rated to operate over the
extended industrial temperature range of −40°C to +125°C.
feedback networks consisting of four resistors determine the
Rev. E
Information furnished by Analog Devices is believed to be accurate and reliable. However, no
responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other
rights of third parties that may result from its use. Specifications subject to change without notice. No
license is granted by implication or otherwise under any patent or patent rights of Analog Devices.
Trademarks and registered trademarks are the property of their respective owners.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781.329.4700
www.analog.com
Fax: 781.461.3113 ©2004–2012 Analog Devices, Inc. All rights reserved.
AD8137
Data Sheet
TABLE OF CONTENTS
Features .............................................................................................. 1
Test Circuits..................................................................................... 21
Theory of Operation ...................................................................... 22
Applications Information.............................................................. 23
Applications....................................................................................... 1
Functional Block Diagram .............................................................. 1
General Descripton .......................................................................... 1
Revision History ............................................................................... 2
Specifications..................................................................................... 3
Absolute Maximum Ratings............................................................ 9
Thermal Resistance ...................................................................... 9
Maximum Power Dissipation ..................................................... 9
ESD Caution.................................................................................. 9
Pin Configuration and Function Descriptions........................... 10
Typical Performance Characteristics ........................................... 11
Analyzing a Typical Application with Matched RF and RG
Networks...................................................................................... 23
Estimating Noise, Gain, and Bandwith with Matched
Feedback Networks.................................................................... 23
Driving an ADC with Greater than 12-Bit Performance...... 27
Outline Dimensions....................................................................... 29
Ordering Guide .......................................................................... 30
Automotive Products................................................................. 30
REVISION HISTORY
7/12—Rev. D to Rev. E
8/04—Rev. 0 to Rev. A.
Changes to Features Section and Applications Section............... 1
Added AD8137W...............................................................Universal
Updated Outline Dimensions ....................................................... 28
Changes to Ordering Guide .......................................................... 29
Added Automotive Products Section .......................................... 29
Added 8-Lead LFCSP.........................................................Universal
Changes to Layout..............................................................Universal
Changes to Product Title and Figure 1...........................................1
Changes to Specifications.................................................................3
Changes to Absolute Maximum Ratings........................................6
Changes to Figure 4 and Figure 5....................................................7
Added Figure 6, Figure 20, Figure 23, Figure 35, Figure 48,
and Figure 58; Renumbered Sequentially ......................................7
Changes to Figure 32...................................................................... 12
Changes to Figure 40...................................................................... 13
Changes to Figure 55...................................................................... 16
Changes to Table 7 and Figure 63................................................. 18
Changes to Equation 19................................................................. 19
Changes to Figure 64 and Figure 65............................................. 20
Changes to Figure 66...................................................................... 22
Added Driving an ADC with Greater Than 12-Bit
7/10—Rev. C to Rev. D
Changes to Power-Down Section, Added Figure 68,
Renumbered Subsequent Figures................................................. 24
Changes to Ordering Guide .......................................................... 27
12/09—Rev. B to Rev. C
Changes to Product Title, Applications Section, and General
Description Section.......................................................................... 1
Changes to Input Resistance Parameter Unit, Table 3................. 5
Added EPAD Mnemonic/Description, Table 6 ............................ 7
Added Figure 61; Renumbered Sequentially .............................. 17
Moved Test Circuits Section.......................................................... 18
Changes to Power Down Section ................................................. 24
Updated Outline Dimensions ....................................................... 26
Performance Section...................................................................... 22
Changes to Ordering Guide.......................................................... 24
Updated Outline Dimensions....................................................... 24
5/04—Revision 0: Initial Version
7/05—Rev. A to Rev. B
Changes to Ordering Guide .......................................................... 24
Rev. E | Page 2 of 32
Data Sheet
AD8137
SPECIFICATIONS
VS = 5 V, VOCM = 0 V (@ 25°C, differential gain = 1, RL, dm = RF = RG = 1 kΩ, unless otherwise noted, TMIN to TMAX = −40°C to +125°C).
Table 1.
Parameter
Conditions
Min
Typ
Max
Unit
DIFFERENTIAL INPUT PERFORMANCE
Dynamic Performance
−3 dB Small Signal Bandwidth
−3 dB Large Signal Bandwidth
VO, dm = 0.1 V p-p
AD8137W only: TMIN-TMAX
VO, dm = 2 V p-p
AD8137W only: TMIN-TMAX
VO, dm = 2 V step
VO, dm = 3.5 V step
64
63
79
79
76
MHz
MHz
MHz
MHz
V/µs
Ns
110
Slew Rate
450
100
85
Settling Time to 0.02%
Overdrive Recovery Time
Noise/Harmonic Performance
G = 2, VI, dm = 12 V p-p triangle wave
Ns
SFDR
VO, dm = 2 V p-p, fC = 500 kHz
VO, dm = 2 V p-p, fC = 2 MHz
f = 50 kHz to 1 MHz
90
76
8.25
1
dB
dB
nV/√Hz
pA/√Hz
Input Voltage Noise
Input Current Noise
DC Performance
f = 50 kHz to 1 MHz
Input Offset Voltage
VIP = VIN = VOCM = 0 V
AD8137W only: TMIN-TMAX
TMIN to TMAX
−2.6
−5.0
0.7
+2.6
+5.0
mV
mV
µV/°C
µA
µA
µA
Input Offset Voltage Drift
Input Bias Current
Input Offset Current
3
TMIN to TMAX
0.5
0.1
1.0
0.45
0.45
AD8137W only: TMIN-TMAX
Open-Loop Gain
91
dB
Input Characteristics
Input Common-Mode Voltage Range
−4
−4
+4
+4
V
V
AD8137W only: TMIN-TMAX
Differential
Common-mode
Common-mode
ΔVICM = 1 V
Input Resistance
800
400
1.8
79
KΩ
KΩ
pF
dB
dB
Input Capacitance
CMRR
66
66
AD8137W only: TMIN-TMAX
Output Characteristics
Output Voltage Swing
Each single-ended output, RL, dm = 1 kΩ
AD8137W only: TMIN-TMAX
VS− + 0.55
VS− + 0.55
VS+ − 0.55
VS+ − 0.55
V
V
Output Current
Output Balance Error
VOCM to VO, cm PERFORMANCE
VOCM Dynamic Performance
−3 dB Bandwidth
Slew Rate
20
−64
mA
dB
f = 1 MHz
VO, cm = 0.1 V p-p
VO, cm = 0.5 V p-p
58
63
1.000
MHz
V/µs
V/V
Gain
0.992
0.990
1.008
1.008
AD8137W only: TMIN-TMAX
AD8137W only: TMIN-TMAX
V/V
VOCM Input Characteristics
Input Voltage Range
−4
−4
+4
+4
V
V
Input Resistance
Input Offset Voltage
35
11
kΩ
mV
mV
nV/√Hz
−28
−28
+28
+28
AD8137W only: TMIN-TMAX
f = 100 kHz to 1 MHz
Input Voltage Noise
18
Rev. E | Page 3 of 32
AD8137
Data Sheet
Parameter
Conditions
Min
Typ
0.3
Max
1.1
Unit
µA
Input Bias Current
AD8137W only: TMIN-TMAX
ΔVO, dm/ΔVOCM, ΔVOCM = 0.5 V
AD8137W only: TMIN-TMAX
1.1
µA
dB
dB
CMRR
62
62
75
Power Supply
Operating Range
+2.7
+2.7
6
6
V
V
AD8137W only: TMIN-TMAX
Quiescent Current
Quiescent Current, Disabled
PSRR
3.2
750
91
3.60
3.65
900
900
mA
mA
µA
µA
dB
dB
AD8137W only: TMIN-TMAX
Power-down = low
AD8137W only: TMIN-TMAX
ΔVS = 1 V
79
79
AD8137W only: TMIN-TMAX
PD Pin
Threshold Voltage
VS− + 0.7
VS− + 0.7
VS− + 1.7
VS− + 1.7
170/240
180/245
+125
V
V
µA
µA
°C
AD8137W only: TMIN-TMAX
Power-down = high/low
AD8137W only: TMIN-TMAX
Input Current
150/210
OPERATING TEMPERATURE RANGE
−40
Rev. E | Page 4 of 32
Data Sheet
AD8137
VS = 5 V, V OCM = 2.5 V (@ 25°C, differential gain = 1, RL, dm = RF = RG = 1 kΩ, unless otherwise noted, TMIN to TMAX = −40°C to +125°C).
Table 2.
Parameter
Conditions
Min
Typ
Max
Unit
DIFFERENTIAL INPUT PERFORMANCE
Dynamic Performance
−3 dB Small Signal Bandwidth
VO, dm = 0.1 V p-p
AD8137W only: TMIN-TMAX
VO, dm = 2 V p-p
AD8137W only: TMIN-TMAX
VO, dm = 2 V step
VO, dm = 3.5 V step
63
61
76
76
75
MHz
MHz
MHz
MHz
V/µs
ns
−3 dB Large Signal Bandwidth
107
Slew Rate
375
110
90
Settling Time to 0.02%
Overdrive Recovery Time
Noise/Harmonic Performance
SFDR
G = 2, VI, dm = 7 V p-p triangle wave
ns
VO, dm = 2 V p-p, fC = 500 kHz
VO, dm = 2 V p-p, fC = 2 MHz
f = 50 kHz to 1 MHz
89
73
8.25
1
dB
dB
nV/√Hz
pA/√Hz
Input Voltage Noise
Input Current Noise
DC Performance
f = 50 kHz to 1 MHz
Input Offset Voltage
VIP = VIN = VOCM = 0 V
AD8137W only: TMIN-TMAX
TMIN to TMAX
−2.7
−5.0
0.7
+2.7
+5.0
mV
mV
µV/°C
µA
µA
µA
Input Offset Voltage Drift
Input Bias Current
Input Offset Current
3
TMIN to TMAX
0.5
0.1
0.9
0.45
0.45
AD8137W only: TMIN-TMAX
Open-Loop Gain
89
dB
Input Characteristics
Input Common-Mode Voltage Range
1
1
4
4
V
V
AD8137W only: TMIN-TMAX
Differential
Common-mode
Common-mode
ΔVICM = 1 V
Input Resistance
800
400
1.8
90
kΩ
kΩ
pF
dB
dB
Input Capacitance
CMRR
64
64
AD8137W only: TMIN-TMAX
Output Characteristics
Output Voltage Swing
Each single-ended output, RL, dm = 1 kΩ
AD8137W only: TMIN-TMAX
VS− + 0.45
VS− + 0.45
VS+ − 0.45
VS+ − 0.45
V
V
Output Current
Output Balance Error
VOCM to VO, cm PERFORMANCE
VOCM Dynamic Performance
−3 dB Bandwidth
Slew Rate
20
−64
mA
dB
f = 1 MHz
VO, cm = 0.1 V p-p
VO, cm = 0.5 V p-p
60
61
1.000
MHz
V/µs
V/V
Gain
0.980
0.975
1.020
1.020
AD8137W only: TMIN-TMAX
AD8137W only: TMIN-TMAX
AD8137W only: TMIN-TMAX
V/V
VOCM Input Characteristics
Input Voltage Range
1
1
4
4
V
V
kΩ
mV
mV
Input Resistance
Input Offset Voltage
35
7.5
−25
−25
+25
+25
Rev. E | Page 5 of 32
AD8137
Data Sheet
Parameter
Conditions
Min
Typ
18
0.25
Max
Unit
nV/√Hz
µA
µA
dB
Input Voltage Noise
Input Bias Current
f = 100 kHz to 5 MHz
0.9
0.9
AD8137W only: TMIN-TMAX
ΔVO, dm /ΔVOCM, ΔVOCM = 0.5 V
AD8137W only: TMIN-TMAX
CMRR
62
62
75
dB
Power Supply
Operating Range
+2.7
+2.7
6
6
V
V
AD8137W only: TMIN-TMAX
Quiescent Current
Quiescent Current, Disabled
PSRR
2.6
450
91
2.8
2.8
600
600
mA
mA
µA
µA
dB
dB
AD8137W only: TMIN-TMAX
Power-down = low
AD8137W only: TMIN-TMAX
ΔVS = 1 V
79
79
AD8137W only: TMIN-TMAX
PD Pin
Threshold Voltage
VS− + 0.7
VS− + 0.7
VS− + 1.5
VS− + 1.5
60/120
60/125
+125
V
V
µA
µA
°C
AD8137W only: TMIN-TMAX
Power-down = high/low
AD8137W only: TMIN-TMAX
Input Current
50/110
OPERATING TEMPERATURE RANGE
−40
Rev. E | Page 6 of 32
Data Sheet
AD8137
VS = 3 V, V OCM = 1.5 V (@ 25°C, differential gain = 1, RL, dm = RF = RG = 1 kΩ, unless otherwise noted, TMIN to TMAX = −40°C to +125°C).
Table 3.
Parameter
Conditions
Min
Typ
Max
Unit
DIFFERENTIAL INPUT PERFORMANCE
Dynamic Performance
−3 dB Small Signal Bandwidth
VO, dm = 0.1 V p-p
AD8137W only: TMIN-TMAX
VO, dm = 2 V p-p
AD8137W only: TMIN-TMAX
VO, dm = 2 V step
VO, dm = 3.5 V step
61
58
62
62
73
93
MHz
MHz
MHz
MHz
V/µs
Ns
−3 dB Large Signal Bandwidth
Slew Rate
340
110
100
Settling Time to 0.02%
Overdrive Recovery Time
Noise/Harmonic Performance
SFDR
G = 2, VI, dm = 5 V p-p triangle wave
Ns
VO, dm = 2 V p-p, fC = 500 kHz
VO, dm = 2 V p-p, fC = 2 MHz
f = 50 kHz to 1 MHz
89
71
8.25
1
dB
dB
nV/√Hz
pA/√Hz
Input Voltage Noise
Input Current Noise
DC Performance
f = 50 kHz to 1 MHz
Input Offset Voltage
VIP = VIN = VOCM = 0 V
AD8137W only: TMIN-TMAX
TMIN to TMAX
−2.75
−5.25
0.7
+2.75
+5.25
mV
mV
µV/°C
µA
µA
µA
Input Offset Voltage Drift
Input Bias Current
Input Offset Current
3
TMIN to TMAX
0.5
0.1
0.9
0.4
0.4
AD8137W only: TMIN-TMAX
Open-Loop Gain
87
dB
Input Characteristics
Input Common-Mode Voltage Range
1
1
2
2
V
V
AD8137W only: TMIN-TMAX
Differential
Common-mode
Common-mode
ΔVICM = 1 V
Input Resistance
800
400
1.8
80
kΩ
kΩ
pF
dB
dB
Input Capacitance
CMRR
64
64
AD8137W only: TMIN-TMAX
Output Characteristics
Output Voltage Swing
Each single-ended output, RL, dm = 1 kΩ
AD8137W only: TMIN-TMAX
VS− + 0.37
VS− + 0.37
VS+ − 0.37
VS+ − 0.37
V
V
Output Current
Output Balance Error
VOCM to VO, cm PERFORMANCE
VOCM Dynamic Performance
−3 dB Bandwidth
Slew Rate
20
−64
mA
dB
f = 1 MHz
VO, cm = 0.1 V p-p
VO, cm = 0.5 V p-p
61
59
1.00
MHz
V/µs
V/V
Gain
0.960
0.955
1.040
1.040
AD8137W only: TMIN-TMAX
AD8137W only: TMIN-TMAX
V/V
VOCM Input Characteristics
Input Voltage Range
1.0
1.0
2.0
2.0
V
V
Input Resistance
35
kΩ
Input Offset Voltage
−25
−25
5.5
+25
+25
mV
mV
nV/√Hz
µA
AD8137W only: TMIN-TMAX
f = 100 kHz to 5 MHz
Input Voltage Noise
Input Bias Current
18
0.3
0.7
0.7
AD8137W only: TMIN-TMAX
µA
Rev. E | Page 7 of 32
AD8137
Data Sheet
Parameter
Conditions
Min
62
62
Typ
Max
Unit
dB
dB
CMRR
ΔVO, dm /ΔVOCM, ΔVOCM = 0.5 V
AD8137W only: TMIN-TMAX
74
Power Supply
Operating Range
+2.7
+2.7
6
6
V
V
AD8137W only: TMIN-TMAX
Quiescent Current
Quiescent Current, Disabled
PSRR
2.3
345
90
2.5
2.5
460
460
mA
mA
µA
µA
dB
dB
AD8137W only: TMIN-TMAX
Power-down = low
AD8137W only: TMIN-TMAX
ΔVS = 1 V
78
78
AD8137W only: TMIN-TMAX
PD Pin
Threshold Voltage
VS− + 0.7
VS− + 0.7
VS− + 1.5
VS− + 1.5
10/70
V
V
µA
µA
°C
AD8137W only: TMIN-TMAX
Power-down = high/low
AD8137W only: TMIN-TMAX
Input Current
8/65
10/75
OPERATING TEMPERATURE RANGE
−40
+125
Rev. E | Page 8 of 32
Data Sheet
AD8137
ABSOLUTE MAXIMUM RATINGS
Table 4.
The power dissipated in the package (PD) is the sum of the
quiescent power dissipation and the power dissipated in the
package due to the load drive for all outputs. The quiescent
power is the voltage between the supply pins (VS) times the
quiescent current (IS). The load current consists of differential
and common-mode currents flowing to the load, as well as
currents flowing through the external feedback networks and
the internal common-mode feedback loop. The internal resistor
tap used in the common-mode feedback loop places a 1 kΩ
differential load on the output. RMS output voltages should be
considered when dealing with ac signals.
Parameter
Rating
Supply Voltage
VOCM
Power Dissipation
Input Common-Mode Voltage
Storage Temperature Range
Operating Temperature Range
Lead Temperature (Soldering, 10 sec)
Junction Temperature
12 V
VS+ to VS−
See Figure 3
VS+ to VS−
−65°C to +125°C
−40°C to +125°C
300°C
150°C
Stresses above those listed under Absolute Maximum Ratings
may cause permanent damage to the device. This is a stress
rating only; functional operation of the device at these or any
other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute
maximum rating conditions for extended periods may affect
device reliability.
Airflow reduces θJA. In addition, more metal directly in contact
with the package leads from metal traces, through holes, ground,
and power planes reduces the θJA.
Figure 3 shows the maximum safe power dissipation in the
package vs. the ambient temperature for the 8-lead SOIC
(125°C/W) and 8-lead LFCSP (θJA = 70°C/W) on a JEDEC
standard 4-layer board. θJA values are approximations.
THERMAL RESISTANCE
3.0
θJA is specified for the worst-case conditions, that is, θJA is
specified for the device soldered in a circuit board in still air.
2.5
LFCSP
Table 5. Thermal Resistance
2.0
Package Type
θJA
157
125
70
θJC
56
56
56
Unit
°C/W
°C/W
°C/W
8-Lead SOIC/2-Layer
8-Lead SOIC/4-Layer
8-Lead LFCSP/4-Layer
1.5
1.0
SOIC-8
0.5
0
MAXIMUM POWER DISSIPATION
The maximum safe power dissipation in the AD8137 package
is limited by the associated rise in junction temperature (TJ) on
the die. At approximately 150°C, which is the glass transition
temperature, the plastic changes its properties. Even temporarily
exceeding this temperature limit may change the stresses that
the package exerts on the die, permanently shifting the parametric
performance of the AD8137. Exceeding a junction temperature
of 175°C for an extended period can result in changes in the
silicon devices, potentially causing failure.
–40–30–20–10
0
10 20 30 40 50 60 70 80 90 100 110120
AMBIENT TEMPERATURE (°C)
Figure 3. Maximum Power Dissipation vs.
Ambient Temperature for a 4-Layer Board
ESD CAUTION
Rev. E | Page 9 of 32
AD8137
Data Sheet
PIN CONFIGURATION AND FUNCTION DESCRIPTIONS
AD8137
–IN
1
2
8
7
6
5
+IN
PD
V
OCM
V
V
3
4
S–
S+
+OUT
–OUT
Figure 4. Pin Configuration
Table 6. Pin Function Descriptions
Pin No.
Mnemonic
Description
1
2
−IN
VOCM
Inverting Input.
An internal feedback loop drives the output common-mode voltage to be equal to the voltage applied to
the VOCM pin, provided the operation of the amplifier remains linear.
3
4
5
6
7
8
VS+
Positive Power Supply Voltage.
+OUT
−OUT
VS−
Positive Side of the Differential Output.
Negative Side of the Differential Output.
Negative Power Supply Voltage.
PD
Power Down.
+IN
Noninverting Input.
EPAD
Exposed paddle may be connected to either ground plane or power plane.
Rev. E | Page 10 of 32
Data Sheet
AD8137
TYPICAL PERFORMANCE CHARACTERISTICS
Unless otherwise noted, differential gain = 1, RG = RF = RL, dm = 1 kΩ, VS = 5 V, T A = 25°C, VOCM = 2.5V. Refer to the basic test circuit in
Figure 60 for the definition of terms.
3
2
3
2
G = 1
G = 1
1
0
1
0
–1
–1
G = 2
G = 5
G = 2
–2
–3
–2
–3
G = 5
–4
–5
–6
–7
–8
–9
–4
–5
–6
–7
–8
–9
G = 10
G = 10
–10
–11
–12
–10
–11
–12
R
V
= 1kΩ
O, dm
G
R = 1kΩ
G
O, dm
= 0.1V p-p
V
= 2.0V p-p
0.1
1
10
FREQUENCY (MHz)
100
1000
0.1
1
10
FREQUENCY (MHz)
100
1000
Figure 8. Large Signal Frequency Response for Various Gains
Figure 5. Small Signal Frequency Response for Various Gains
3
4
V
= +3
V
= +3
V
= +5
S
2
3
2
1
0
S
S
V
= +5
S
1
0
V
= ±5
–1
S
V
= ±5
–2
–3
–1
–2
–3
–4
–5
S
–4
–5
–6
–7
–8
–9
–6
–7
–8
–9
–10
–11
–12
–10
–11
V
= 0.1V p-p
V
= 2.0V p-p
O, dm
O, dm
1
10
100
1000
1
10
100
1000
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 6. Small Signal Frequency Response for Various Power Supplies
Figure 9. Large Signal Frequency Response for Various Power Supplies
3
2
1
0
4
T = +25°C
3
2
1
–1
0
T = +85°C
–2
–1
T = +85°C
–3
–2
T = +25°C
–4
–3
–4
T = +125°C
–5
T = +125°C
T = –40°C
–6
–7
–5
–6
–7
–8
–9
–8
–9
T = –40°C
–10
–11
–12
–10
–11
V
= 0.1V p-p
V
= 2.0V p-p
O, dm
O, dm
1
10
100
1000
1
10
100
1000
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 7. Small Signal Frequency Response at Various Temperatures
Figure 10. Large Signal Frequency Response at Various Temperatures
Rev. E | Page 11 of 32
AD8137
Data Sheet
3
2
1
3
2
1
R
= 500Ω
R
= 1kΩ
L, dm
L, dm
R
0
–1
–2
–3
0
–1
–2
–3
= 2kΩ
L, dm
–4
–4
–5
–6
–5
–6
–7
–8
–7
–8
R
= 2kΩ
L, dm
R
= 500Ω
–9
–9
L, dm
–10
–11
–10
R
= 1kΩ
L, dm
–11
–12
V
= 2V p-p
V
= 0.1V p-p
O, dm
O, dm
–12
1
10
100
1000
1
10
100
1000
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 11. Small Signal Frequency Response for Various Loads
Figure 14. Large Signal Frequency Response for Various Loads
3
2
3
C
= 0pF
2
F
C
= 0pF
C
F
1
0
1
0
C
= 1pF
F
= 1pF
F
–1
–1
–2
–3
–2
–3
C
= 2pF
C = 2pF
F
F
–4
–5
–6
–7
–8
–9
–4
–5
–6
–7
–8
–9
–10
–11
–12
–10
–11
–12
V
= 0.1V p-p
V
= 2.0V p-p
O, dm
O, dm
1
10
100
1000
1
10
100
1000
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 12. Small Signal Frequency Response for Various CF
Figure 15. Large Signal Frequency Response for Various CF
2
3
2
1
V
= 4V
OCM
V
= 2.5V
OCM
1
0
–1
–2
–3
–4
0
V
= 1V
OCM
–1
0.5V p-p
–2
–3
–4
–5
–6
–7
–5
–6
–8
–9
–7
2V p-p
–8
–10
–11
–9
1V p-p
0.1V p-p
–10
–12
–13
–11
–12
V
= 0.1V p-p
O, dm
1
10
100
1000
1
10
100
1000
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 13. Small Signal Frequency Response at Various VOCM
Figure 16. Frequency Response for Various Output Amplitudes
Rev. E | Page 12 of 32
Data Sheet
AD8137
4
3
4
3
2
1
2
1
0
–1
–2
–3
0
–1
–2
–3
R
= 500Ω
F
R
= 2kΩ
F
R
= 2kΩ
R
= 500Ω
F
F
–4
–5
–6
R
= 1kΩ
–4
–5
–6
F
R
= 1kΩ
F
–7
–8
–7
–8
–9
G = 1
–9
V
V
= ±5V
O, dm
G = 1
S
–10
–11
–10
–11
= 0.1V p-p
V
= 2V p-p
O, dm
1
10
100
1000
1
10
100
1000
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 17. Small Signal Frequency Response for Various RF
Figure 20. Large Signal Frequency Response for Various RF
–65
–40
G = 1
G = 1
V
= 2V p-p
V
= 2V p-p
O, dm
O, dm
–70
–75
–80
–85
–90
–95
–50
–60
–70
–80
V
= +3V
S
V
= +3V
S
V
= +5V
S
V
= +5V
S
V
S
= ±5V
V
= ±5V
–90
–100
–110
S
–100
–105
0.1
1
10
0.1
1
FREQUENCY (MHz)
10
FREQUENCY (MHz)
Figure 21. Third Harmonic Distortion vs. Frequency and Supply Voltage
Figure 18. Second Harmonic Distortion vs. Frequency and Supply Voltage
–50
–55
–50
F
= 500kHz
C
–55
–60
–65
SECOND HARMONIC SOLID LINE
THIRD HARMONIC DASHED LINE
V
= +3V
S
–60
–65
V
= +5V
S
V
= +5V
S
–70
–75
–70
–75
V
= +3V
S
–80
–85
–80
–85
V
= +3V
S
V
= +5V
S
V
= +3V
S
V
= +5V
S
–90
–95
–90
–95
F
= 2MHz
C
SECOND HARMONIC SOLID LINE
THIRD HARMONIC DASHED LINE
–100
–100
0.25 1.25 2.25 3.25 4.25 5.25 6.25 7.25 8.25 9.25
(V p-p)
0.25 1.25 2.25 3.25 4.25 5.25 6.25 7.25 8.25 9.25
(V p-p)
V
V
O, dm
O, dm
Figure 22. Harmonic Distortion vs. Output Amplitude and Supply, FC = 2 MHz
Figure 19. Harmonic Distortion vs. Output Amplitude and Supply,
C = 500 kHz
F
Rev. E | Page 13 of 32
AD8137
Data Sheet
–40
–40
V
= 2V p-p
V
= 2V p-p
O, dm
O, dm
–50
–60
–70
–80
–90
–50
–60
–70
–80
–90
R = 200Ω
L, dm
R
= 200Ω
= 500Ω
L, dm
R
= 1kΩ
L, dm
R
= 1kΩ
L, dm
R
L, dm
R
= 500Ω
–100
–110
–100
–110
L, dm
0.1
1
FREQUENCY (MHz)
10
10
10
0.1
1
10
FREQUENCY (MHz)
Figure 23. Second Harmonic Distortion at Various Loads
Figure 26. Third Harmonic Distortion at Various Loads
–40
–40
V
R
= 2V p-p
V
= 2V p-p
O, dm
= 1kΩ
O, dm
R = 1kΩ
G
G
–50
–60
–70
–80
–90
–50
–60
–70
–80
–90
G = 2
G = 5
G = 5
G = 2
G = 1
G = 1
–100
–110
–100
–110
0.1
1
0.1
1
10
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 24. Second Harmonic Distortion at Various Gains
Figure 27. Third Harmonic Distortion at Various Gains
–40
–40
V
= 2V p-p
V
= 2V p-p
O, dm
G = 1
O, dm
G = 1
–50
–60
–70
–80
–90
–50
–60
–70
–80
–90
R
= 500Ω
F
R
= 2kΩ
F
R
= 1kΩ
F
R
= 500Ω
F
–100
–110
–100
–110
R
= 2kΩ
F
R
= 1kΩ
F
0.1
1
0.1
1
10
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 25. Second Harmonic Distortion at Various RF
Figure 28. Third Harmonic Distortion at Various RF
Rev. E | Page 14 of 32
Data Sheet
AD8137
–50
–60
–70
–80
–90
–50
F
= 500kHz
F
V
= 500kHz
C
C
V
= 2V p-p
= 2V p-p
O, dm
O, dm
SECOND HARMONIC SOLID LINE
THIRD HARMONIC DASHED LINE
SECOND HARMONIC SOLID LINE
THIRD HARMONIC DASHED LINE
–60
–70
–80
–90
–100
–110
–100
–110
0.5
0.7
0.9
1.1
1.3
1.5
1.7
1.9
2.1
2.3
2.5
0.5
1.0
1.5
2.0
2.5
3.0
3.5
4.0
4.5
V
(V)
V
(V)
OCM
OCM
Figure 29. Harmonic Distortion vs. VOCM, VS = 5 V
Figure 32. Harmonic Distortion vs. VOCM, VS = 3 V
100
1000
100
10
10
1
10
1
10
100
1k
10k
100k
1M
10M
100M
100
1k
10k
100k
1M
10M
100M
FREQUENCY (Hz)
FREQUENCY (Hz)
Figure 33. VOCM Voltage Noise vs. Frequency
Figure 30. Input Voltage Noise vs. Frequency
–10
–20
20
V
= 0.2V p-p
V
V
= 0.2V p-p
O, cm
IN, cm
10
0
INPUT CMRR = ∆V
∆V
CMRR = ∆V
∆V
OCM
O, cm/
IN, cm
OCM
O, dm/
–30
–40
–10
–20
–30
–50
–60
–40
–50
–60
–70
–80
–70
–80
1
10
FREQUENCY (MHz)
100
1
10
100
FREQUENCY (MHz)
Figure 34. VOCM CMRR vs. Frequency
Figure 31. CMRR vs. Frequency
Rev. E | Page 15 of 32
AD8137
Data Sheet
2.0
8
G = 2
INPUT
× 2
V
1.5
1.0
O, dm
C
= 0pF
6
4
F
V
= 3.5V p-p
O, dm
INPUT
OUTPUT
0.5
0
2
0
ERROR = V
= 110ns
- INPUT
O, dm
–2
–0.5
–1.0
–1.5
–2.0
T
SETTLE
–4
–6
–8
50ns/DIV
250ns/DIV
TIME (ns)
TIME (ns)
Figure 38. Settling Time (0.02%)
Figure 35. Overdrive Recovery
1.5
100
75
50
25
0
C
= 0pF
F
2V p-p
1V p-p
1.0
0.5
0
C
C
= 1pF
= 0pF
F
F
C
= 0pF
F
C
= 1pF
F
C
= 1pF
F
–25
–50
–0.5
–1.0
–1.5
–75
20ns/DIV
V
= 100mV p-p
TIME (ns)
O, dm
10ns/DIV
–100
TIME (ns)
Figure 36. Small Signal Transient Response for Various Feedback
Capacitances
Figure 39. Large Signal Transient Response for Various Feedback
Capacitances
100
75
1.5
R
= 111, C = 5pF
L
S
1.0
0.5
50
R
= 111, C = 5pF
L
S
25
0
R
= 60.4, C = 15pF
L
S
0
R
= 60.4, C = 15pF
L
S
–25
–50
–0.5
–75
–1.0
–1.5
20ns/DIV
20ns/DIV
–100
TIME (ns)
TIME (ns)
Figure 37. Small Signal Transient Response for Various Capacitive Loads
Figure 40. Large Signal Transient Response for Various Capacitive Loads
Rev. E | Page 16 of 32
Data Sheet
AD8137
–5
1000
100
10
PSRR = ∆V
∆V
S
O, dm/
–15
–25
–35
–45
–55
–65
–PSRR
1
0.1
+PSRR
–75
–85
0.01
0.01
0.1
1
10
100
0.1
1
10
100
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 41. PSRR vs. Frequency
Figure 44. Single-Ended Output Impedance vs. Frequency
4.0
1
0
–1
–2
–3
3.5
2V p-p
3.0
–4
–5
1V p-p
–6
–7
2.5
2.0
1.5
V
= ±5
S
V
= +5
S
–8
–9
–10
–11
V
= +3
100
S
–12
–13
–14
20ns/DIV
V
= 0.1V p-p
O, dm
1.0
1
10
FREQUENCY (MHz)
1000
TIME (ns)
Figure 45. VOCM Large Signal Transient Response
Figure 42. VOCM Small Signal Frequency Response for Various Supply Voltages
350
345
340
335
–300
700
600
500
–305
–310
–315
–320
V
S+
– V
OP
400
300
V
– V –
S
ON
200
100
V
= +3V
0
V
= +5V
S
S
–100
–200
–300
–400
–500
–600
–700
V + – V
S
OP
330
V
– V
S–
ON
325
320
–325
–330
–40
–20
0
20
40
60
80
100
120
200
1k
RESISTIVE LOAD (Ω)
10k
TEMPERATURE (°C)
Figure 43. Output Saturation Voltage vs. Output Load
Figure 46. Output Saturation Voltage vs. Temperature
Rev. E | Page 17 of 32
AD8137
Data Sheet
2.60
2.55
2.50
2.45
2.40
0.3
0.2
0.1
0
15
10
5
V
OS, cm
V
OS, dm
0
–0.1
5
–0.2
–0.3
10
2.35
2.30
–15
–40
–20
0
20
40
60
80
100
120
–40
–20
0
20
40
60
80
100
120
TEMPERATURE (°C)
TEMPERATURE (°C)
Figure 47. Offset Voltage vs. Temperature
Figure 50. Supply Current vs. Temperature
1.2
70�
1.0
0.8
0.6
0.4
0.2
0
50
30
10
–10
–30
–50
–70
–0.2
–0.4
0.50
1.50
2.50
(V)
3.50
4.50
0
0.5
1.0
1.5
2.0
2.5
(V)
OCM
3.0
3.5
4.0
4.5
5.0
V
V
ACM
Figure 48. Input Bias Current vs. Input Common-Mode Voltage, VACM
Figure 51. VOCM Bias Current vs. VOCM Input Voltage
0.40
0.35
0.30
0.25
3
–0.1
–0.2
–0.3
2
I
BIAS
1
0
I
OS
0.20
–1
–0.4
–0.5
0.15
0.10
–2
–3
–40
–20
0
20
40
60
80
100
120
–40
–20
0
20
40
60
80
100
120
TEMPERATURE (°C)
TEMPERATURE (°C)
Figure 49. Input Bias and Offset Current vs. Temperature
Figure 52. VOCM Bias Current vs. Temperature
Rev. E | Page 18 of 32
Data Sheet
AD8137
5
4
3
2
1
0
1.5
1.0
V
= +5V
S
V
= ±2.5V
S
G = 1 (R = R = 1kΩ)
R
INPUT = 1Vp-p @ 1MHz
F
G
= 1kΩ
L, dm
V
O, dm
0.5
0
V
= +3V
S
–1
–2
–0.5
–1.0
–1.5
V
= ±5V
S
–3
–0.5V
PD
–4
–5
2µs/DIV
–2.0V
–5
–4
–3
–2
–1
0
1
2
3
4
5
V
TIME (µs)
OCM
Figure 53. VO, cm vs. VOCM Input Voltage
Figure 56. Power-Down Transient Response
40�
3.6
3.2
2.8
20
0
PD (0.8V TO 1.5V)
2.4
2.0
1.6
–20
–40
–60
–80
1.2
0.8
–100
–120
0.4
0
100ns/DIV
0
0.5
1.0
1.5
2.0
2.5
3.0
3.5
4.0
4.5
5.0
PD VOLTAGE (V)
TIME (ns)
Figure 57. Power-Down Turn-On Time
PD
PD
Voltage
Figure 54.
Current vs.
3.4
3
2
PD (1.5V TO 0.8V)
I +
3.0
2.6
2.2
1.8
1.4
S
1
0
–1
1.0
–2
–3
I –
0.6
0.2
S
40ns/DIV
0
0.5
1.0
1.5
2.0
2.5
3.0
3.5
4.0
4.5
5.0
TIME (ns)
PD VOLTAGE (V)
Figure 58. Power-Down Turn-Off Time
PD
Figure 55. Supply Current vs.
Voltage
Rev. E | Page 19 of 32
AD8137
Data Sheet
25
V
V
= ±5V
S
= 0V
OCM
G = +1
20
15
10
5
0
–5
–4
–3
–2
–1
0
1
2
3
4
5
POWER-DOWN VOLTAGE (V)
Figure 59. Supply Current vs. Power-Down Voltage
Rev. E | Page 20 of 32
Data Sheet
AD8137
TEST CIRCUITS
R
C
F
50Ω
50Ω
F
R
R
= 1kΩ
G
52.3Ω
–
+
V
R
1kΩ
V
O, dm
V
MIDSUPPLY
TEST
AD8137
L, dm
OCM
52.3Ω
–
+
= 1kΩ
G
C
F
TEST
SIGNAL
SOURCE
R
F
Figure 60. Basic Test Circuit
R
= 1kΩ
F
50Ω
R
R
R
= 1kΩ
S
G
52.3Ω
–
+
V
C
R
V
V
MIDSUPPLY
52.3Ω
TEST
AD8137
L, dm
L, dm
O, dm
OCM
–
+
50Ω
R
= 1kΩ
S
G
TEST
SIGNAL
SOURCE
R
= 1kΩ
F
Figure 61. Capacitive Load Test Circuit, G = 1
Rev. E | Page 21 of 32
AD8137
Data Sheet
THEORY OF OPERATION
100
The AD8137 is a low power, low cost, fully differential voltage
feedback amplifier that features a rail-to-rail output stage,
common-mode circuitry with an internally derived common-
mode reference voltage, and bias shutdown circuitry. The amplifier
uses two feedback loops to separately control differential and
common-mode feedback. The differential gain is set with external
resistors as in a traditional amplifier, and the output common-
mode voltage is set by an internal feedback loop, controlled by
an external VOCM input. This architecture makes it easy to set
arbitrarily the output common-mode voltage level without
affecting the differential gain of the amplifier.
80
60
40
20
OPEN-LOOP GAIN (dB)
0
–20
–40
–60
–80
–100
–120
–140
–160
PHASE (DEGREES)
–180
–200
0.0001
0.001
0.01
0.1
1
10
100
FREQUENCY (MHz)
V
OCM
Figure 63. Open-Loop Gain and Phase
A
CM
In Figure 62, the common-mode feedback amplifier ACM
samples the output common-mode voltage, and by negative
feedback forces the output common-mode voltage to be equal
to the voltage applied to the VOCM input. In other words, the
feedback loop servos the output common-mode voltage to the
voltage applied to the VOCM input. An internal bias generator
sets the VOCM level to approximately midsupply; therefore, the
output common-mode voltage is set to approximately midsupply
when the VOCM input is left floating. The source resistance of the
internal bias generator is large and can be overridden easily by an
external voltage supplied by a source with a relatively small output
resistance. The VOCM input can be driven to within approximately
1 V of the supply rails while maintaining linear operation in the
common-mode feedback loop.
–OUT
CP +IN
–IN CN
+OUT
C
C
C
C
Figure 62. Block Diagram
From Figure 62, the input transconductance stage is an H-bridge
whose output current is mirrored to high impedance nodes CP
and CN. The output section is traditional H-bridge driven circuitry
with common emitter devices driving nodes +OUT and −OUT.
The 3 dB point of the amplifier is defined as
g m
BW =
The common-mode feedback loop inside the AD8137 produces
outputs that are highly balanced over a wide frequency range
without the requirement of tightly matched external components,
because it forces the signal component of the output common-
mode voltage to be zeroed. The result is nearly perfectly balanced
differential outputs of identical amplitude and exactly 180°
apart in phase.
2π×CC
where:
gm is the transconductance of the input stage.
CC is the total capacitance on node CP/CN (capacitances CP
and CN are well matched).
For the AD8137, the input stage gm is ~1 mA/V and the
capacitance CC is 3.5 pF, setting the crossover frequency of the
amplifier at 41 MHz. This frequency generally establishes an
amplifier’s unity gain bandwidth, but with the AD8137, the
closed-loop bandwidth depends upon the feedback resistor
value as well (see Figure 17). The open-loop gain and phase
simulations are shown in Figure 63.
Rev. E | Page 22 of 32
Data Sheet
AD8137
APPLICATIONS INFORMATION
Output balance is measured by placing a well-matched resistor
divider across the differential voltage outputs and comparing
the signal at the divider’s midpoint with the magnitude of the
differential output. By this definition, output balance is equal to
the magnitude of the change in output common-mode voltage
divided by the magnitude of the change in output differential
mode voltage:
ANALYZING A TYPICAL APPLICATION WITH
MATCHED RF AND RG NETWORKS
Typical Connection and Definition of Terms
Figure 64 shows a typical connection for the AD8137, using
matched external RF/RG networks. The differential input
terminals of the AD8137, VAP and VAN, are used as summing
junctions. An external reference voltage applied to the VOCM
terminal sets the output common-mode voltage. The two
output terminals, VOP and VON, move in opposite directions
in a balanced fashion in response to an input signal.
∆VO, cm
∆VO, dm
Output Balance =
(3)
The differential negative feedback drives the voltages at the summing
junctions VAN and VAP to be essentially equal to each other.
C
F
V
AN = VAP
(4)
R
F
R
R
V
V
V
G
AP
ON
The common-mode feedback loop drives the output common-
mode voltage, sampled at the midpoint of the two internal
common-mode tap resistors in Figure 62, to equal the voltage
set at the VOCM terminal. This ensures that
V
–
IP
+
V
OCM
R
V
L, dm
AD8137
O, dm
G
V
AN
OP
V
–
IN
+
R
F
F
VO, dm
VOP =VOCM
+
(5)
2
C
and
Figure 64. Typical Connection
VO, dm
2
The differential output voltage is defined as
O, dm = VOP − VON
VON =VOCM
−
(6)
V
(1)
(2)
ESTIMATING NOISE, GAIN, AND BANDWITH WITH
MATCHED FEEDBACK NETWORKS
Estimating Output Noise Voltage and Bandwidth
Common-mode voltage is the average of two voltages. The
output common-mode voltage is defined as
VOP + VON
VO, cm
=
The total output noise is the root-sum-squared total of several
statistically independent sources. Because the sources are
statistically independent, the contributions of each must be
individually included in the root-sum-square calculation. Table 7
lists recommended resistor values and estimates of bandwidth
and output differential voltage noise for various closed-loop
gains. For most applications, 1% resistors are sufficient.
2
Output Balance
Output balance is a measure of how well VOP and VON are
matched in amplitude and how precisely they are 180° out of
phase with each other. It is the internal common-mode feedback
loop that forces the signal component of the output common-
mode toward zero, resulting in the near perfectly balanced
differential outputs of identical amplitude and are exactly 180°
out of phase. The output balance performance does not require
tightly matched external components, nor does it require that
the feedback factors of each loop be equal to each other. Low
frequency output balance is ultimately limited by the mismatch
of an on-chip voltage divider.
Table 7. Recommended Values of Gain-Setting Resistors and
Voltage Gain for Various Closed-Loop Gains
3 dB Bandwidth
Gain RG (Ω) RF (Ω) (MHz)
Total Output
Noise (nV/√Hz)
1
2
5
10
1 k
1 k
1 k
1 k
1 k
2 k
5 k
10 k
72
40
12
6
18.6
28.9
60.1
112.0
Rev. E | Page 23 of 32
AD8137
Data Sheet
Feedback Factor Notation
The differential output voltage noise contains contributions
from the AD8137’s input voltage noise and input current noise
as well as those from the external feedback networks.
When working with differential drivers, it is convenient to
introduce the feedback factor β, which is defined as
RG
β ≡
The contribution from the input voltage noise spectral density
is computed as
(14)
RF + RG
RF
RG
This notation is consistent with conventional feedback analysis
and is very useful, particularly when the two feedback loops are
not matched.
Vo_n1 = v 1+
, or equivalently, vn/β
(7)
n
where vn is defined as the input-referred differential voltage
noise. This equation is the same as that of traditional op amps.
Input Common-Mode Voltage
The linear range of the VAN and VAP terminals extends to within
approximately 1 V of either supply rail. Because VAN and VAP are
essentially equal to each other, they are both equal to the amplifier’s
input common-mode voltage. Their range is indicated in the
specifications tables as input common-mode range. The voltage
at VAN and VAP for the connection diagram in Figure 64 can be
expressed as
The contribution from the input current noise of each input is
computed as
Vo_n2 = in
(
RF
)
(8)
where in is defined as the input noise current of one input. Each
input needs to be treated separately because the two input currents
are statistically independent processes.
VAN = VAP = VACM =
The contribution from each RG is computed as
(
VIP +VIN
)
RG
RF + RG
RF
RF + RG
R
RG
×
+
×VOCM
(15)
F
Vo_n3 = 4kTR
(9)
G
2
where VACM is the common-mode voltage present at the amplifier
input terminals.
This result can be intuitively viewed as the thermal noise of
each RG multiplied by the magnitude of the differential gain.
Using the β notation, Equation (15) can be written as
The contribution from each RF is computed as
Vo_n 4 = 4kTRF
V
ACM = βVOCM + (1 − β)VICM
or equivalently,
ACM = VICM + β(VOCM − VICM
(16)
(17)
(10)
Voltage Gain
V
)
The behavior of the node voltages of the single-ended-to-
differential output topology can be deduced from the signal
definitions and Figure 64. Referring to Figure 64, CF = 0 and
setting VIN = 0, one can write:
where VICM is the common-mode voltage of the input signal,
that is
VIP + VIN
VICM
≡
2
VIP −VAP VAP −VON
(11)
(12)
=
RG
RF
For proper operation, the voltages at VAN and VAP must stay
within their respective linear ranges.
OP
RG
RF + RG
VAN = VAP = V
Calculating Input Impedance
The input impedance of the circuit in Figure 64 depends on
whether the amplifier is being driven by a single-ended or a
differential signal source. For balanced differential input
signals, the differential input impedance (RIN, dm) is simply
Solving the previous two equations and setting VIP to Vi gives
the gain relationship for VO, dm/Vi.
R
F
V
OP
− V
= V
=
V
i
(13)
ON
O, dm
R
G
RIN, dm = 2RG
(18)
An inverting configuration with the same gain magnitude can
be implemented by simply applying the input signal to VIN and
setting VIP = 0. For a balanced differential input, the gain from
For a single-ended signal (for example, when VIN is grounded
and the input signal drives VIP), the input impedance becomes
R
G
R
R
=
(19)
IN
VIN, dm to VO, dm is also equal to RF/RG, where VIN, dm = VIP − VIN.
F
1−
2(R + R )
G
F
Rev. E | Page 24 of 32
Data Sheet
AD8137
5V
0.1µF
1kΩ
0.1µF
1kΩ
50Ω
3
1.0nF
1.0nF
5
8
2
1
+
VDD
V
OCM
V
V
–
+
IN
AD8137
+2.5V
GND
–2.5V
V
–
IN
AD7450A
4
6
V
REFB
IN
1kΩ
1kΩ
50Ω
GND
V
REF
2.5kΩ
+1.88V
V
V
+1.25V
+0.63V
ACM WITH
= 0
REFB
ADR525A
2.5V SHUNT
REFERENCE
2.5V
V
REFA
Figure 65. AD8137 Driving AD7450A, 12-Bit ADC
5V
The input impedance of a conventional inverting op amp
configuration is simply RG; however, it is higher in Equation 19
because a fraction of the differential output voltage appears at
the summing junctions, VAN and VAP. This voltage partially
bootstraps the voltage across the input resistor RG, leading to
the increased input resistance.
0.1µF
1kΩ
3
1kΩ
5
8
+
V
OCM
2
V
IN
0V TO 5V
AD8137
1
–
4
Input Common-Mode Swing Considerations
6
In some single-ended-to-differential applications, when using a
single-supply voltage, attention must be paid to the swing of the
1kΩ
1kΩ
TO
5V
AD7450A
0.1µF
10kΩ
V
REF
input common-mode voltage, VACM
.
ADR525A
2.5V SHUNT
REFERENCE
0.1µF
+
+
AD8031
–
Consider the case in Figure 65, where VIN is 5 V p-p swinging
about a baseline at ground and VREFB is connected to ground.
The input signal to the AD8137 is originating from a source
with a very low output resistance.
10µF
0.1µF
The circuit has a differential gain of 1.0 and β = 0.5. VICM has an
amplitude of 2.5 V p-p and is swinging about ground. Using the
results in Equation 16, the common-mode voltage at the inputs of
the AD8137, VACM, is a 1.25 V p-p signal swinging about a baseline
of 1.25 V. The maximum negative excursion of VACM in this case is
0.63 V, which exceeds the lower input common-mode voltage limit.
Figure 66. Low-Z Bias Source
Another way to avoid the input common-mode swing limitation
is to use dual power supplies on the AD8137. In this case, the
biasing circuitry is not required.
Bandwidth vs. Closed-Loop Gain
One way to avoid the input common-mode swing limitation is
to bias VIN and VREF at midsupply. In this case, VIN is 5 V p-p
swinging about a baseline at 2.5 V, and VREF is connected to a
low-Z 2.5 V source. VICM now has an amplitude of 2.5 V p-p and
is swinging about 2.5 V. Using the results in Equation 17, VACM
is calculated to be equal to VICM because VOCM = VICM. Therefore,
The 3 dB bandwidth of the AD8137 decreases proportionally
to increasing closed-loop gain in the same way as a traditional
voltage feedback operational amplifier. For closed-loop gains
greater than 4, the bandwidth obtained for a specific gain can
be estimated as
RG
f
−3dB ,VO, dm
=
×(72 MHz)
(20)
VICM swings from 1.25 V to 3.75 V, which is well within the input
RG + RF
or equivalently, β(72 MHz).
This estimate assumes a minimum 90° phase margin for the
common-mode voltage limits of the AD8137. Another benefit
seen by this example is that because VOCM = VACM = VICM, no
wasted common-mode current flows. Figure 66 illustrates a way
to provide the low-Z bias voltage. For situations that do not
require a precise reference, a simple voltage divider suffices to
develop the input voltage to the buffer.
amplifier loop, a condition approached for gains greater than 4.
Lower gains show more bandwidth than predicted by the equation
due to the peaking produced by the lower phase margin.
Rev. E | Page 25 of 32
AD8137
Data Sheet
Estimating DC Errors
Driving a Capacitive Load
Primary differential output offset errors in the AD8137 are due
to three major components: the input offset voltage, the offset
between the VAN and VAP input currents interacting with the
feedback network resistances, and the offset produced by the
dc voltage difference between the input and output common-
mode voltages in conjunction with matching errors in the
feedback network.
A purely capacitive load reacts with the bondwire and pin
inductance of the AD8137, resulting in high frequency ringing
in the transient response and loss of phase margin. One way to
minimize this effect is to place a small resistor in series with
each output to buffer the load capacitance. The resistor and load
capacitance forms a first-order, low-pass filter; therefore, the
resistor value should be as small as possible. In some cases, the
ADCs require small series resistors to be added on their inputs.
The first output error component is calculated as
Figure 37 and Figure 40 illustrate transient response vs. capacitive
load and were generated using series resistors in each output
and a differential capacitive load.
R + R
RG
F
G
Vo_e1 =V
, or equivalently as VIO/β
(21)
(22)
IO
where VIO is the input offset voltage.
Layout Considerations
The second error is calculated as
Standard high speed PCB layout practices should be adhered
to when designing with the AD8137. A solid ground plane is
recommended and good wideband power supply decoupling
networks should be placed as close as possible to the supply pins.
R + R
RGRF
RF + RG
F
G
Vo_e 2 = I
= I RF
( )
IO
IO
RG
where IIO is defined as the offset between the two input bias
To minimize stray capacitance at the summing nodes, the
copper in all layers under all traces and pads that connect to
the summing nodes should be removed. Small amounts of stray
summing-node capacitance cause peaking in the frequency
response, and large amounts can cause instability. If some stray
summing-node capacitance is unavoidable, its effects can be
compensated for by placing small capacitors across the feedback
resistors.
currents.
The third error voltage is calculated as
Vo_e3 = Δenr × (VICM − VOCM
)
(23)
where Δenr is the fractional mismatch between the two feedback
resistors.
The total differential offset error is the sum of these three error
sources.
Terminating a Single-Ended Input
Additional Impact of Mismatches in the Feedback Networks
Controlled impedance interconnections are used in most high
speed signal applications, and they require at least one line
termination. In analog applications, a matched resistive termination
is generally placed at the load end of the line. This section deals
with how to properly terminate a single-ended input to the AD8137.
The internal common-mode feedback network still forces the
output voltages to remain balanced, even when the RF/RG feed-
back networks are mismatched. The mismatch, however, causes
a gain error proportional to the feedback network mismatch.
Ratio-matching errors in the external resistors degrade the
ability to reject common-mode signals at the VAN and VIN input
terminals, similar to a four resistor, difference amplifier made
from a conventional op amp. Ratio-matching errors also produce a
differential output component that is equal to the VOCM input
voltage times the difference between the feedback factors (βs).
In most applications using 1% resistors, this component amounts
to a differential dc offset at the output that is small enough to
be ignored.
The input resistance presented by the AD8137 input circuitry
is seen in parallel with the termination resistor, and its loading
effect must be taken into account. The Thevenin equivalent
circuit of the driver, its source resistance, and the termination
resistance must all be included in the calculation as well. An
exact solution to the problem requires solution of several
simultaneous algebraic equations and is beyond the scope of
this data sheet. An iterative solution is also possible and is easier,
especially considering the fact that standard resistor values are
generally used.
Rev. E | Page 26 of 32
Data Sheet
AD8137
Figure 67 shows the AD8137 in a unity-gain configuration, and
with the following discussion, provides a good example of how
to provide a proper termination in a 50 Ω environment.
Power-Down
PD
The AD8137 features a
pin that can be used to minimize the
quiescent current consumed when the device is not being used.
PD
+5V
is asserted by applying a low logic level to Pin 7. The threshold
between high and low logic levels is nominally 1.1 V above the
negative supply rail. See Table 1 to Table 3 for the threshold limits.
0.1µF
PD
The AD8137
pin features an internal pull-up network that
1kΩ
–
PD
enables the amplifier for normal operation. The AD8137
pin can be left floating (that is, no external connection is
3
2V p-p
50Ω
1kΩ
5
8
2
1
+
R
V
T
OCM
V
IN
required) and does not require an external pull-up resistor to
AD8137
0V
52.3Ω
SIGNAL
SOURCE
ensure normal on operation (see Figure 68).
–
4
6
1.02kΩ
PD
Do not connect the
pin directly to VS+ in 5 V applications.
+
1kΩ
This can cause the amplifier to draw excessive supply current
(see Figure 59) and may induce oscillations and/or stability
issues.
0.1µF
–5V
Figure 67. AD8137 with Terminated Input
+V
S
The 52.3 Ω termination resistor, RT, in parallel with the 1 kΩ
input resistance of the AD8137 circuit, yields an overall input
resistance of 50 Ω that is seen by the signal source. To have
matched feedback loops, each loop must have the same RG if it
has the same RF. In the input (upper) loop, RG is equal to the 1 kΩ
resistor in series with the (+) input plus the parallel combination
of RT and the source resistance of 50 Ω. In the upper loop, RG is
therefore equal to 1.03 kΩ. The closest standard value is 1.02 kΩ
and is used for RG in the lower loop.
+V
S
50kΩ
Q1
Q2
5kΩ
PD
REF A
150kΩ
–V
S
PD
Figure 68.
Pin Circuit
DRIVING AN ADC WITH GREATER THAN 12-BIT
PERFORMANCE
Things become more complicated when it comes to determining
the feedback resistor values. The amplitude of the signal source
generator VIN is two times the amplitude of its output signal when
terminated in 50 Ω. Therefore, a 2 V p-p terminated amplitude
is produced by a 4 V p-p amplitude from VS. The Thevenin
equivalent circuit of the signal source and RT must be used when
calculating the closed-loop gain because RG in the upper loop is
split between the 1 kΩ resistor and the Thevenin resistance
looking back toward the source. The Thevenin voltage of the
signal source is greater than the signal source output voltage
when terminated in 50 Ω because RT must always be greater
than 50 Ω. In this case, RT is 52.3 Ω and the Thevenin voltage
and resistance are 2.04 V p-p and 25.6 Ω, respectively.
Because the AD8137 is suitable for 12-bit systems, it is desirable
to measure the performance of the amplifier in a system with
greater than 12-bit linearity. In particular, the effective number
of bits (ENOB) is most interesting. The AD7687, 16-bit, 250 KSPS
ADC performance makes it an ideal candidate for showcasing
the 12-bit performance of the AD8137.
For this application, the AD8137 is set in a gain of 2 and driven
single-ended through a 20 kHz band-pass filter, while the output
is taken differentially to the input of the AD7687 (see Figure 69).
This circuit has mismatched RG impedances and, therefore, has a
dc offset at the differential output. It is included as a test circuit to
illustrate the performance of the AD8137. Actual application
circuits should have matched feedback networks.
Now the upper input branch can be viewed as a 2.04 V p-p
source in series with 1.03 kΩ. Because this is to be a unity-gain
application, a 2 V p-p differential output is required, and RF
must therefore be 1.03 kΩ × (2/2.04) = 1.01 kΩ ≈ 1 kΩ.
For an AD7687 input range up to −1.82 dBFS, the AD8137 power
supply is a single 5 V applied to VS+ with VS− tied to ground. To
increase the AD7687 input range to −0.45 dBFS, the AD8137
supplies are increased to +6 V and −1 V. In both cases, the VOCM
This example shows that when RF and RG are large compared to RT,
the gain reduction produced by the increase in RG is essentially
cancelled by the increase in the Thevenin voltage caused by RT
being greater than the output resistance of the signal source. In
general, as RF and RG become smaller in terminated applications,
RF needs to be increased to compensate for the increase in RG.
PD
pin is biased with 2.5 V and the
pin is left floating. All voltage
supplies are decoupled with 0.1 µF capacitors. Figure 70 and
Figure 71 show the performance of the −1.82 dBFS setup and the
−0.45 dBFS setup, respectively.
When generating the typical performance characteristics data,
the measurements were calibrated to take the effects of the
terminations on closed-loop gain into account.
Rev. E | Page 27 of 32
AD8137
Data Sheet
V +
S
1.0kΩ
20kHz
V+
GND
33Ω
33Ω
499Ω
499Ω
V
+
IN
V
DD
BPF
V
1nF
1nF
OCM
AD8137
AD7687
GND
–
1.0kΩ
+2.5
V –
S
Figure 69. AD8137 Driving AD7687, 16-Bit 250 KSPS ADC
0
0
–10
–20
THD = –91.75dBc
SNR = 91.35dB
SINAD = 88.75dB
ENOB = 14.4
–10
THD = –93.63dBc
SNR = 91.10dB
SINAD = 89.74dB
ENOB = 14.6
–20
–30
–40
–50
–60
–70
–80
–90
–100
–30
–40
–50
–60
–70
–80
–90
–100
–110
–120
–130
–110
–120
–130
–140
–140
–150
–160
–170
0
–150
–160
0
20
40
60
80
100
120
140
20
40
60
80
100
120
140
FREQUENCY (kHz)
FREQUENCY (kHz)
Figure 71. AD8137 Performance on +6 V, −1 V Supplies, −0.45 dBFS
Figure 70. AD8137 Performance on Single 5 V Supply, −1.82 dBFS
Rev. E | Page 28 of 32
Data Sheet
AD8137
OUTLINE DIMENSIONS
5.00 (0.1968)
4.80 (0.1890)
8
1
5
4
6.20 (0.2441)
5.80 (0.2284)
4.00 (0.1574)
3.80 (0.1497)
0.50 (0.0196)
0.25 (0.0099)
1.27 (0.0500)
BSC
45°
1.75 (0.0688)
1.35 (0.0532)
0.25 (0.0098)
0.10 (0.0040)
8°
0°
0.51 (0.0201)
0.31 (0.0122)
COPLANARITY
0.10
1.27 (0.0500)
0.40 (0.0157)
0.25 (0.0098)
0.17 (0.0067)
SEATING
PLANE
COMPLIANT TO JEDEC STANDARDS MS-012-AA
CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS
(IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR
REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN.
Figure 72. 8-Lead Standard Small Outline Package [SOIC_N]
Narrow Body
(R-8)
Dimensions shown in millimeters and (inches)
1.84
1.74
1.64
3.10
3.00 SQ
2.90
0.50 BSC
8
5
PIN 1 INDEX
EXPOSED
PAD
1.55
1.45
1.35
AREA
0.50
0.40
0.30
4
1
PIN 1
INDICATOR
(R 0.15)
TOP VIEW
BOTTOM VIEW
FOR PROPER CONNECTION OF
THE EXPOSED PAD, REFER TO
THE PIN CONFIGURATION AND
FUNCTION DESCRIPTIONS
0.80
0.75
0.70
0.05 MAX
0.02 NOM
COPLANARITY
0.08
SECTION OF THIS DATA SHEET.
SEATING
PLANE
0.30
0.25
0.20
0.203 REF
COMPLIANT TOJEDEC STANDARDS MO-229-WEED
Figure 73. 8-Lead Lead Frame Chip Scale Package [LFCSP_WD]
3 mm × 3 mm Body, Very Very Thin, Dual Lead
(CP-8-13)
Dimensions shown in millimeters
Rev. E | Page 29 of 32
AD8137
Data Sheet
ORDERING GUIDE
Model1, 2
AD8137YR
AD8137YR-REEL7
AD8137YRZ
AD8137YRZ-REEL
AD8137YRZ-REEL7
AD8137YCPZ-R2
AD8137YCPZ-REEL
AD8137YCPZ-REEL7
AD8137WYCPZ-R7
AD8137YCP-EBZ
AD8137YR-EBZ
Temperature Range
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
Package Description
Package Option
Branding
8-Lead Standard Small Outline Package (SOIC_N)
8-Lead Standard Small Outline Package (SOIC_N)
8-Lead Standard Small Outline Package (SOIC_N)
8-Lead Standard Small Outline Package (SOIC_N)
8-Lead Standard Small Outline Package (SOIC_N)
8-Lead Lead Frame Chip Scale Package (LFCSP_WD)
8-Lead Lead Frame Chip Scale Package (LFCSP_WD)
8-Lead Lead Frame Chip Scale Package (LFCSP_WD)
8-Lead Lead Frame Chip Scale Package (LFCSP_WD)
LFCSP Evaluation Board
R-8
R-8
R-8
R-8
R-8
CP-8-13
CP-8-13
CP-8-13
CP-8-13
HFB#
HFB#
HFB#
H2G
SOIC Evaluation Board
1 Z = RoHS Compliant Part; # denotes that RoHS part may be top or bottom marked.
2 W = Qualified for Automotive Applications.
AUTOMOTIVE PRODUCTS
The AD8137W models are available with controlled manufacturing to support the quality and reliability requirements of automotive
applications. Note that these automotive models may have specifications that differ from the commercial models; therefore, designers
should review the Specifications section of this data sheet carefully. Only the automotive grade products shown are available for use in
automotive applications. Contact your local Analog Devices account representative for specific product ordering information and to
obtain the specific Automotive Reliability reports for these models.
Rev. E | Page 30 of 32
Data Sheet
NOTES
AD8137
Rev. E | Page 31 of 32
AD8137
NOTES
Data Sheet
©2004–2012 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
D04771-0-7/12(E)
Rev. E | Page 32 of 32
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